JP6504850B2 - Control device, rotary electric machine using the same, and drive system including the control device and the rotary electric machine - Google Patents

Description

  The present invention relates to a control device for a rotating electrical machine, a rotating electrical machine using the same, and a drive system including the control device and the rotating electrical machine.

Conventionally, electric energy is lost in the magnetization of the magnetic body constituting the stator or the rotor when the rotary electric machine is driven to rotate. Various efforts have been made to reduce this loss.
In particular, in order to reduce the iron loss due to the harmonic component of the magnetic flux passing through the magnetic body, a magnetic flux filter circuit having a flux filter winding is provided on the stator core of the rotating electric machine. It is proposed to attenuate the (For example, refer to patent document 1)

JP, 2008-301551, A

According to the technology proposed in Patent Document 1, it is possible to attenuate time harmonics whose frequency is farther than the fundamental wave frequency of the rotating electrical machine, such as harmonics resulting from the switching of the inverter-driven rotating electrical machine. There is a problem that the size of the rotating electric machine is increased because a dedicated flux filter winding is required separately from the armature winding of the rotating electric machine.
SUMMARY OF THE INVENTION An object of the present invention is to provide a control device capable of reducing the size of a rotating electrical machine while reducing iron loss in response to distortion of a magnetic flux waveform due to a fundamental wave of magnetic flux and magnetic flux of harmonics.

A control device according to the present invention includes a magnetic flux calculating unit for calculating a magnetic flux passing through a stator core salient pole portion projecting at equal intervals in a radial direction from an annular yoke in a rotating electrical machine; and the stator core salient pole A magnetic flux command unit for generating a magnetic flux command value for reducing harmonics to the fundamental wave of the magnetic flux including the magnetic flux produced by a phase conductor wound around the part; and supplying the rotating electric machine based on the magnetic flux and the magnetic flux command value Control voltage.

  The control device configured in this way controls the voltage supplied to the rotating electrical machine based on the magnetic flux and the magnetic flux command value, and hence a dedicated magnetic flux filter winding is not required. The rotating electric machine can be miniaturized while reducing the iron loss corresponding to the distortion of the waveform.

FIG. 1 is a schematic diagram showing a drive system in a first embodiment. FIG. 3 is a cross-sectional view along the rotation axis showing the structure of the motor in the first embodiment. FIG. 2 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor in the first embodiment. FIG. 1 is a circuit diagram showing an inverter according to a first embodiment. FIG. 2 is a diagram showing a hardware configuration of a drive system according to Embodiment 1. FIG. 2 is a block diagram showing a configuration of a control device in Embodiment 1. FIG. 5 is a block diagram showing an operation of a control device according to Embodiment 1. FIG. 10 is a cross-sectional view perpendicular to the rotation axis showing the structure of a motor according to a second embodiment. FIG. 10 is a cross-sectional view perpendicular to the rotation axis showing the structure of a motor according to Embodiment 3; FIG. 14 is a cross-sectional view perpendicular to the rotation axis showing the structure of a motor according to a fourth embodiment.

Embodiment 1
FIG. 1 is a schematic diagram showing a drive system 100 including an electric rotating machine having an 8-pole, 48-slot, 6-DOF H-bridge configuration, which is a target of Embodiment 1 of the present invention. FIG. 2 is a cross-sectional view along the rotation axis for showing the structure of the motor 1 in FIG. FIG. 3 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor 1 in FIG. FIG. 4 is a circuit diagram showing inverter 200 in FIG. FIG. 5 is a block diagram showing control device 300 in FIG. FIG. 6 is a block diagram showing the operation of each block of control device 300 in FIG. 1, that is, control device 300 shown in FIG.

As shown in FIG. 1, a drive system 100 targeted by the present invention is a device for driving a load 50 by the power of a power supply 27. The drive system 100 detects the states of an inverter 200 which is a power converter for converting DC power and AC power to each other, a motor 1 which is a rotating electric machine connected to the AC side terminal of the inverter 200, and the motor 1. And a control device 300 which performs calculation based on the detected information, inputs a control signal to the inverter 200, and controls the state of the motor 1, and the DC side terminal of the inverter 200 is connected to the external DC power supply 27. Connected and the motor 1 will be connected to an external load 50 to transmit rotational movement to the load 50.
The motor 1 used here is a permanent magnet motor having 8 poles and 48 slots.

The structure of the motor 1 will be described with reference to FIG. The motor 1, which is a rotating electric machine, is disposed on the central axis of the frame 2, a cylindrical frame 2, a load side bracket 3 and an anti-load side bracket 4 provided covering the both sides of the frame 2, and The shaft 7 rotatably supported at two points by the bracket 3 and the anti-load side bracket 4 via the load-side bearing 5 and the anti-load-side bearing 6 and the shaft 7 are inserted and integrated with a key or the like. The rotor 8 housed in the case 10 composed of the side bracket 3 and the anti-load side bracket 4 and an annular ring fixed to the inner wall surface of the frame 2 by press fitting or shrinkage fit and so on A stator 9 is provided.
The load side bearing 5 of the motor 1 is fixed to the load side bracket 3 by a bearing retainer 11 in the axial direction with a bolt or the like. The non-load side bearing 6 is axially fixed to the non-load side bracket 4 via a wave washer 12 with a degree of freedom.
The case 10 is formed by fixing the load side bracket 3 and the non-load side bracket 4 to the frame 2 with a bolt or the like.

As shown in FIG. 3, the stator 9 has a stator core 15 having teeth 14 which are 48 stator iron core salient pole portions projecting at equal intervals inward in the radial direction from the inner peripheral side of the annular yoke 13, and the teeth The phase conductors 17a to 17f inserted in the respective stator slots 16 formed in the axial direction and formed between the fourteen and an insulator 18 covering the phase conductors 17a to 17f.
The stator core 15 is formed by laminating a plurality of thin steel plates such as electromagnetic steel plates whose both surfaces are subjected to insulation processing.
Each of the phase conductors 17 a to 17 f is integrally molded with the insulator 18, and each of the phase conductors 17 a to 17 f covered with the insulator 18 is fixed to the stator core 15 by being press-fit into each stator slot 16.
The rotor 8 has a cylindrical rotor core 19 formed with a total of eight circumferentially equally spaced magnetic slots 20 extending in the axial direction, and N poles and S poles alternately in each magnet slot 20 on the outer diameter side And an end plate 22 which is fixed to both ends in the axial direction of the rotor core 19 and which closes both sides of the magnet slot 20. The end plate 22 is preferably made of nonmagnetic material.

Each phase conductor 17a-17f passes through the stator slot 16 from one end in the axial direction of the stator core 15 and is exposed at the other end, and then continues to have one pole pitch, that is, the sixth stator slot 16 in the circumferential direction. After being inserted from the end into the stator slot 16 and exposed at one end, the stator slot 16 is inserted again from one end of the stator slot 16 of one pole pitch in the circumferential direction and exposed at the other end.
Each of the phase conductors 17a to 17f is formed by wave winding in which such insertion of each stator slot 16 is repeated three times in total in the circumferential direction of the stator core 15.
In FIG. 3, phase conductors 17 a to 17 f are inserted into stator slot 16 as a pair of phase conductors which are electrically conducted and form one phase. The stator core 15 is wound with phase conductors 17a to 17f having a total of six or six-phase wave wound configurations.
Further, in FIG. 3, although the cross sections of the phase conductors 17 a to 17 f should be shown as being divided into three in the radial direction in practice, they are collectively described as one.

The respective phase conductors 17 a to 17 f are connected to one end of each of the load side lead 23 and the non-load side lead 24 at both ends. The load side leads 23 and the non-load side leads 24 are respectively drawn out of the motor 1 through the outlets 25 formed in the frame 2.
FIG. 4 is a circuit diagram showing inverter 200. Referring to FIG. The inverter 200 is composed of six inverter subunits 201.

The load side lead 23 of the inverter subunit 201 is electrically connected to the positive electrode terminal 31 of the DC power supply 27 through the first positive electrode side switch 26 which turns on and off the current, and controls the current on and off It is electrically connected to the negative electrode terminal 32 of the DC power supply 27 via the second negative electrode side switch 28 which is a load side control component.
The non-load side reed 24 is electrically connected to the negative electrode terminal 32 of the DC power supply 27 via the first negative electrode side switch 29 which turns on and off the current, and positive electrode side control which controls the current on and off It is electrically connected to the positive electrode terminal 31 of the DC power supply 27 via the second positive electrode side switch 30 which is a component.

Thus, in the inverter subunit 201, a so-called H bridge circuit is configured by the first positive electrode side switch 26, the second negative electrode side switch 28, the first negative electrode side switch 29, and the second positive electrode side switch 30. ing.
Although the first positive electrode side switch 26, the second positive electrode side switch 30, the first negative electrode side switch 29, and the second negative electrode side switch 28 are constituted by an insulated gate bipolar transistor (IGBT) using a silicon semiconductor, , And may be configured by a field effect transistor (MOS-FET).
In addition, the semiconductor switch may be configured using a wide band gap semiconductor such as silicon carbide (SiC) or gallium nitride (GaN).
Although not shown, the first positive side switch 26, the second positive side switch 30, the first negative side switch 29, and the second negative side switch 28 are respectively switches 26, 30, 29, 28 and A reflux diode is inserted in parallel.
The DC power supply 27 is configured of a lead battery, a lithium ion battery, or the like.

Each individual phase conductor 17 is electrically connected to an individual H bridge circuit, and a DC power supply 27 is individually provided for each H bridge circuit.
That is, each of inverter sub-units 201 which is a part of the power converter corresponds to one end of phase conductor 17 which is load side lead 23 and DC power supply 27 with respect to each of phase conductor 17 of motor 1 which is a rotating electric machine. It comprises a first positive side switch 26 between the positive electrode terminal 31 and a second negative side switch 28 between one end of the phase conductor 17 which is the load side lead 23 and the negative electrode terminal 32 of the DC power supply 27. Between the other switch of the first switch group and the other end of the phase conductor 17 which is the non-load side lead 24 and the positive electrode terminal 31 of the DC power supply 27 and the phase conductor which is the non-load side lead 24 A second switch group including a first negative electrode side switch 29 is provided between the other end of the second terminal 17 and the negative electrode terminal 32 of the DC power supply 27.
In FIG. 1, when the first positive electrode side switch 26 and the first negative electrode side switch 29 are turned on and the second negative electrode side switch 28 and the second positive electrode side switch 30 are turned off by driving of the control device, The end of the load-side lead 23 has a potential on the positive electrode side, and the end of the non-load-side lead 24 has a potential on the negative electrode side.
As a result, current flows from the load side lead 23 to the non-load side lead 24 in the phase conductor 17.

On the other hand, when the first positive electrode side switch 26 and the first negative electrode side switch 29 are turned off and the second negative electrode side switch 28 and the second positive electrode side switch 30 are turned on by driving of the control device, the load side The end of the lead 23 has a potential on the negative electrode side, and the end of the non-load side lead 24 has a potential on the positive electrode side. As a result, current flows from the non-load side lead 24 to the load side lead 23 in the phase conductor 17.
When all the four switches 26, 30, 29, 28 of the H bridge circuit are turned off, the phase conductor 17 is disconnected from the DC power supply 27 and no current flows.
As described above, the control device 300 changes the ratio of the on time and the off time of the on / off of the switches 26, 30, 29, and 28, and the on time and the off time, so that each phase conductor 17 has an arbitrary amplitude and The current of the phase can be conducted.

  In the drive system configured as described above, when the motor 1 is operated by the conventional control technique, the following problems occur. That is, when the motor 1 is driven, a magnetic flux in which the magnetic flux generated by the phase conductor 17 and the magnetic flux generated by the permanent magnet 21 are superimposed is generated in the teeth 14. Usually, the magnetic flux produced by the phase conductor 17 is substantially sinusoidal, and the magnetic flux produced by the permanent magnet in the teeth 14 is also substantially sinusoidal. However, the two superimposed magnetic flux waveforms become a waveform in which harmonics are superimposed due to the phase difference of the substantially sinusoidal magnetic flux, and the iron loss generated in the teeth 14 is increased by the harmonic components. Such problems particularly occur in the case of advancing the phase of the current supplied to the motor 1 in order to utilize reluctance torque, or for the purpose of reducing the induced voltage generated when the motor 1 is rotated at high speed. It will be noticeable when it happens.

In order to solve such a problem, the present invention employs a control device having the configuration described below.
FIG. 5 is a diagram showing a hardware configuration of a drive system for driving the control device according to the first embodiment.
In FIG. 5, this drive system 100 includes a motor 1, an inverter 200, a control device 300, and a host controller 400.
The control device 300 includes a processor 101 and a storage device 102 as hardware.
Although not illustrated, the storage device 102 includes volatile storage devices such as random access memory and non-volatile auxiliary storage devices such as flash memory. Further, although not shown, the storage device 102 may be provided with volatile storage devices such as random access memory and auxiliary storage devices such as hard disk instead of nonvolatile auxiliary storage devices.

The processor 101 executes a program input from the storage device 102. Since the storage device 102 includes an auxiliary storage device and a volatile storage device, a program is input to the processor 101 from the auxiliary storage device via the volatile storage device. Further, the processor 101 may output data such as an operation result to a volatile storage device of the storage device 102, or may store the data in the auxiliary storage device via the volatile storage device.
The input and output of data etc. between the components of the hardware of FIG. 5 will be described later.
FIG. 6 is a block diagram showing a control device according to the first embodiment of the present invention, and as shown in FIG. 6, control device 300 includes magnetic flux command unit 303, torque command unit 305, and motor 1 respectively. A detection unit 301 connected to both ends of the phase conductor 17 for detecting the electric potential between the both ends, a magnetic flux calculation for calculating a magnetic flux passing through each tooth 14 from the electric potential detected by the detection unit 301 and calculating a harmonic magnetic flux A magnetic flux comparison unit 304 that compares the output of the magnetic flux calculation unit 302 and the output of the magnetic flux command unit 303. Further, the current obtained by current monitoring unit 306 for detecting the current between motor 1 and inverter 200 is compared with the output value of torque command unit 305, and the signal input to the inverter by the output of magnetic flux comparison unit 304 And a control unit 307 that calculates and outputs.

The detection unit 301, the magnetic flux calculation unit 302, the magnetic flux command unit 303, the magnetic flux comparison unit 304, the torque command unit 305, the current monitor unit 306, and the control unit 307 in FIG. 6 execute the program stored in the storage device 102. Or a processing circuit such as a system LSI not shown. Further, the plurality of processors 101 and the plurality of storage devices 102 may cooperate with each other to execute the above function, or the plurality of processing circuits may cooperate with each other to execute the above function. In addition, the above functions may be performed in cooperation with each other by a combination of a plurality of processors 101 and a plurality of storage devices 102 and a plurality of processing circuits.
Note that each of the detection unit 301 and the current monitoring unit 306 may be processed by the hardware itself of the detection unit 301 and the current monitoring unit 306.
The host controller 400 outputs a torque command described later to the control device 300.

And each part of the control apparatus 300 is comprised so that a specific function may be shown as shown in FIG.
In other words, torque command unit 305 outputs d-axis current command value id1 * and q-axis current command value iq1 * of the fundamental wave that meet the torque command that is the desired torque input from host controller 400. Then, using the d-axis currents id1 and iq1 of the actual fundamental wave components detected by the current monitoring unit 306, the control unit 307 generates fundamental wave voltage command values vd1 * and vq1 * of the dq axes.

  On the other hand, the magnetic flux command unit 303 is a third, seventh, eleventh (3 + 4 Nth, N is a natural number: third-order system thereafter) harmonics with respect to the fundamental wave of the magnetic flux generated in each tooth 14 facing the magnet of one pole pair Dq axis flux command values λ d 3 *, λ q 3 * and fifth, ninth, 13 th (5 + 4 N order, N is a natural number: 5 th order system thereafter) harmonics reducing dq axis flux command values λ d 5 *, λ q 5 * Output The magnetic flux λ d 3, λ q 3 of the dq axis of the third harmonic with respect to the fundamental wave of the magnetic flux actually generated in each tooth 14 calculated by the magnetic flux computing unit 302 and the flux λ d 5, λ q 5 of the d q axis of the fifth harmonic. The controller 307 generates dq axis third-order and fifth-order harmonic voltage command values vd3 *, vq3 *, vd5 *, vq5 * in the control unit 307 using the

Then, the control unit 307 performs dq inverse conversion on the fundamental wave voltage command values vd1 *, vq1 *, and the third order and fifth order harmonic voltage command values vd3 *, vq3 *, vd5 *, vq5 *, and six-phase conversion. Generates a voltage command value v * of The PWM control of the inverter 200 is performed using this six-phase voltage command value v *.
The detection unit 301 calculates potential differences v between the load side lead 23 of the motor 1 and the non-load side lead 24 for each of six sets, and outputs the potential difference v to the magnetic flux operation unit 302.

The magnetic flux calculation unit 302 uses the six voltages v detected by the detection unit, the phase resistance R known in advance, and the current i flowing through each of the phase conductors 17a to 17f, and λ = ∫ (v−Ri) dT From the relationship, magnetic fluxes λA, λB, λC, λD, λE, λF, which are interlinked with the six phase conductors 17a to 17f, respectively, are calculated. Next, the magnetic flux λT of each of the six teeth 14 between the respective stator slots 16 is calculated from the difference between the magnetic fluxes linked to the phase conductors 17 a to 17 f inserted in the adjacent stator slots 16. The magnetic fluxes of the six teeth 14 are dq converted, and the dq axis magnetic flux λ d 3, λ q 3 of the third harmonic and the d q axis magnetic flux of the fifth harmonic with respect to the fundamental wave of the magnetic flux actually generated in each tooth 14 λd5 and λq5 are calculated, and the result is output to the magnetic flux comparison unit 304.
The magnetic pole position of the motor 1 used for dq conversion and dq reverse conversion is calculated using the output of a rotational position sensor (not shown) attached to the motor 1; A magnetic pole position estimated value using a waveform may be used.

In the drive system 100 configured as described above, since control is performed to suppress harmonics of the magnetic flux of each of the teeth 14, 3, 5, 7, ... next to the fundamental wave than the carrier frequency The core loss of higher harmonics can be reduced. Such an effect can not be obtained by the conventional phase-by-phase harmonic suppression control or multi-phase control.
Further, in the control device 300, since the magnetic flux of each of the teeth 14 of the motor 1 is feedback controlled, the change of the magnetic flux due to the change of the operating condition or the temperature change of the permanent magnet 21 or the temperature change of the phase conductor 17 Control can be performed with high precision in response to changes in resistance value and the like.

Further, since control device 300 has a torque command unit, and the magnetic flux command unit has a command for the harmonic magnetic flux, the iron loss generated in teeth 14 is reduced without a large change in the torque output by motor 1. be able to.
Further, the detection unit 301 detects a voltage using the phase conductor 17 of the motor 1, and the magnetic flux calculation unit 302 calculates the magnetic flux passing through each tooth 14 using the voltage detected by the detection unit 301. There is no need to add a new member such as a dedicated flux filter winding for monitoring the magnetic flux passing through 14 to the motor 1, and the motor can be miniaturized.

The motor 1 has six phases that can be controlled independently (because of the H-bridge configuration) to the stator slots 16 adjacent to these six teeth 14 with respect to six teeth 14 facing one pole pair Since the conductor 17 is provided, there is a degree of freedom to control the magnetic flux of all six teeth 14 arbitrarily, and iron loss of all teeth can be reduced. In addition, if control is established with respect to 1 pole pair as description, since the other teeth 14 are rotationally symmetric, flux harmonic suppression will be established in all the teeth 14.
If the detection unit 301 is provided with a low pass filter between the load side lead 23 and the non-load side lead 24 of the motor 1, the voltage resulting from the switching of the inverter 200 of the motor 1 driven by PWM control by this. You can eliminate the fluctuation.

  Although the harmonic flux command is set to 0 in the first embodiment, it may be other than 0. In this way, although the iron loss generated in each tooth 14 increases, the current ripple output from inverter 200 can be reduced, so that the torque ripple can be reduced and the loss generated in inverter 200 is reduced. Therefore, the total loss generated in the drive system 100 can be reduced.

In the first embodiment, it has been described that the phase conductor 17 of the motor 1 is formed by wave winding, but the present invention is not limited to wave winding. Also, although all the nodes are wound, the same effect can be obtained by winding in a short node.
Although the six inverter subunits 201 are connected to the individual DC power supplies 27 in the first embodiment, the same effects can be obtained even if they are connected in parallel to the same DC power supply 27.

Although the harmonics of the magnetic flux generated in all the teeth 14 are reduced using six phase conductors 17 in the first embodiment, the harmonics are generated in some teeth 14 using some phase conductors 17. The magnetic flux may be reduced. For example, three phase conductors 17 may be used to reduce harmonics to one out of six teeth 14. In this way, it is possible to halve the processing load of the control device 200 for suppressing the harmonic flux while obtaining half the iron loss reduction effect of the teeth 14.
In addition to the motors of the six phase conductors 17 in the present embodiment, there are S teeth wound around the stator iron core salient pole portion facing N teeth, M magnetic poles and one pole (S is There are L phase conductors that satisfy S / N / M, and L pieces that independently control L phase conductors (L is a natural number that satisfies S L L L N / M) of S phase conductors If there is an inverter subunit 201A (not shown), the iron loss of all the teeth can be reduced.

Embodiment 2
FIG. 8 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor 1A, for explaining the second embodiment of the H bridge configuration with 8 poles and 48 slots and 12 degrees of freedom.
The motor 1A is a 6-phase motor with 8 poles and 48 slots.
In FIG. 8, two phase conductors 17 are inserted in each stator slot 16, one on the radial outer diameter side of stator slot 16 and the other on the radial inner diameter side of stator slot 16. , And 12 phase conductors 17 in total.
In this case, the inverter 200 is configured of twelve inverter subunits 201 (not shown). Further, the control device 300 calculates the magnetic flux of the teeth 14 using six phase conductors 17 among the twelve phase conductors 17. Specifically, using the terminal voltages of the six phase conductors 17 detected by the detection unit 301, the magnetic flux calculation unit 302 calculates a magnetic flux.
At this time, the six phase conductors 17 used are not inserted into the same stator slot 16 respectively. The other structure is the same as that of the first embodiment.

Even in such a configuration, the same effect as that of the first embodiment can be obtained. Furthermore, since two phase conductors 17 are separately wound on the inner diameter side and the outer diameter side in one stator slot 16, the magnetic flux waveform of each tooth 14 is formed on the inner diameter side and the outer diameter side of the teeth 14. It can be divided and controlled. Such an effect is particularly effective in reducing the iron loss in the motor 1 in which the leakage flux in the middle of the teeth 14 is large.
Motor 1A is not limited to 8 poles and 48 slots, and inverter subunit 201 may have twice the number of phases in any number of poles and slots.

Third Embodiment
FIG. 9 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor 1B, for explaining the third embodiment of the 8-pole 12-slot 3-DOF H bridge configuration and concentrated winding.
The motor 1B is a three-phase motor having eight poles and twelve slots.
In FIG. 9, the motor 1B has 12 teeth 14, and 12 phase conductors are wound on concentrated windings in each of the teeth 14. Then, the 12 phase conductors 17 are skipped by two in the circumferential direction, that is, ones separated by two pole pitches are connected in series to constitute three phases.
In this case, the inverter 200 is composed of three inverter subunits 201, and is connected to both ends of the three-phase phase conductor 17 of the motor 1B. Further, the control device 300 calculates the magnetic flux of the teeth 14 using the three phase conductors 17. Specifically, using the terminal voltages of the three phase conductors 17 detected by the detection unit 301, the magnetic flux calculation unit 302 calculates a magnetic flux. The other structure is the same as that of the first embodiment.

Even in such a configuration, the same effect as that of the first embodiment can be obtained. Moreover, since it can implement | achieve with the structure of a concentrated winding, the height of a coil end can be reduced and the motor 1 can be miniaturized. Furthermore, the length of the phase conductor 17 can be shortened, and copper loss can also be reduced. Iron loss can be reduced even in a configuration in which harmonics of the magnetic flux generated by the armature winding is likely to be large compared to distributed winding, such as concentrated winding. Since only three targets need to be independently controlled, the number of parts can be reduced, and the effect of easy miniaturization can be obtained.
Although the phase conductors 17 are connected in series in the third embodiment, the load side leads 23 of the phase conductors 17 of the same phase and the anti-load side leads 24 may be connected and connected in parallel.
Motor 1B is not limited to 8 poles and 12 slots, but may be (3 ± 1) · K poles 3K slots (K is a natural number).

Fourth Embodiment
FIG. 10 is a cross-sectional view perpendicular to the rotation axis showing the structure of motor 1C, for explaining the fourth embodiment of the 10-pole 12-slot concentrated winding.
The motor 1C is a 10-pole 12-slot concentrated winding three-phase motor.
In FIG. 10, the motor 1C has twelve teeth 14, and twelve phase conductors 17 are wound around concentrated teeth in each of the teeth 14.
The two phase conductors 17 arranged at axially symmetrical positions are wound in reverse and connected in series, and both ends of the six phase conductors 17 are connected to the inverter subunit 201, respectively. The rotor 8 has a cylindrical rotor core 19 formed with a total of ten axially spaced magnet slots 20 at equal intervals in the circumferential direction, and N poles and S poles alternately in each magnet slot 20 on the outer diameter side And a permanent magnet 21 inserted to position the
In this case, the inverter 200 is configured of six inverter subunits 201.
Control device 300C calculates the magnetic flux of teeth 14 using six phase conductors 17. Specifically, using the terminal voltages of the six phase conductors 17 detected by the detection unit 301, the magnetic flux calculation unit 302 calculates a magnetic flux. The other structure is the same as that of the first embodiment.

Even in such a configuration, the same effects as in the first embodiment can be obtained. Moreover, since it can implement | achieve with the structure of a concentrated winding, the height of a coil end can be reduced and the motor 1 can be miniaturized. Furthermore, the length of the phase conductor 17 can be shortened, and copper loss can also be reduced. Even in a configuration such as concentrated winding in which harmonics of the magnetic flux generated by the armature winding tends to be large compared to distributed winding, the effect of reducing iron loss can be obtained. The iron loss can be similarly reduced even in the configuration in which the three phases of the armature are not completed within one pole pair.
The motor 1C is not limited to 10 poles and 12 slots, but may be 2 · (6 ± 1) · K poles 12K slots (K is a natural number).

Fifth Embodiment
In the fifth embodiment, as in the motor 1C shown in FIG. 10, in the case of using a 10-pole 12-slot concentrated winding three-phase motor, the inverter 200 is composed of 12 inverter subunits 201 and 12 The two ends of the 12 phase conductors 17 are connected to the inverter sub-unit 201 of FIG. In this case, in the control device 300, the individual magnetic fluxes of the twelve teeth 14 are respectively calculated using the twelve phase conductors 17. Specifically, using the terminal voltage of the 12 phase conductors 17 detected by the detection unit 301, the magnetic flux calculation unit 302 calculates a magnetic flux.
The other configuration is the same as that of the first embodiment.

With such a configuration, the magnetic flux of all the teeth 14 can be suppressed and controlled individually. For example, when the motor 1 is eccentric and the magnetic fluxes of the permanent magnets 21 are different from one another, or when the permanent magnets 21 are misaligned respectively, the magnetic flux change of the teeth 14 also occurs at rotationally symmetric positions. Will be different. Even in such a case, since all the teeth 14 can be individually controlled as in the fifth embodiment, iron loss in the teeth 14 can be reduced.
Motor 1C is not limited to 10 poles and 12 slots, but may be (6 ± 1) · 2K poles 12K slots (K is a natural number).

  In the present invention, within the scope of the invention, each embodiment can be freely combined, and each embodiment can be appropriately modified or omitted.

1 motor, 14 teeth, 17 phase conductors, 100 drive system,
101 processor, 102 storage device, 200 inverter, 300 controller,
301 detection unit, 302 magnetic flux operation unit, 303 magnetic flux command unit, 304 next phase comparison unit,
305 torque command unit, 306 current monitor unit, 307 control unit

Claims (13)

A magnetic flux calculating unit for calculating a magnetic flux passing through a stator core salient pole portion projecting at equal intervals in a radial direction from an annular yoke in a rotating electric machine, and a phase conductor wound around the stator core salient pole portion A magnetic flux command unit that generates a magnetic flux command value that reduces harmonics of the magnetic flux containing the magnetic flux generated by the magnetic flux to the fundamental wave, and a control unit that controls a voltage supplied to the rotating electrical machine based on the magnetic flux and the magnetic flux command value And a control device.   The control device according to claim 1, wherein the magnetic flux calculation unit calculates the magnetic flux passing through each of the plurality of stator core salient pole portions.   The magnetic flux comparison part which compares the said magnetic flux and the said magnetic flux command value is further provided, and the said control part controls the voltage supplied to the said rotary electric machine based on the comparison result of the said magnetic flux comparison part. Control device. And a torque command unit for outputting a fundamental wave current command value which is a command value of a fundamental wave of current,
The magnetic flux calculating unit calculates a harmonic magnetic flux which is a harmonic of the magnetic flux, the magnetic flux comparing unit compares the harmonic magnetic flux and the magnetic flux command value, and the control unit compares the magnetic flux comparing unit The control device according to claim 3, wherein a voltage supplied to the rotating electrical machine is controlled based on the result and the fundamental wave current command value.   And a detection unit for detecting the terminal voltage of each of the phase conductors wound around the stator core salient pole portion of the rotary electric machine, the magnetic flux calculation unit calculating the magnetic flux using the terminal voltage The control apparatus of any one of Claim 3 or Claim 4.   N phases of the stator core salient pole portion, M magnetic poles, and S phases (S is a natural number satisfying S ≧ N / M) wound on the stator core salient pole portion facing the one pole The control device according to any one of claims 1 to 5, wherein the control device according to any one of claims 1 to 5 includes L pieces of L pieces (L is a natural number satisfying S.gtoreq.L.gtoreq.N / M) of the S phase conductors. A rotating electrical machine in which the amplitude and phase of the current supplied to the phase conductors are independently controlled. The phase conductors are inserted two by two in each of the stator slots formed between the stator core salient pole portions, and one of the phase conductors is disposed on the radial outer diameter side of the stator slot, The other phase conductor is disposed on the radially inner side of the stator slot,
The rotating electrical machine according to claim 6, wherein the magnetic flux calculating unit calculates the magnetic flux using half of the phase conductors among the phase conductors.   The rotating electrical machine according to claim 6, wherein the number of the phase conductors is the same as the number of the stator core salient pole portions, and the magnetic flux computing unit computes the magnetic flux using all the phase conductors. N = 3K (K is a natural number),
M = (3 ± 1) · K,
The rotating electrical machine according to claim 6, wherein S = L = 3. N = 12 K (K is a natural number),
M = 2 · (6 ± 1) · K,
The rotating electrical machine according to claim 6, wherein S = L = 6.   A control device according to any one of claims 1 to 5, a power converter controlled by said control device for mutually converting DC power and AC power, and an AC side terminal of said power converter Drive system comprising the above-described electric rotating machine.   The rotating electric machine includes S pieces wound around the N stator core salient pole portions, the M magnetic poles, and the stator core salient pole portions facing one pole (S: S ≧ N / M Amplitudes and phases of currents applied to L phase conductors (L is a natural number satisfying SLL ≧ N / M) of the S phase conductors by the control device. The drive system according to claim 11, wherein each is independently controlled.   The power converter is a switch for turning on and off current between one end of the phase conductor and each of the positive electrode terminal and the negative electrode terminal of the DC power supply for each of the L phase conductors of the rotating electrical machine. The drive according to claim 12, further comprising: a first switch group having a second switch group having the switch between the other end of the phase conductor and each of the positive electrode terminal and the negative electrode terminal of the DC power supply. system.