JP2016158313A - Control apparatus, rotary electric machine using same, and drive system comprising control apparatus and rotary electric machine - Google Patents

Abstract

PROBLEM TO BE SOLVED: To solve the following problem: a rotary electric machine is enlarged because dedicated windings for a magnetic flux filter is required when iron loss is suppressed by a harmonic magnetic flux passing through a stator core salient-pole part of the rotary electric machine.SOLUTION: A control apparatus includes: a magnetic flux operation part that calculates a magnetic flux passing through a stator core salient-pole part protruded at regular intervals in a radial direction from a toric yoke of a rotary electric machine; a magnetic flux command part that generates a magnetic flux command value for reducing higher harmonics with respect to a fundamental wave of the magnetic flux; and a control part that controls a voltage supplied to the rotary electric machine on the basis of the magnetic flux and the magnetic flux command value.SELECTED DRAWING: Figure 6

Description

  The present invention relates to a control device for a rotating electrical machine, a rotating electrical machine using the same, and a drive system including the control device and the rotating electrical machine.

Conventionally, electric energy is lost in the magnetization of a magnetic material constituting the stator or the rotor when the rotary electric machine is rotationally driven. Various efforts have been made to reduce this loss.
In particular, in order to reduce the iron loss due to the harmonic component of the magnetic flux passing through the magnetic material, a magnetic flux filter circuit having a magnetic flux filter winding is provided in the stator core of the rotating electrical machine, and the harmonic component of the magnetic flux having a predetermined frequency or higher is provided. It has been proposed to attenuate. (For example, see Patent Document 1)

JP 2008-301551A

In the technique proposed in Patent Document 1, it is possible to attenuate time harmonics that are separated from the fundamental frequency of the rotating electrical machine, such as harmonics resulting from switching of the inverter-driven rotating electrical machine, In addition to the armature winding of the rotating electrical machine, a dedicated magnetic flux filter winding is required, which increases the size of the rotating electrical machine.
An object of the present invention is to provide a control device capable of reducing the size of a rotating electric machine while reducing iron loss in response to distortion of the magnetic flux waveform caused by the fundamental wave and the harmonic magnetic flux.

  A control device according to the present invention includes a magnetic flux calculation unit that calculates a magnetic flux that passes through a stator core salient pole portion that is projected from a ring-shaped yoke of a rotating electrical machine at equal intervals in a radial direction, and a harmonic with respect to a fundamental wave of the magnetic flux. And a magnetic flux command unit that generates a magnetic flux command value for reducing waves, and controls a voltage supplied to the rotating electrical machine based on the magnetic flux and the magnetic flux command value.

  The control device configured as described above controls the voltage supplied to the rotating electrical machine based on the magnetic flux and the magnetic flux command value, thereby eliminating the need for a dedicated magnetic flux filter winding. It is possible to reduce the size of the rotating electric machine while reducing the iron loss corresponding to the distortion of the waveform.

FIG. 2 is a schematic diagram showing a drive system in the first embodiment. FIG. 3 is a cross-sectional view along the rotation axis showing the structure of the motor in the first embodiment. FIG. 3 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor in the first embodiment. 1 is a circuit diagram showing an inverter according to a first embodiment. 2 is a diagram showing a hardware configuration of a drive system in Embodiment 1. FIG. 2 is a block diagram showing a configuration of a control device in Embodiment 1. FIG. FIG. 3 is a block diagram illustrating an operation of the control device according to the first embodiment. FIG. 6 is a cross-sectional view perpendicular to a rotation axis showing the structure of a motor according to Embodiment 2. FIG. 5 is a cross-sectional view perpendicular to a rotation axis showing the structure of a motor according to Embodiment 3. FIG. 6 is a cross-sectional view perpendicular to a rotation axis showing the structure of a motor according to a fourth embodiment.

Embodiment 1
FIG. 1 is a schematic diagram showing a drive system 100 including a rotating electrical machine having an 8-pole 48-slot, 6-degree-of-freedom H-bridge configuration, which is a target of the first embodiment of the present invention. FIG. 2 is a cross-sectional view along the rotation axis for showing the structure of the motor 1 in FIG. FIG. 3 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor 1 in FIG. FIG. 4 is a circuit diagram showing inverter 200 in FIG. FIG. 5 is a block diagram showing the control device 300 in FIG. FIG. 6 is a block diagram showing the operation of each block of the control device 300 in FIG. 1, that is, the control device 300 shown in FIG.

As shown in FIG. 1, a drive system 100 that is an object of the present invention is a device for driving a load 50 by the power of a power supply 27. The drive system 100 detects an inverter 200 that is a power converter that mutually converts DC power and AC power, a motor 1 that is a rotating electrical machine connected to an AC terminal of the inverter 200, and a state of the motor 1. And a control device 300 that performs a calculation based on the detected information, inputs a control signal to the inverter 200, and controls the state of the motor 1, and a DC side terminal of the inverter 200 is connected to an external DC power supply 27. In addition, the motor 1 is connected to an external load 50 and transmits a rotational motion to the load 50.
The motor 1 used here is an 8-pole, 48-slot permanent magnet motor.

The structure of the motor 1 will be described with reference to FIG. A motor 1 that is a rotating electrical machine is arranged on a cylindrical frame 2, a load-side bracket 3 and an anti-load-side bracket 4 provided on both sides of the frame 2, and a center axis of the frame 2. A shaft 7 that is rotatably supported by a bracket 3 and an anti-load side bracket 4 via a load-side bearing 5 and an anti-load side bearing 6, and the shaft 7 is inserted and integrated with a key or the like. A rotor 8 housed in a case 10 composed of a side bracket 3 and an anti-load side bracket 4, and an annular shape fixed to the inner wall surface of the frame 2 by press-fitting, shrinkage or the like and surrounded by a gap with the rotor 8 And a stator 9.
The load-side bearing 5 of the motor 1 is fixed to the load-side bracket 3 with a bearing retainer 11 in the axial direction with a bolt or the like. The anti-load side bearing 6 is fixed to the anti-load side bracket 4 via the wave washer 12 with a degree of freedom in the axial direction.
The case 10 is formed by fixing the load side bracket 3 and the anti-load side bracket 4 to the frame 2 with bolts or the like.

As shown in FIG. 3, the stator 9 includes a stator core 15 having 48 stator core salient pole portions protruding at equal intervals from the inner peripheral side of the annular yoke 13 radially inward, and the teeth. 14, phase conductors 17a to 17f inserted in the status lots 16 extending in the axial direction and formed between the phase conductors 17 and an insulator 18 covering the phase conductors 17a to 17f.
The stator core 15 is formed by laminating a plurality of thin steel plates such as electromagnetic steel plates whose surfaces are insulated.
The phase conductors 17 a to 17 f are integrally molded with an insulator 18, and the phase conductors 17 a to 17 f covered with the insulator 18 are fixed to the stator core 15 by being press-fitted into the status lots 16.
The rotor 8 includes a cylindrical rotor core 19 having magnet slots 20 formed in a total of eight equally spaced circumferentially and extending in the axial direction, and N poles and S poles in each magnet slot 20 alternately on the outer diameter side. The permanent magnet 21 is inserted so as to be positioned at both ends of the magnet slot 20 and the end plate 22 is fixed to both ends of the rotor core 19 in the axial direction and closes both sides of the magnet slot 20. The end plate 22 is preferably made of a nonmagnetic material.

The phase conductors 17a to 17f are inserted into the status lot 16 from one end in the axial direction of the stator core 15 and exposed at the other end, and then the other one of the sixth status lots 16 in the circumferential direction is continued. After being inserted into the status lot 16 from one end and exposed at one end, the status lot 16 is inserted again from one end of the status lot 16 having a one-pole pitch in the circumferential direction and exposed at the other end.
Each of the phase conductors 17 a to 17 f is configured by wave windings in which the insertion of each status lot 16 is repeated three times in the circumferential direction of the stata core 15.
In FIG. 3, the phase conductors 17 a to 17 f are inserted into the status lot 16 as a set of phase conductors that are electrically connected to form one phase. A total of six phase conductors 17a to 17f having a six-phase wave winding configuration are wound around the stator core 15.
In addition, in FIG. 3, the phase conductors 17a to 17f should actually be divided into three sections in the radial direction, but are shown as one.

Each phase conductor 17a-17f is connected to one end of each of the load side lead 23 and the anti-load side lead 24 at both ends thereof. The load-side leads 23 and the anti-load-side leads 24 are drawn out of the motor 1 through drawer ports 25 formed in the frame 2.
FIG. 4 is a circuit diagram showing the inverter 200. The inverter 200 is composed of six inverter subunits 201.

The load-side lead 23 of the inverter subunit 201 is electrically connected to the positive terminal 31 of the DC power supply 27 via the first positive-side switch 26 that turns on and off the current, and controls the current on and off. It is electrically connected to the negative terminal 32 of the DC power supply 27 via a second negative switch 28 that is a load side control component.
The anti-load side lead 24 is electrically connected to the negative terminal 32 of the DC power supply 27 via a first negative side switch 29 that turns on and off the current, and also has a positive side control that controls the current on and off. It is electrically connected to the positive terminal 31 of the DC power supply 27 via the second positive switch 30 that is a component.

Thus, the inverter subunit 201 forms a so-called H-bridge circuit by the first positive switch 26, the second negative switch 28, the first negative switch 29, and the second positive switch 30. ing.
The first positive switch 26, the second positive switch 30, the first negative switch 29, and the second negative switch 28 are constituted by insulated gate bipolar transistors (IGBT) using a silicon semiconductor. A field effect transistor (MOS-FET) may be used.
Alternatively, a semiconductor switch using a wide band gap semiconductor such as silicon carbide (SiC) or gallium nitride (GaN) may be used.
Although not shown, the first positive switch 26, the second positive switch 30, the first negative switch 29, and the second negative switch 28 are the switches 26, 30, 29, and 28, respectively. A free-wheeling diode is inserted in parallel.
The DC power supply 27 is composed of a lead battery, a lithium ion battery, or the like.

Each individual phase conductor 17 is electrically connected to an individual H bridge circuit, and a DC power source 27 is individually provided for each H bridge circuit.
That is, each of the inverter subunits 201 that are a part of the power converter is connected to one end of the phase conductor 17 that is the load-side lead 23 and the DC power supply 27 with respect to each of the phase conductors 17 of the motor 1 that is a rotating electrical machine. The first positive electrode side switch 26 is formed between the positive electrode terminal 31 and the second negative electrode side switch 28 between one end of the phase conductor 17 which is the load side lead 23 and the negative electrode terminal 32 of the DC power source 27. Between the other end of the phase conductor 17 that is the first switch group and the anti-load side lead 24 and the positive terminal 31 of the DC power supply 27, the second positive side switch 30 and the phase conductor that is the anti-load side lead 24 A second switch group including a first negative electrode side switch 29 is provided between the other end of 17 and the negative electrode terminal 32 of the DC power supply 27.
In FIG. 1, when the first positive electrode side switch 26 and the first negative electrode side switch 29 are turned on and the second negative electrode side switch 28 and the second positive electrode side switch 30 are turned off by driving the control device, The end of the load side lead 23 has a positive side potential, and the end of the anti-load side lead 24 has a negative side potential.
As a result, a current flows through the phase conductor 17 from the load side lead 23 toward the anti-load side lead 24.

On the other hand, when the first positive electrode side switch 26 and the first negative electrode side switch 29 are turned off and the second negative electrode side switch 28 and the second positive electrode side switch 30 are turned on by driving the control device, the load side The end of the lead 23 has a negative potential, and the end of the anti-load side lead 24 has a positive potential. As a result, a current flows through the phase conductor 17 from the anti-load side lead 24 toward the load side lead 23.
When all the four switches 26, 30, 29, and 28 of the H bridge circuit are turned off, the phase conductor 17 is disconnected from the DC power source 27 and no current flows.
As described above, the control device 300 switches the on / off of each switch 26, 30, 29, 28, and changes the ratio of the on time and the off time, thereby allowing each phase conductor 17 to have an arbitrary amplitude. A phase current can be applied.

  In the drive system configured as described above, when the motor 1 is operated with the conventional control technique, the following problems occur. That is, when the motor 1 is driven, a magnetic flux generated by superimposing the magnetic flux generated by the phase conductor 17 and the magnetic flux generated by the permanent magnet 21 is generated on the teeth 14. Normally, the magnetic flux generated by the phase conductor 17 is substantially sinusoidal, and the magnetic flux generated by the permanent magnet on the teeth 14 is also substantially sinusoidal. However, the superimposed magnetic flux waveform is a waveform in which harmonics are superimposed due to the phase difference of the substantially sinusoidal magnetic flux, and the iron loss generated in the teeth 14 is increased by this harmonic component. Such a problem is caused by a weak magnetic flux control especially for the purpose of reducing the induced voltage generated when the current phase applied to the motor 1 is advanced in order to utilize the reluctance torque or when the motor 1 is rotated at a high speed. It will occur remarkably when doing so.

In order to solve such a problem, the present invention employs a control device having the configuration described below.
FIG. 5 is a diagram illustrating a hardware configuration of a drive system that drives the control device according to the first embodiment.
In FIG. 5, the drive system 100 includes a motor 1, an inverter 200, a control device 300, and a host controller 400.
The control device 300 includes a processor 101 and a storage device 102 as hardware.
Although not shown, the storage device 102 includes a volatile storage device such as a random access memory, and a nonvolatile auxiliary storage device such as a flash memory. Although not shown, the storage device 102 may include a volatile storage device such as a random access memory and an auxiliary storage device such as a hard disk instead of the nonvolatile auxiliary storage device.

The processor 101 executes a program input from the storage device 102. Since the storage device 102 includes an auxiliary storage device and a volatile storage device, a program is input to the processor 101 from the auxiliary storage device via the volatile storage device. Further, the processor 101 may output data such as a calculation result to the volatile storage device of the storage device 102, or may store the data in the auxiliary storage device via the volatile storage device.
Input / output of data and the like between the hardware components in FIG. 5 will be described later.
FIG. 6 is a block diagram showing a control device according to Embodiment 1 of the present invention. As shown in FIG. 6, the control device 300 includes a magnetic flux command unit 303, a torque command unit 305, and a motor 1 respectively. A detecting unit 301 connected to both ends of the phase conductor 17 and detecting a potential between the both ends, a magnetic flux that calculates a magnetic flux passing through each tooth 14 from a potential detected by the detecting unit 301, and calculates a harmonic magnetic flux. 302 and a magnetic flux comparison unit 304 that compares the output of the magnetic flux calculation unit 302 with the output of the magnetic flux command unit 303. Further, a signal obtained by comparing the current obtained by the current monitoring unit 306 that detects the current between the motor 1 and the inverter 200 with the output value of the torque command unit 305 and a signal input to the inverter by the output of the magnetic flux comparison unit 304 It has the control part 307 which calculates and outputs.

The detection unit 301, the magnetic flux calculation unit 302, the magnetic flux command unit 303, the magnetic flux comparison unit 304, the torque command unit 305, the current monitor unit 306, and the control unit 307 in FIG. 6 are a processor 101 that executes a program stored in the storage device 102. Or a processing circuit such as a system LSI (not shown). In addition, a plurality of processors 101 and a plurality of storage devices 102 may execute the function in cooperation, or a plurality of processing circuits may execute the function in cooperation. Further, the above functions may be executed in cooperation with a combination of a plurality of processors 101 and a plurality of storage devices 102 and a plurality of processing circuits.
Note that each of the detection unit 301 and the current monitoring unit 306 may be processed by the hardware of the detection unit 301 and the current monitoring unit 306.
The host controller 400 outputs a torque command to be described later to the control device 300.

And each part of the control apparatus 300 is comprised so that a specific function may be fulfilled, as shown in FIG.
That is, the torque command unit 305 outputs a fundamental wave d-axis current command value id1 * and q-axis current command value iq1 * corresponding to a torque command that is a desired torque input from the host controller 400. Then, the dq-axis fundamental wave voltage command values vd1 * and vq1 * are generated by the control unit 307 using the d-axis currents id1 and iq1 of the actual fundamental wave components detected by the current monitor unit 306.

  On the other hand, the magnetic flux command unit 303 is a third-order, seventh-order, and eleventh-order (3 + 4N-th order, N is a natural number: hereafter a third-order system) harmonic with respect to the fundamental wave of the magnetic flux generated in each tooth 14 facing one pole pair magnet. Dq-axis magnetic flux command values λd3 *, λq3 * and fifth-order, ninth-order, and thirteenth-order (5 + 4N-th order, N is a natural number: the fifth-order system thereafter) dq-axis magnetic flux command values λd5 *, λq5 * Is output. Then, the dq-axis magnetic fluxes λd3 and λq3 of the third-order harmonics and the dq-axis magnetic fluxes λd5 and λq5 of the fifth-order harmonics with respect to the fundamental wave of the magnetic flux generated in each actual tooth 14 calculated by the magnetic flux calculation unit 302 Then, the control unit 307 generates the dq-axis third-order and fifth-order harmonic voltage command values vd3 *, vq3 *, vd5 *, and vq5 *.

Then, the control unit 307 dq-inverts the fundamental wave voltage command values vd1 *, vq1 * and the third and fifth harmonic voltage command values vd3 *, vq3 *, vd5 *, vq5 *, and performs six-phase conversion. The voltage command value v * is generated. PWM control of the inverter 200 is performed using the six-phase voltage command value v *.
The detection unit 301 calculates the potential difference v between the load-side lead 23 and the anti-load-side lead 24 of the motor 1 for each of the six sets, and outputs it to the magnetic flux calculation unit 302.

The magnetic flux calculation unit 302 uses the six voltages v detected by the detection unit, the phase resistance R that is known in advance, and the current i that flows through each of the phase conductors 17a to 17f to satisfy λ = ∫ (v−Ri) dT. From the relationship, magnetic fluxes λA, λB, λC, λD, λE, and λF interlinked with each of the six phase conductors 17a to 17f are respectively calculated. Next, the magnetic flux λT of each of the six teeth 14 between the status lots 16 is calculated from the difference in magnetic flux interlinking with the phase conductors 17 a to 17 f inserted in the adjacent status lots 16. The magnetic fluxes of the six teeth 14 are subjected to dq conversion, and the dq-axis magnetic fluxes λd3 and λq3 of the third-order harmonics and the dq-axis magnetic fluxes of the fifth-order harmonics with respect to the fundamental wave of the magnetic flux generated in each actual tooth 14 λd5 and λq5 are calculated and the result is output to the magnetic flux comparison unit 304.
In addition, although the magnetic pole position of the motor 1 used for dq conversion and dq reverse conversion is calculated using the output of the rotational position sensor (not shown) attached to the motor 1, superimposition of harmonic magnetic flux or induced voltage. A magnetic pole position estimated value using a waveform may be used.

In the drive system 100 configured as described above, control is performed so as to suppress the harmonics of the magnetic flux of each tooth 14, and therefore, 3, 5, 7,... The iron loss of higher harmonics can be reduced. Such an effect cannot be obtained by conventional harmonic suppression control and multiphase control for each phase.
Further, in the control device 300, since the magnetic flux of each tooth 14 of the motor 1 is feedback controlled, the magnetic flux changes due to a change in the operating state, the temperature change of the permanent magnet 21, the temperature change of the phase conductor 17, etc. It can be controlled with high accuracy in response to changes in the resistance value.

Moreover, since the control apparatus 300 has a torque command part and a magnetic flux command part has the command with respect to a harmonic magnetic flux, the iron loss which generate | occur | produces in the teeth 14 is reduced, without the torque which the motor 1 outputs changing largely. be able to.
Further, the detection unit 301 detects the voltage using the phase conductor 17 of the motor 1, and the magnetic flux calculation unit 302 calculates the magnetic flux passing through each tooth 14 using the voltage detected by the detection unit 301. Therefore, it is not necessary to add a new member such as a dedicated magnetic flux filter winding for monitoring the magnetic flux passing through the motor 1 to the motor 1, and the size can be reduced.

The motor 1 has six teeth 14 that are opposed to one pole pair, and each phase lot 16 adjacent to the six teeth 14 can be controlled independently (because of an H-bridge configuration). Since the conductor 17 is provided, there is a degree of freedom to arbitrarily control the magnetic fluxes of all the six teeth 14, and the iron loss of all the teeth can be reduced. If the control is established for one pole pair as described, the other teeth 14 are rotationally symmetric, and hence the magnetic flux harmonic suppression is established in all the teeth 14.
If the detection unit 301 is provided with a low-pass filter between the load-side lead 23 and the anti-load-side lead 24 of the motor 1, the voltage caused by the switching of the inverter 200 of the motor 1 driven by PWM control thereby. Variations can be eliminated.

  In the first embodiment, the harmonic magnetic flux command is set to 0, but may be other than 0. In this way, the iron loss generated in each tooth 14 increases. However, since the current ripple output from the inverter 200 can be reduced, the torque ripple can be reduced and the loss generated in the inverter 200 can be reduced. Therefore, the total loss generated in the drive system 100 can be reduced.

In the first embodiment, it has been described that the phase conductor 17 of the motor 1 is configured by wave winding, but is not limited to wave winding. Moreover, although it winds to all the nodes, there exists the same effect, even if it winds to a short node.
In the first embodiment, each of the six inverter subunits 201 is connected to the individual DC power supply 27, but the same effect can be obtained even if they are connected in parallel to the same DC power supply 27.

In the first embodiment, the harmonics of the magnetic flux generated in all the teeth 14 are reduced using the six phase conductors 17, but are generated in some of the teeth 14 using some of the phase conductors 17. The magnetic flux may be reduced. For example, three phase conductors 17 may be used so as to reduce harmonics by skipping one of the six teeth 14. If it does in this way, the processing load concerning the harmonic magnetic flux suppression of the control apparatus 200 can be halved, obtaining the iron loss reduction effect of the teeth 14 in half.
In addition, not only the motors of the six phase conductors 17 in the present embodiment, but S teeth wound around the stator core salient poles facing N teeth, M poles, and one pole (S is L having a number of phase conductors (natural number satisfying S ≧ N / M) and independently controlling L of the S phase conductors (L is a natural number satisfying S ≧ L ≧ N / M). If there is an inverter subunit 201A (not shown), the iron loss of all teeth can be reduced.

Embodiment 2
FIG. 8 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor 1A for explaining the second embodiment of the 8-pole 48-slot 12-degree-of-freedom H-bridge configuration.
The motor 1A is an 8-pole 48-slot 6-phase motor.
In FIG. 8, two phase conductors 17 are inserted in each status lot 16, and one is arranged on the radially outer diameter side of the status lot 16 and the other is placed on the radially inner diameter side of the status lot 16. , A total of twelve phase conductors 17 are provided.
In this case, the inverter 200 is composed of 12 inverter subunits 201 (not shown). Further, the control device 300 calculates the magnetic flux of the teeth 14 using the six phase conductors 17 out of the twelve phase conductors 17. Specifically, the magnetic flux calculation unit 302 calculates the magnetic flux using the terminal voltages of the six phase conductors 17 detected by the detection unit 301.
At this time, the six phase conductors 17 that are not inserted in the same status lot 16 are used. Other structures are the same as those in the first embodiment.

Even in such a configuration, the same effect as in the first embodiment can be obtained. Further, since two phase conductors 17 are wound separately on the inner diameter side and the outer diameter side in one status lot 16, the magnetic flux waveform of each tooth 14 is applied to the inner diameter side and the outer diameter side of the tooth 14. It can be controlled separately. Such an effect is particularly effective in reducing the iron loss in the motor 1 having a large leakage magnetic flux in the middle of the teeth 14.
The motor 1A is not limited to 8 poles and 48 slots, and the inverter subunit 201 only needs to be twice the number of phases in any number of poles and slots.

Embodiment 3
FIG. 9 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor 1B for explaining the third embodiment of the 8-pole 12-slot 3-DOF H-bridge configuration and concentrated winding.
The motor 1B is an 8-pole 12-slot three-phase motor.
In FIG. 9, the motor 1 </ b> B has twelve teeth 14, and twelve phase conductors are wound around each tooth 14 in concentrated winding. Then, twelve phase conductors 17 are skipped in the circumferential direction, that is, two phase conductors 17 apart from each other are connected in series to form three phases.
In this case, the inverter 200 includes three inverter subunits 201 and is connected to both ends of the three-phase phase conductor 17 of the motor 1B. The control device 300 calculates the magnetic flux of the teeth 14 using the three phase conductors 17. Specifically, the magnetic flux calculation unit 302 calculates the magnetic flux using the terminal voltages of the three phase conductors 17 detected by the detection unit 301. Other structures are the same as those in the first embodiment.

Even in such a configuration, the same effect as in the first embodiment can be obtained. Moreover, since it can implement | achieve with the structure of concentrated winding, the height of a coil end can be reduced and the motor 1 can be reduced in size. Furthermore, the length of the phase conductor 17 can be shortened, and copper loss can also be reduced. Iron loss can be reduced even in a configuration where the harmonics of the magnetic flux generated by the armature winding are likely to be larger than the distributed winding, such as concentrated winding. Since only three objects need to be independently controlled, the number of parts can be reduced and the effect of being easily miniaturized can be obtained.
In the third embodiment, the phase conductors 17 are connected in series. However, the load-side leads 23 and the anti-load-side leads 24 of the phase conductors 17 of the same phase may be connected in parallel.
The motor 1B is not limited to 8 poles and 12 slots, but may be (3 ± 1) · K poles and 3K slots (K is a natural number).

Embodiment 4
FIG. 10 is a cross-sectional view perpendicular to the rotation axis showing the structure of the motor 1C for explaining the fourth embodiment of the 10 pole 12 slot concentrated winding.
The motor 1C is a 10-pole 12-slot concentrated winding three-phase motor.
In FIG. 10, the motor 1 </ b> C has twelve teeth 14, and twelve phase conductors 17 are wound around each tooth 14 in concentrated winding.
The two phase conductors 17 arranged at the axially symmetric positions are wound in opposite directions and connected in series, and both ends of the six phase conductors 17 are connected to the inverter subunit 201, respectively. The rotor 8 includes a columnar rotor core 19 having magnet slots 20 formed in total at equal intervals in the circumferential direction and extending in the axial direction, and N poles and S poles in each magnet slot 20 alternately on the outer diameter side. The permanent magnet 21 is inserted so as to be positioned.
In this case, the inverter 200 is composed of six inverter subunits 201.
Control device 300 </ b> C calculates the magnetic flux of teeth 14 using six phase conductors 17. Specifically, the magnetic flux calculation unit 302 calculates the magnetic flux using the terminal voltages of the six phase conductors 17 detected by the detection unit 301. Other structures are the same as those in the first embodiment.

Even in such a configuration, the same effects as those of the first embodiment can be obtained. Moreover, since it can implement | achieve with the structure of concentrated winding, the height of a coil end can be reduced and the motor 1 can be reduced in size. Furthermore, the length of the phase conductor 17 can be shortened, and copper loss can also be reduced. Even in a configuration where the harmonics of the magnetic flux generated by the armature winding is likely to be larger than that of the distributed winding, such as concentrated winding, an effect of reducing iron loss can be obtained. Even in a configuration in which the three phases of the armature are not completed within one pole pair, the iron loss can be similarly reduced.
The motor 1C is not limited to 10 poles and 12 slots, and may be 2 · (6 ± 1) · K poles and 12K slots (K is a natural number).

Embodiment 5
In the fifth embodiment, similarly to the motor 1C shown in FIG. 10, a concentrated winding three-phase motor having 10 poles and 12 slots is used, and the inverter 200 is composed of twelve inverter subunits 201. Both end portions of 12 phase conductors 17 are connected to each inverter subunit 201. In this case, the control device 300 calculates the individual magnetic fluxes of the 12 teeth 14 using the 12 phase conductors 17, respectively. Specifically, the magnetic flux calculation unit 302 calculates the magnetic flux using the terminal voltages of the twelve phase conductors 17 detected by the detection unit 301.
Other configurations are the same as those of the first embodiment.

With such a configuration, the magnetic fluxes of all the teeth 14 can be individually suppressed and controlled. For example, when the motor 1 is eccentric and the magnetic fluxes of the permanent magnets 21 are different from each other, or when the permanent magnets 21 are displaced from each other, the change in the magnetic flux of the teeth 14 even at rotationally symmetric positions. Will be different. Even in such a case, since all the teeth 14 can be individually controlled as in the fifth embodiment, the iron loss in the teeth 14 can be reduced.
The motor 1C is not limited to 10 poles and 12 slots, but may be (6 ± 1) · 2K poles and 12K slots (K is a natural number).

  It should be noted that the present invention can be freely combined with each other within the scope of the invention, and each embodiment can be appropriately modified or omitted.

1 motor, 14 teeth, 17 phase conductor, 100 drive system,
101 processor, 102 storage device, 200 inverter, 300 control device,
301 detection unit, 302 magnetic flux calculation unit, 303 magnetic flux command unit, 304 secondary phase comparison unit,
305 Torque command unit, 306 Current monitor unit, 307 Control unit

Claims (13)

A magnetic flux calculation unit for calculating a magnetic flux passing through a stator core salient pole portion protruding at equal intervals in a radial direction from an annular yoke in the rotating electrical machine;
A magnetic flux command unit that generates a magnetic flux command value for reducing harmonics of the fundamental wave of the magnetic flux;
And a control unit that controls a voltage supplied to the rotating electrical machine based on the magnetic flux and the magnetic flux command value.   The control device according to claim 1, wherein the magnetic flux calculation unit calculates the magnetic flux that passes through each of the plurality of stator core salient pole portions. A magnetic flux comparison unit for comparing the magnetic flux and the magnetic flux command value;
The control device according to claim 2, wherein the control unit controls a voltage supplied to the rotating electrical machine based on a comparison result of the magnetic flux comparison unit. A torque command unit that outputs a fundamental current command value that is a fundamental wave command value;
The magnetic flux calculation unit calculates a harmonic magnetic flux that is a harmonic of the magnetic flux,
The magnetic flux comparison unit compares the harmonic magnetic flux and the magnetic flux command value,
The control device according to claim 3, wherein the control unit controls a voltage supplied to the rotating electrical machine based on a comparison result of the magnetic flux comparison unit and the fundamental wave current command value. A detector that detects each terminal voltage of the phase conductor wound around the stator core salient pole of the rotating electrical machine;
The control device according to claim 3 or 4, wherein the magnetic flux calculation unit calculates the magnetic flux using the terminal voltage. N stator core salient poles, M magnetic poles, and S (S is a natural number satisfying S ≧ N / M) phases wound around the stator core salient poles facing one pole Has a conductor,
The control device according to any one of claims 1 to 5, wherein L of the S phase conductors (L is a natural number satisfying S ≧ L ≧ N / M) is energized. A rotating electrical machine in which the current amplitude and phase are independently controlled. Two phase conductors are inserted into each of the status lots formed between the stator core salient poles,
One of the phase conductors is arranged on the outer diameter side in the radial direction of the status lot,
The other phase conductor is disposed on the inner diameter side in the radial direction of the status lot,
The rotating electrical machine according to claim 6, wherein the magnetic flux calculation unit calculates the magnetic flux using half of the phase conductors among the phase conductors. The number of phase conductors is the same as the number of stator core salient pole portions,
The rotating electrical machine according to claim 6, wherein the magnetic flux calculation unit calculates the magnetic flux using all the phase conductors. N = 3K (K is a natural number)
M = (3 ± 1) · K,
The rotating electrical machine according to claim 6, wherein S = L = 3. N = 12K (K is a natural number),
M = 2 · (6 ± 1) · K,
The rotating electrical machine according to claim 6, wherein S = L = 6. The control device according to any one of claims 1 to 5,
A power converter that is controlled by the control device and converts DC power and AC power to each other;
The drive system provided with the said rotary electric machine connected to the alternating current side terminal of the said power converter.   The rotating electrical machine includes N stator core salient poles, M magnetic poles, and S wound around the stator core salient poles facing one pole (S is S ≧ N / M). The amplitude and phase of the current supplied to the L phase conductors (L is a natural number satisfying S ≧ L ≧ N / M) among the S phase conductors by the control device. The drive system according to claim 11, wherein each is controlled independently.   For each of the L phase conductors of the rotating electrical machine, the power converter includes a switch for turning on and off a current between one end of the phase conductor and each of a positive terminal and a negative terminal of a DC power source. The drive according to claim 12, further comprising: a first switch group having a second switch group having the switch between the other end of the phase conductor and each of the positive terminal and the negative terminal of the DC power source. system.