JP5363913B2 - Rotating electric machine drive system - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To effectively increase a torque in a wide rotational-number region by a structure capable of simplifying the winding structure of a dynamo-electric machine in a dynamo-electric machine driving system. <P>SOLUTION: A stator includes a plurality of phases of stator windings 28u, 28v and 28w wound in a concentrated winding, and generates a rotating magnetic field of a frequency comprising a higher harmonic component by the flow of an AC current through the stator windings 28u, 28v and 28w. A rotor includes rotor windings arranged at a plurality of positions in the peripheral direction and diodes rectifying the currents flowing through each rotor winding. The magnetic characteristics of magnetic poles at a plurality of positions in the peripheral direction generated by the current flowing through each rotor winding are made to differ alternately. The dynamo-electric machine driving system includes a switch 42 superposing pulse currents to stator currents flowing through the stator windings 28u, 28v and 28w only when the inter-phase voltage of the dynamo-electric machine 10 or a value corresponding to the inter-phase voltage is less than a threshold value or equal to or lower than the threshold value and when a preset pulse-superposing request condition holds. <P>COPYRIGHT: (C)2011,JPO&amp;INPIT

Description

  The present invention relates to a rotating electrical machine drive system that drives a rotating electrical machine in which a stator and a rotor are arranged to face each other.

  Conventionally, brushless generators as described in Patent Documents 1 to 4 are known. In the generators described in Patent Documents 1 and 2, the winding structure is complicated, and it is difficult to reduce the size. In the generators described in Patent Documents 3 and 4, the winding structure is complicated, and it is difficult to efficiently generate induced electromotive force due to the harmonic component of the magnetic field in the field winding of the rotor.

  Patent Document 5 discloses a field winding type synchronous machine including a stator and a rotor, in which the rotor core has a core teeth portion forming a pair of field poles, and a field magnetic flux is to be formed in the core teeth portion. A synchronous machine having a rotor coil lined around it and shorting the rotor coil through a diode is described. Of the armature currents flowing through the stator coils, the rotor excitation current applied to the synchronous current, which is the current component for generating torque, is assumed to have a pulse-like waveform higher than the frequency of the synchronous current. That is, Patent Literature 5 describes a field winding type synchronous machine that generates torque by superimposing a pulse current on a stator current to generate an induction current in a rotor winding.

Japanese Patent Laid-Open No. Sho 62-23348 JP-A-4-285454 JP-A-8-65976 JP-A-11-220857 JP 2007-185082 A

[Prior Invention Invented Prior to the Present Invention]
On the other hand, the inventors of the present invention invented the following rotating electrical machine according to the prior invention prior to the present invention. FIGS. 29-31 is a figure which shows schematic structure of the rotary electric machine which concerns on a prior invention. FIG. 29 is a diagram illustrating a schematic configuration of the stator and the rotor as viewed in a direction parallel to the rotation axis of the rotor. FIG.
FIG. 31 shows a schematic configuration of the stator, and FIG. 31 shows a schematic configuration of the rotor. The rotating electrical machine 10 includes a stator 12 fixed to a casing (not shown), and a rotor 14 that is opposed to the stator 12 with a predetermined gap and is rotatable with respect to the stator 12. 29 to 31 show an example of a radial type rotating electrical machine in which the stator 12 and the rotor 14 are opposed to each other in the radial direction orthogonal to the rotation shaft 22 (hereinafter simply referred to as the radial direction in the description of the previous invention). The rotor 14 is disposed on the radially inner side of the stator 12.

  As shown in FIG. 30, the stator 12 includes a stator core 26, and stator windings 28u, 28v of a plurality of phases (more specifically, for example, three phases of u phase, v phase, and w phase) disposed on the stator core 26. , 28w. A plurality of teeth 30 projecting radially inward (toward the rotor 14 (FIG. 29)) are arranged on the stator core 26 at intervals from each other along the circumferential direction around the rotating shaft 22 (FIG. 29). A slot 31 is formed between the teeth 30. That is, the stator core 26 is formed with a plurality of slots 31 spaced apart from each other in the circumferential direction. The stator windings 28 u, 28 v, 28 w of each phase are wound around the teeth 30 through the slots 31 with concentrated short-winding windings. As described above, the stator windings 28u, 28v, and 28w are wound around the teeth 30 to form a magnetic pole. The teeth 30 arranged in the circumferential direction are magnetized by passing a plurality of phases of alternating current through the stator windings 28u, 28v, 28w of the plurality of phases, and a rotating magnetic field that rotates in the circumferential direction is generated in the stator 12. Can do.

  The rotating magnetic field formed on the teeth 30 acts on the rotor 14 from the front end surface. In the example shown in FIG. 30, one pole pair is configured by three teeth 30 around which three-phase (u-phase, v-phase, and w-phase) stator windings 28u, 28v, and 28w are wound. Phase stator windings 28u, 28v, 28w are wound around each tooth 30, and the number of pole pairs of the stator 12 is four.

  As shown in FIG. 31, the rotor 14 includes a rotor core 16 and a plurality of rotor windings 18 n and 18 s disposed on the rotor core 16. A plurality of salient poles 19 projecting radially outward (toward the stator 12) are arranged on the rotor core 16 at intervals from each other along the circumferential direction, and each salient pole 19 is arranged in the stator 12 (FIG. 30). Is facing. In the rotor 14, due to the salient pole 19, the magnetic resistance when the magnetic flux from the stator 12 (tooth 30) passes changes according to the rotation direction, and the magnetic resistance is lowered at the position of the salient pole 19. The magnetic resistance increases at the position between. The rotor windings 18n and 18s are wound around the salient poles 19 so that the rotor windings 18n and the rotor windings 18s are alternately arranged in the circumferential direction. Here, the winding central axis of each rotor winding 18n, 18s coincides with the radial direction. As shown in FIG. 31, when the magnetic path between the salient poles 19 with high magnetic resistance is a d-axis magnetic path and the magnetic path of the salient pole 19 with low magnetic resistance is a q-axis magnetic path, each rotor winding 18n , 18s are arranged in a q-axis magnetic path having a low magnetic resistance. In the example shown in FIG. 31, the rotor windings 18n and 18s wound around the salient poles 19 are not electrically connected to each other and are separated (insulated). Then, diodes 21n and 21s (rectifier elements) are connected to each of the electrically separated rotor windings 18n and 18s. Since each rotor winding 18n is short-circuited via the diode 21n, the direction of the current flowing through each rotor winding 18n is rectified in one direction by the diode 21n. Similarly, since each rotor winding 18s is short-circuited via the diode 21s, the direction of the current flowing through each rotor winding 18s is rectified in one direction by the diode 21s. Here, the diodes are arranged so that the directions of currents flowing in the rotor windings 18n and the rotor windings 18s arranged adjacent to each other in the circumferential direction (rectification directions by the diodes 21n and 21s), that is, the forward directions are opposite to each other. 21n and 21s are connected to the rotor windings 18n and 18s in opposite directions.

  When a direct current corresponding to the rectification direction of the diode 21n flows through the rotor winding 18n, the salient pole 19 around which the rotor winding 18n is wound is magnetized, so that the salient pole 19 is a magnet with a fixed magnetic pole (magnetic pole). Part). Similarly, when a direct current corresponding to the rectification direction of the diode 21s flows through the rotor winding 18s, the salient pole 19 around which the rotor winding 18s is wound is magnetized, so that the salient pole 19 is fixed to the magnetic pole. It functions as a magnet (magnetic pole part). Since the direct current directions of the rotor winding 18n and the rotor winding 18s adjacent to each other in the circumferential direction are opposite to each other, the magnetization directions of the salient poles 19 adjacent to each other in the circumferential direction are opposite to each other. And the magnetic poles of the salient poles 19 alternate in the circumferential direction. Here, the rotor by the diodes 21n and 21s is formed such that the N pole is formed on the salient pole 19 around which the rotor winding 18n is wound, and the S pole is formed on the salient pole 19 around which the rotor winding 18s is wound. The rectification directions of the currents of the windings 18n and 18s are respectively set. Thereby, a magnet is formed on each salient pole 19 so that the N pole and the S pole are alternately arranged in the circumferential direction. In FIG. 31, the direction of the broken-line arrow shown outside the rotor windings 18 n and 18 s with respect to the radial direction of the rotor 14 represents the magnetization direction of the salient pole 19. And two poles 19 (N pole and S pole) adjacent in the circumferential direction constitute one pole pair. In the example shown in FIG. 31, eight poles 19 are formed, and the number of pole pairs of the rotor 14 is four. Therefore, in the example shown in FIGS. 29 to 31, the number of pole pairs of the stator 12 and the number of pole pairs of the rotor 14 are both four, and the number of pole pairs of the stator 12 and the number of pole pairs of the rotor 14 are equal. However, the number of pole pairs of the stator 12 and the number of pole pairs of the rotor 14 may both be other than four pole pairs. As described above, the magnetic characteristics of the salient poles 19 which are magnetic pole portions at a plurality of locations in the circumferential direction of the rotor 14 generated by the current flowing through the rotor windings 18 n and 18 s are alternately different in the circumferential direction of the rotor 14. .

  In the prior invention, the width of each salient pole 19 in the circumferential direction of the rotor 14 is set to be shorter than the width corresponding to 180 ° in electrical angle of the rotor 14. The width θ of each rotor winding 18n, 18s in the circumferential direction is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, and the rotor windings 18n, 18s It is wound with a roll. The width θ of the rotor windings 18n and 18s here can be expressed by the center width of the cross section of the rotor windings 18n and 18s in consideration of the cross-sectional area of the rotor windings 18n and 18s. That is, the width θ of the rotor windings 18n and 18s can be expressed by the average value of the inner peripheral surface width and the outer peripheral surface width of the rotor windings 18n and 18s. The electrical angle of the rotor 14 is represented by a value obtained by multiplying the mechanical angle of the rotor 14 by the number of pole pairs of the rotor 14 (p = 4 in the example shown in FIG. 31) (electrical angle = mechanical angle × p). Therefore, the width θ of each rotor winding 18n, 18s in the circumferential direction satisfies the following expression (1), where r is the distance from the center of the rotating shaft 22 to the rotor windings 18n, 18s.

  θ <π × r / p (1)

  In the prior invention, the distribution of the magnetomotive force that generates the rotating magnetic field in the stator 12 is based on the arrangement of the stator windings 28u, 28v, 28w of each phase and the shape of the stator core 26 by the teeth 30 and the slots 31 (basic It does not have a sinusoidal distribution (only of waves), but includes harmonic components. In particular, in the concentrated winding, the stator windings 28u, 28v, 28w of the respective phases do not overlap each other, so that the amplitude level of the harmonic component generated in the magnetomotive force distribution of the stator 12 increases. For example, when the stator windings 28u, 28v, and 28w are three-phase concentrated windings, the amplitude level of the input electrical frequency tertiary component increases as a harmonic component. In the following description, a harmonic component generated in the magnetomotive force due to the arrangement of the stator windings 28u, 28v, 28w and the shape of the stator core 26 is referred to as a spatial harmonic.

  In response to the rotating magnetic field (fundamental wave component) formed in the teeth 30 acting on the rotor 14 by passing a three-phase alternating current through the three-phase stator windings 28u, 28v, 28w, the magnetoresistance of the rotor 14 is increased. So that the salient poles 19 are attracted to the rotating magnetic field of the teeth 30. As a result, torque (reluctance torque) acts on the rotor 14, and the rotor 14 is rotationally driven in synchronization with the rotating magnetic field (fundamental wave component) formed by the stator 12.

  Furthermore, when the rotating magnetic field including the spatial harmonic component formed in the teeth 30 is interlinked with the rotor windings 18n and 18s of the rotor 14, the rotor windings 18n and 18s have a spatial harmonic component that causes the rotor 14 Magnetic flux fluctuations having a frequency different from the rotational frequency (the fundamental wave component of the rotating magnetic field) occur. Due to this magnetic flux variation, an induced electromotive force is generated in each of the rotor windings 18n and 18s. The current flowing through the rotor windings 18n and 18s along with the generation of the induced electromotive force is rectified by the diodes 21n and 21s to be unidirectional (direct current). The salient poles 19 are magnetized in response to the direct current rectified by the diodes 21n and 21s flowing in the rotor windings 18n and 18s, so that the magnetic poles become either N or S poles. ) A fixed magnet is generated at each salient pole 19. As described above, since the current rectification directions of the rotor windings 18n and 18s by the diodes 21n and 21s are opposite to each other, the magnets generated in the respective salient poles 19 are alternately arranged in the circumferential direction with N and S poles. Will be. Then, the magnetic field of each salient pole 19 (magnet with a fixed magnetic pole) interacts with the rotating magnetic field (fundamental wave component) of the teeth 30 to cause attraction and repulsion. Torque (torque corresponding to magnet torque) is applied to the rotor 14 also by electromagnetic interaction (attraction and repulsion) between the rotating magnetic field (fundamental wave component) of the tooth 30 and the magnetic field of the salient pole 19 (magnet). The rotor 14 is driven to rotate in synchronization with the rotating magnetic field (fundamental wave component) formed by the stator 12. As described above, the rotating electrical machine 10 according to the previous invention can be caused to function as an electric motor that generates power (mechanical power) in the rotor 14 by using power supplied to the stator windings 28u, 28v, 28w. On the other hand, the rotating electrical machine 10 according to the previous invention can be made to function as a generator that generates power in the stator windings 28u, 28v, 28w using the power of the rotor 14.

  Here, the result of calculating the interlinkage magnetic flux to the rotor windings 18n and 18s due to the spatial harmonics is shown in FIGS. 32A and 32B. The waveform in the upper half of FIG. 32A shows the temporal change of the motor current that is a certain one-phase current flowing through the stator windings 28u, 28v, 28w, and the waveform in the lower half shows the motor in the upper half. The waveform of the interlinkage magnetic flux to the rotor windings 18n and 18s when the phase of the alternating current flowing through the stator windings 28u, 28v and 28w (current advance angle with respect to the rotor position) is changed with the current as a reference is shown. . FIG. 32B shows the frequency analysis result of the flux linkage waveform applied to the rotor windings 18n and 18s. From the frequency analysis result shown in FIG. 32B, an input electrical frequency tertiary component is mainly generated. As shown in FIG. 32A, it can be seen that when the current advance angle is changed, the linkage flux bias changes, but the linkage flux waveform does not change much.

  The amplitude (variation width) of the interlinkage magnetic flux to the rotor windings 18n and 18s is affected by the width θ of the rotor windings 18n and 18s in the circumferential direction. Here, FIG. 33 shows the result of calculating the amplitude (variation width) of the interlinkage magnetic flux to the rotor windings 18n and 18s while changing the width θ of the rotor windings 18n and 18s in the circumferential direction. In FIG. 33, the coil width θ is shown converted to an electrical angle. As shown in FIG. 33, the fluctuation width of the linkage flux to the rotor windings 18n and 18s increases as the coil width θ decreases from 180 °, so that the coil width θ is made smaller than 180 °. By setting the rotor windings 18n and 18s to short-pitch windings, the amplitude of the interlinkage magnetic flux due to spatial harmonics can be increased as compared with full-pitch windings.

  Therefore, in the prior invention, the width of each salient pole 19 in the circumferential direction is made smaller than the width corresponding to 180 ° in electrical angle, and the rotor windings 18n and 18s are wound around each salient pole 19 with short-pitch winding. Thus, the induced electromotive force due to the spatial harmonics generated in the rotor windings 18n and 18s can be efficiently increased. For this reason, it is possible to efficiently generate an induced current in the rotor windings 18n and 18s using spatial harmonics that do not easily contribute to torque generation, and efficiently generate the magnetic flux of the magnet generated in each salient pole 19 by the induced current. Can be increased. As a result, the torque acting on the rotor 14 can be increased efficiently. Furthermore, it is possible to efficiently generate induced electromotive force due to space harmonics in the rotor windings 18n and 18s without providing the stator 12 with other types of exciting windings other than the stator windings 28u, 28v, and 28w. it can. For this reason, the winding provided in the stator 12 can be simplified to one type (only the stator windings 28u, 28v, 28w), and the winding structure of the stator 12 can be simplified. The induced current generated by the induced electromotive force is rectified by the diodes 21n and 21s, so that the rotor 14 is not provided with any type of winding other than the rotor windings 18n and 18s. Since the pole 19 can function as a magnetic pole portion that is a magnet with a fixed magnetic pole, the winding provided in the rotor 14 can be simplified to one type (only the rotor windings 18n and 18s). The structure can be simplified. As a result, the winding structure of the rotating electrical machine 10 can be simplified, and the rotating electrical machine 10 can be downsized.

  Furthermore, as shown in FIG. 33, when the coil width θ is 90 °, the amplitude of the interlinkage magnetic flux due to the spatial harmonics is maximized. Therefore, in the prior invention, in order to further increase the amplitude of the interlinkage magnetic flux to the rotor windings 18n and 18s due to the spatial harmonics, the width θ of each rotor winding 18n and 18s in the circumferential direction is the electrical angle of the rotor 14. Is preferably equal to (or substantially equal to) the width corresponding to 90 °. For this reason, it is preferable that the width θ of each rotor winding 18n, 18s in the circumferential direction satisfies (or substantially satisfies) the following expression (2).

  θ = π × r / (2 × p) (2)

  Thus, by making the width θ of each rotor winding 18n, 18s in the circumferential direction equal to (or substantially equal to) the electrical angle corresponding to 90 °, the spatial harmonics generated in the rotor windings 18n, 18s. Can be maximized, and the magnetic flux generated in each salient pole 19 by the induced current can be increased most efficiently. As a result, the torque acting on the rotor 14 can be increased more efficiently. That is, when the width θ greatly exceeds the width corresponding to 90 °, the magnetomotive force in the direction of canceling each other easily interlinks with the rotor windings 18n and 18s, but becomes smaller than the width corresponding to 90 °. Therefore, the possibility becomes low. However, if the width θ is greatly reduced from a width corresponding to 90 °, the magnitude of the magnetomotive force linked to the rotor windings 18n and 18s is greatly reduced. For this reason, such inconvenience can be prevented by setting the width θ to a width corresponding to about 90 °. Therefore, the width θ of each rotor winding 18n, 18s in the circumferential direction is preferably substantially equal to a width corresponding to 90 ° in electrical angle.

  FIG. 34 shows the result of calculating the torque of the rotor 14 while changing the phase of the alternating current flowing through the stator windings 28u, 28v, 28w (current advance angle with respect to the rotor position). FIG. 34 shows calculation results when the amplitude (current amplitude) and phase (current advance angle) of the alternating current flowing through the stator windings 28u, 28v, and 28w are changed while keeping the rotation speed of the rotor 14 constant. Yes. As shown in FIG. 34, since the torque of the rotor 14 changes when the current advance angle is changed, the rotor 14 is controlled by controlling the current advance angle (phase of alternating current flowing through the stator windings 28u, 28v, 28w). Torque can be controlled. Furthermore, as shown in FIG. 34, since the torque of the rotor 14 changes even when the current amplitude is changed, the current amplitude (the amplitude of the alternating current flowing through the stator windings 28u, 28v, 28w) is also controlled. The torque of the rotor 14 can be controlled. Further, since the torque of the rotor 14 changes even if the rotation speed of the rotor 14 is changed, the torque of the rotor 14 can also be controlled by controlling the rotation speed of the rotor 14.

However, in the case of the rotating electrical machine 10 according to such a prior invention, an effect that the winding structure of the rotating electrical machine 10 can be simplified can be obtained, but it is still improved from the aspect of effectively increasing the torque during low-speed rotation with a low rotational speed. There is room for. FIG. 35 is a diagram in which the relationship between the rotational speed and the regenerative torque is obtained by experiments using the rotary electric machine 10 according to the previous invention as a generator. As shown in FIG. 35, in the rotating electrical machine 10, the regenerative torque greatly decreased in a low rotation speed region, for example, less than 800 min ⁻¹ (= rpm). On the other hand, FIGS. 36A and 36B are diagrams showing temporal changes in the rotor induced current, which are currents of two phases flowing through the rotor windings 18n and 18s, that is, different phases of the A phase and the B phase. FIG. 36B shows the case where the rotational speed of the rotor 14 is 200 min ⁻¹ , and FIG. 36B shows the case where the rotational speed of the rotor 14 is 800 min ⁻¹ .

As can be seen from FIGS. 36A and 36B, in the region where the rotational speed of the rotor 14 is low (200 min ⁻¹ or the like), the rotor induced current is greatly reduced compared to the region where the rotational speed is medium. The reason for this is that in the previous invention, the rotor induced current flowing through the rotor windings 18n and 18s is generated by the magnetic field fluctuation due to the harmonic component of the rotating magnetic field generated by the stator, whereas in the region where the rotational speed is low, each rotor This is because the interlinkage magnetic flux interlinking with the windings 18n and 18s does not change much, but the fluctuation speed of the interlinkage magnetic flux decreases, so that the induced electromotive voltage decreases and the rotor induced current decreases. For this reason, the regenerative torque decreases during low-speed rotation. In the above description, the case where the regenerative torque is reduced in a region where the rotational speed is low has been described. However, even when the rotating electrical machine 10 according to the previous invention is used as an electric motor (motor), the low rotational speed region is used for the same reason. Then, there is a possibility that the rotational torque is greatly reduced.

  In the case of the configurations described in Patent Documents 1 to 5, a structure that can simplify the winding structure of the rotating electrical machine and can effectively increase the torque in a wide rotational speed region is not disclosed. For example, in the case of the synchronous machine described in Patent Document 5, when a sinusoidal current is applied to the stator winding, no current for exciting the field pole is generated in the rotor winding, so that no induced current is generated. In such a structure, torque cannot be generated unless a current having a higher frequency than the frequency of the fundamental current of the stator current such as a pulse current is superimposed on the stator current. However, in the case of the structure described in Patent Document 5, a pulse current is superimposed on the stator current regardless of the rotational speed and the interphase voltage of the rotating electrical machine related to the rotational speed. For this reason, in the high rotation speed region, the applicable voltage (drive voltage) whose magnitude changes corresponding to the rise that is the time change of the current is limited, so that a sufficient pulse current cannot be superimposed. As a result, the induced current of the rotor may decrease, leading to a decrease in torque.

  An object of the present invention is to effectively increase the torque in a wide rotational speed region with a structure that can simplify the winding structure of a rotating electrical machine in a rotating electrical machine drive system.

  The rotating electrical machine drive system according to the present invention employs the following means in order to achieve the above object.

A rotating electrical machine drive system according to the present invention is a rotating electrical machine drive system that drives a rotating electrical machine in which a stator and a rotor are opposed to each other. The stator has a plurality of slots spaced apart from each other in the circumferential direction around the rotor rotational axis. A stator core formed and a multi-phase stator winding wound around the stator core through the slot in a concentrated manner, and an AC current flows through the stator winding to rotate a frequency including harmonic components. A magnetic field is generated, and the rotor is arranged at a plurality of locations in the circumferential direction of the rotor core, and a rotor winding in which an induced electromotive force is generated when a rotating magnetic field including harmonic components generated by the stator is linked, and A rectifying element connected to each rotor winding and rectifying a current flowing through each rotor winding by the generation of the induced electromotive force. And by varying the magnetic properties of the magnetic pole portions in the circumferential direction a plurality of locations to be made in the circumferential direction alternately, the width in the circumferential direction of the rotor windings, smaller than 180 degrees in electrical angle of each phase of the stator current and which, furthermore, d-axis voltage command value Vd and used when the stator current line voltage of the rotary electric machine increases in proportion to the rotational speed of the rotor in certain cases (1), or vector control of the stator current The first pulse superposition requirement condition that the line voltage relation value, which is a value (Vd ² + Vq ² ) ^1/2 (2) calculated from the q-axis voltage command value Vq , is less than or less than the threshold is satisfied. The pulse superposition state is determined so that the pulse superposition condition is met only when the preset second pulse superposition requirement is met and the pulse current is superimposed on the stator current flowing through the stator winding. Turn off A characteristic line that defines the relationship between the torque of the rotating electrical machine and the number of rotations when the rotating electrical machine can be driven regardless of the switching by the switching unit and the pulse current is not superimposed on the stator current is provided, A rotating electrical machine drive system having a characteristic that torque decreases at a lower rotational speed with a predetermined rotational speed as a boundary .

According to the rotating electrical machine drive system of the present invention, the winding structure of the rotating electrical machine can be simplified for the same reason as in the previous invention. Moreover, according to the present invention, it is possible to effectively increase the torque in a wide rotational speed range. That is, the number of revolutions when the first pulse superimposition requirement condition is satisfied, and the preset second pulse superimposition requirement condition is satisfied when the line voltage relationship value of the rotating electrical machine is less than or less than the threshold value Since the pulse current can be superimposed on the stator current flowing through the stator winding in a low region, even if the number of rotations is low, magnetic field fluctuations other than the fundamental wave (sine wave) current of the rotating magnetic field are generated, and the rotor winding The torque can be improved by increasing the rotor induced current. Further, since the switching unit does not superimpose the pulse current on the stator current when the line voltage relationship value of the rotating electrical machine is equal to or greater than the threshold value or exceeds the threshold value, the torque can be sufficiently increased even in the high rotation speed region.

  Further, in the case of the synchronous machine described in Patent Document 5, torque cannot be generated unless a current having a higher frequency than the frequency of the fundamental current of the stator current such as a pulse current is superimposed on the stator current. On the other hand, in the case of the present invention, unlike the case of the synchronous machine described in Patent Document 5, when a sinusoidal current is passed through the stator current of the rotating electrical machine, it occurs in a stator having concentrated windings. Harmonic components can be used to generate an induced current in the rotor winding, and torque can be generated without necessarily superimposing a pulse current. For this reason, in the applied voltage, sine wave drive is performed in a region where there is not enough room for pulse current superposition, that is, sine wave drive using a sine wave stator current, and only in a region where there is sufficient room in the applied voltage. The torque can be increased by superimposing the pulse current. That is, it is not necessary to perform pulse superposition over the entire driving range of the rotating electrical machine, and sine wave driving can be performed in a wide driving range in which insufficient torque does not occur.

In the rotating electrical machine according to the present invention, preferably, the switching unit includes a torque rotational speed acquisition means for acquiring the required output torque required for the rotating electrical machine and the rotational speed of the rotating electrical machine, and a voltage corresponding to the required output torque. A line voltage acquisition means for acquiring a line voltage related value from a command value, and a sine wave torque calculation means for calculating a sine wave torque that can be generated by a sine wave current from a rotation speed and a current command value corresponding to a required output torque And the required output torque and the calculated sine wave torque are compared, and either the required output torque is equal to or greater than the sine wave torque or exceeds the sine wave torque, the second pulse superimposition request condition is used for pulse superimposition. Determining means for determining that the condition is satisfied.

  According to the above configuration, sinusoidal driving can be performed more effectively in a wide driving range.

In the rotating electrical machine according to the present invention, preferably, the switching unit includes a torque rotational speed acquisition means for acquiring the required output torque required for the rotating electrical machine and the rotational speed of the rotating electrical machine, and a voltage corresponding to the required output torque. A line voltage acquisition means for acquiring a line voltage related value from the command value, a sine wave loss and a required output torque when the required output torque is obtained by a sine wave current from the required output torque and the rotation speed And the number of revolutions to compare the pulse superposition loss when the required output torque can be obtained by superimposing the pulse on the sine wave current. And determining means for determining that the pulse superposition condition is satisfied, with any one of exceeding being the second pulse superposition request condition.

  According to the above configuration, the efficiency can be improved when the rotating electrical machine is driven.

  In the rotating electrical machine according to the present invention, preferably, each rotor winding is connected to a rectifying element whose forward direction is reversed between adjacent rotor windings in the circumferential direction of the rotor, and each rectifying element is connected to the induction coil. By rectifying the current flowing through the rotor winding by the generation of the electromotive force, the phase of the current flowing through the rotor winding adjacent in the circumferential direction is alternately changed between the A phase and the B phase.

  According to the above configuration, each rotor winding is connected to the rectifying element whose forward direction is the same in the circumferential direction between the rotor windings adjacent to each other in the circumferential direction of the rotor, and is generated by the current flowing through each rotor winding. Compared with the configuration in which the magnetic properties of the magnetic pole portions at a plurality of circumferential directions are alternately changed, the induced current that flows to generate the magnetic pole portion having one magnetic characteristic is different from that of the magnetic pole portion having another magnetic characteristic. It is possible to prevent the influence of the induced current flowing for generation in the direction in which the current is reduced, and to further improve the torque.

  In the rotating electrical machine according to the present invention, preferably, the width of each rotor winding in the circumferential direction of the rotor is substantially equal to a width corresponding to 90 ° in electrical angle.

  According to the above configuration, the induced electromotive force generated by the harmonics of the rotating magnetic field generated in the rotor winding can be generated to the maximum, and the magnetic flux of the magnetic pole portion generated by the induced current flowing in each rotor winding is most efficiently generated. Can be increased well. As a result, the torque acting on the rotor can be increased more efficiently.

  In the rotating electrical machine according to the present invention, preferably, each rotor winding is disposed in a q-axis magnetic path having a high inductance located at a plurality of locations in the circumferential direction of the rotor, and the rotor core is rectified by a rectifying element. A magnetic pole portion that functions as a magnet having a fixed magnetic pole by being magnetized in accordance with current flowing through the rotor winding, and includes a plurality of magnetic pole portions that are spaced apart from each other in the circumferential direction of the rotor.

  According to the said structure, the torque which acts on a rotor can be increased more efficiently.

  In addition, each rotor winding is arranged in a q-axis magnetic path having a high inductance located at a plurality of locations in the circumferential direction of the rotor, and the rotor core responds to the current rectified by the rectifying element flowing in the rotor winding. In a configuration including a plurality of magnetic pole portions that are magnetized and function as magnets with fixed magnetic poles and are spaced apart from each other in the circumferential direction of the rotor, preferably in the rotor core, each magnetic pole portion Protrudes toward the stator.

  In addition, each rotor winding is arranged in a q-axis magnetic path having a high inductance located at a plurality of locations in the circumferential direction of the rotor, and the rotor core responds to the current rectified by the rectifying element flowing in the rotor winding. In a configuration including a plurality of magnetic pole portions that function as a magnet having a magnetic pole fixed by magnetizing and are spaced apart from each other in the circumferential direction of the rotor, preferably in the rotor core, the circumference of the rotor Permanent magnets are arranged at portions located between the magnetic pole portions in the direction.

  In addition, each rotor winding is arranged in a q-axis magnetic path having a high inductance located at a plurality of locations in the circumferential direction of the rotor, and the rotor core responds to the current rectified by the rectifying element flowing in the rotor winding. In a configuration including a plurality of magnetic pole portions that are magnetized and that function as magnets with fixed magnetic poles and are spaced apart from each other in the circumferential direction of the rotor, the rotor core preferably includes an annular core portion. In addition, the rotor winding is wound around the annular core portion by toroidal winding, and each magnetic pole portion protrudes from the annular core portion toward the stator.

  In the rotating electrical machine according to the present invention, preferably, all of the rotor windings are electrically connected, and the rectifying element is connected in common to the rotor windings, and each rotor is generated by the generation of the induced electromotive force. Rectifying the current flowing through the windings and reversing the winding directions of the two rotor windings adjacent to each other in the circumferential direction, thereby generating magnetic pole portions at a plurality of circumferential directions generated by the current flowing through each rotor winding. The magnetic characteristics are alternately different.

  All of the rotor windings are electrically connected, and the rectifying element is connected in common to each rotor winding, and rectifies the current flowing through each rotor winding by the generation of the induced electromotive force, and A configuration in which the magnetic characteristics of the magnetic pole portions at a plurality of positions in the circumferential direction are alternately changed by reversing the winding directions of two rotor windings adjacent to each other in the direction. Preferably, the width of each rotor winding in the circumferential direction of the rotor is larger than the width corresponding to 90 ° in electrical angle and smaller than the width corresponding to 120 ° in electrical angle.

  In the rotating electrical machine according to the present invention, preferably, each rotor winding is disposed in a d-axis magnetic path having a low inductance located at a plurality of locations in the circumferential direction of the rotor.

  According to the said structure, the torque of a rotary electric machine can be made high effectively. That is, since the rotor windings are arranged in d-axis magnetic paths having low inductance located at a plurality of locations in the circumferential direction of the rotor, the current phase-torque characteristics are the same regardless of the rotation direction of the rotor, and the maximum torque value is obtained. And the torque can be effectively increased. For example, when the power running torque is increased, the power running torque can be increased both during the forward rotation of the rotor and during the reverse rotation of the rotor. Further, when increasing the regenerative torque, it is possible to increase the regenerative torque both when the rotor is rotating forward and when the rotor is rotating backward. Therefore, it is possible to realize a rotating electrical machine that can obtain high torque in both forward and reverse rotations of the rotor.

  Further, in the configuration in which each rotor winding is arranged in a d-axis magnetic path having a low inductance located at a plurality of locations in the circumferential direction of the rotor, preferably, in the rotor core, in a portion that coincides with the magnetic pole portion in the circumferential direction of the rotor. Permanent magnets are arranged.

  According to the above configuration, the magnetization direction of the permanent magnet is different between the permanent magnets adjacent in the circumferential direction, the magnetization direction of the permanent magnet, and the magnetization direction of the magnetic pole portion that matches the circumferential direction of the rotor with respect to the permanent magnet. , The permanent magnet generation torque generated by the permanent magnet and the rotor winding generation torque generated by the induced current flowing in the rotor winding become the maximum torque at the same phase of the current advance angle. That is, due to the induced current in the rotor winding, the rotor winding functions equivalently as an electromagnet, and the magnetic flux linked to the permanent magnet increases, and the torque of the rotating electrical machine increases accordingly. For this reason, the torque of the rotating electrical machine can be increased more effectively, and the torque characteristics are the same regardless of the rotation direction of the rotor. Further, since the fluctuation of magnetic flux in the permanent magnet is suppressed by the induced current flowing through the rotor winding, eddy current loss in the permanent magnet can be suppressed and the heat generation of the magnet can be reduced.

  Further, in the configuration in which each rotor winding is arranged in a d-axis magnetic path having a low inductance located at a plurality of locations in the circumferential direction of the rotor, preferably, in the rotor core, a portion located between the magnetic pole portions in the circumferential direction of the rotor Projecting toward the stator.

  In the rotating electrical machine according to the present invention, preferably, the rotor windings are electrically separated from each other, and a rectifying element is provided for each of the electrically separated rotor windings.

  In the rotating electrical machine according to the present invention, preferably, the rotor windings arranged adjacent to each other in the circumferential direction of the rotor are electrically separated from each other, and the rectifying element is the electrically separated rotor. The rotor windings provided for each winding and arranged every other circumferential direction are electrically connected to each other.

  In the rotating electrical machine according to the present invention, preferably, when the pulse current is superimposed on the stator current, the inverter current is superimposed on the stator current of each phase so that the pulse current is superimposed at a predetermined number of times set for one cycle. Drive signal output means for generating a drive signal and outputting the drive signal is provided.

  According to the above configuration, the interval at which the pulse current is superimposed depends on the frequency of the sine wave current that is the fundamental wave of the stator current. For this reason, it is possible to easily superimpose the pulse current on the spatial harmonic component of the rotating magnetic field with the optimum positional relationship of the rotor, and it is possible to easily increase the torque in the low speed region.

  In the rotating electrical machine according to the present invention, preferably, when the pulse current is superimposed on the stator current, the inverter drive signal is generated so that the pulse current is superimposed on the stator current of each phase at the set predetermined frequency. Drive signal output means for outputting a drive signal is provided.

  According to the above configuration, since the interval at which the pulse current is superimposed does not depend on the frequency of the sine wave current that is the fundamental wave of the stator current, it is possible to increase the torque when the rotation is stopped or in the extremely low speed rotation region. .

  According to the rotating electrical machine drive system of the present invention, it is possible to effectively increase the torque in a wide rotational speed region with a structure that can simplify the winding structure of the rotating electrical machine.

It is a figure which shows schematic structure of the rotary electric machine drive system which concerns on embodiment of this invention. In embodiment of this invention, it is the schematic which shows a part of part which the stator and rotor oppose. FIG. 2 is a diagram illustrating in detail a configuration of a switching unit in the configuration of FIG. 1. It is a figure which shows the experimental result which calculated | required the time change of the stator current at the time of superimposing a pulse current on a stator current by embodiment of this invention. It is a figure which shows the experimental result which calculated | required the time change of the rotor current at the time of rotating a rotor by 200min < ^-1 > by embodiment of this invention. It is a figure which shows the experimental result which calculated | required the relationship between the regenerative torque and rotation speed of a rotary electric machine at the time of superimposing a pulse current on a stator current in a low speed rotation area | region by embodiment of this invention. It is a figure which shows the experimental result of the time change of a stator current at the time of superimposing a pulse current on a stator current in a low speed rotation area | region by another embodiment of this invention. It is a figure which shows the experimental result which calculated | required the relationship between the regenerative torque of a rotary electric machine at the time of superimposing a pulse current on a stator current, and rotation speed by another embodiment of this invention. It is a figure which shows the experimental result of the time change of the stator electric current at the time of a stop of a rotary electric machine by another embodiment of this invention. It is a figure which shows the experimental result which calculated | required the relationship between the regenerative torque at the time of a stop of a rotary electric machine, and the superimposed frequency of a pulse current by another embodiment of this invention. In another embodiment of this invention, it is a figure which shows the structure of the switching part. It is a figure which shows an example of the 1-phase stator current (a) in the case of flowing a sine wave current to a stator, and the 2-phase rotor current (b) corresponding to this. It is a figure which shows an example of the 1-phase stator current (a) at the time of superimposing a pulse current on the sine wave current of FIG. 11 on a stator, and the 2-phase rotor current (b) corresponding to this. It is a figure which shows the example in which a copper loss falls by the case where a pulse current is superimposed rather than the case of a sine wave drive by the torque of a rotary electric machine increasing. In another embodiment of this invention, it is a block diagram which shows the drive control method of a rotary electric machine. In another embodiment of this invention, it is a block diagram which shows another example of the drive control method of a rotary electric machine. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. FIG. 21 is a diagram illustrating a result of calculating the amplitude of the linkage flux to the rotor winding while changing the width θ of the rotor winding in the circumferential direction in the configuration example of FIG. 20. It is the schematic which shows the other structural example of the rotary electric machine which comprises embodiment of this invention. In other structural examples of the rotary electric machine which constitutes an embodiment of the present invention, it is a schematic diagram seen in the direction parallel to the rotation axis of the rotor. In the configuration example of FIG. 23, the schematic configuration of the rotor is viewed in a direction parallel to the rotation axis of the rotor. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. In the rotary electric machine which concerns on a prior invention, it is a figure which shows schematic structure of the stator and rotor seen in the direction parallel to the rotating shaft of a rotor. In the rotary electric machine which concerns on a prior invention, it is a figure which shows schematic structure of a stator. In the rotary electric machine which concerns on a prior invention, it is a figure which shows schematic structure of a rotor. In the rotary electric machine which concerns on a prior invention, it is a figure which shows a motor current and the result of having calculated the linkage flux to the rotor winding | winding by a space harmonic. In the rotary electric machine which concerns on a prior invention, it is a figure which shows the frequency analysis result of the linkage magnetic flux waveform to a rotor winding | winding by a space harmonic. In the rotating electrical machine according to the previous invention, it is a diagram showing a result of calculating the amplitude of the interlinkage magnetic flux to the rotor winding while changing the width θ of the rotor winding in the circumferential direction. In the rotary electric machine which concerns on a prior invention, it is a figure which shows the result of having calculated the torque of the rotor, changing the phase of the alternating current sent through a stator winding. It is a figure which shows the experimental result which calculated | required the relationship between regenerative torque and rotation speed in the rotary electric machine which concerns on a prior invention. In the rotating electrical machine according to the previous invention, it is a diagram showing a temporal change of the rotor current when the rotor is rotated at 200 min ⁻¹ . In the rotating electrical machine according to the previous invention, it is a diagram showing a temporal change of the rotor current when the rotor is rotated at 800 min ⁻¹ .

  Hereinafter, embodiments of the present invention will be described with reference to the drawings. 1-3, 4A, 4B, and 5 are views showing an embodiment of the present invention. FIG. 1 is a diagram illustrating a schematic configuration of a rotating electrical machine drive system according to the present embodiment. FIG. 2 is a schematic view showing a part of a portion where the stator and the rotor face each other in the present embodiment. FIG. 3 is a diagram showing in detail the configuration of the switching unit in the configuration of FIG. The rotating electrical machine drive system 34 of this embodiment includes the rotating electrical machine 10, an inverter 36 that drives the rotating electrical machine 10, a control device 38 that controls the inverter 36, and a power storage device 40, and drives the rotating electrical machine 10. In addition, since the structure itself of the rotary electric machine 10 is the same as that of the rotary electric machine 10 according to the prior invention shown in FIGS. Simplify or omit. The power storage device 40 is provided as a direct current power source and is chargeable / dischargeable, and is constituted by, for example, a secondary battery. The inverter 36 includes a switching element (not shown), and converts the DC power from the power storage device 40 into odd-numbered alternating current such as u-phase, v-phase, and w-phase by switching operation of the switching element, Electric power can be supplied to each phase of the stator windings 28u, 28v, 28w. The control device 38 controls the switching operation of the switching elements constituting the inverter 36, and controls the phase (current advance angle) of the alternating current that flows through the stator windings 28u, 28v, 28w, so that the rotor 14 (FIG. 2). ) To control the torque. Such a rotating electrical machine drive system 34 is used, for example, as a vehicular travel power generator mounted on a hybrid vehicle, a fuel cell vehicle, an electric vehicle, or the like that includes an engine and a travel motor as drive sources.

  As shown in FIG. 2, the rotating electrical machine 10 that functions as an electric motor or a generator includes a stator 12 and a rotor 14 that are arranged to face each other. Stator windings 28u, 28v, 28w are wound by concentrated winding at a plurality of locations in the circumferential direction of the stator core 26, and rotor windings 18n, 18s are wound by concentrated winding at a plurality of locations in the circumferential direction of the rotor core 16. The width θ of the rotor windings 18n and 18s with respect to the circumferential direction of the rotor 14 is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, and the rotor windings 18n and 18s It is wound with a roll. More preferably, the width θ of the rotor windings 18n and 18s in the circumferential direction of the rotor 14 is equal to or substantially equal to the width corresponding to 90 ° in terms of the electrical angle of the rotor 14. The reason for this is as described in the previous invention.

  The control device 38 includes a microcomputer having a CPU, a memory, etc., and controls the torque of the rotating electrical machine 10 by controlling the switching of the switching element of the inverter 36. Further, the control device 38 includes a switching unit 42 and drive signal output means 44. The switching unit 42 satisfies any of the first pulse superposition request conditions that satisfy any of the first pulse superposition request conditions in which the interphase voltage of the rotating electrical machine 10 is less than or less than the preset threshold value. Is satisfied, a pulse current is superimposed on the stator current flowing through the stator windings 28u, 28v, 28w, and at least one of the first pulse superposition requirement condition and the second pulse superposition requirement condition is not satisfied, The pulse superimposed state is switched so that the pulse current is not superimposed on the stator current. The pulse current flows in a very short period compared to one cycle of the fundamental current of the stator current. That is, the switching unit 42 satisfies the first pulse superimposition request condition in which any of the interphase voltages of the rotating electrical machine 10 is less than the threshold value or less than the threshold value, and the preset second pulse superimposition request condition is Only when it is satisfied, it is determined that the pulse superposition condition is satisfied, and the pulse superposition state is switched so that the pulse current is superimposed on the stator current flowing through the stator windings 28u, 28v, 28w. For example, the first pulse superimposition requirement condition is that the interphase voltage of the rotating electrical machine 10 is less than a preset threshold value. However, the first pulse superimposition requirement condition may be that the interphase voltage is not more than a preset threshold value. Whether or not to include the case where the interphase voltage matches the threshold value is set in the switching unit 42 in advance in the first pulse superimposition request condition. The rotating electrical machine drive system 34 can drive the rotating electrical machine 10 regardless of the switching of the switching unit 42. As shown in FIG. 3, the switching unit 42 includes torque rotation number acquisition means 68, interphase voltage acquisition means 70, sine wave torque calculation means 72, and pulse superposition condition determination means 74. The rotating electrical machine drive system 34 includes a position sensor 46 (FIG. 1) that detects the rotational position of the rotor 14 of the rotating electrical machine 10, and inputs a detection signal of the position sensor 46 to the control device 38. For example, the position sensor 46 is disposed opposite to the outer peripheral surface of a magnetic wheel plate (not shown) that is fixed to a portion fixed to the rotor 14 (such as the rotary shaft 22) and whose magnetic characteristics alternately change in the circumferential direction. By detecting a change in magnetic characteristics, it is possible to detect the rotational position.

  When the pulse current is superimposed on the stator current, the drive signal output means 44 shown in FIG. 1 superimposes the pulse current on the stator current of each phase at regular intervals at a predetermined number of times for one cycle. A drive signal for the inverter 36 is generated and a drive signal is output. For example, in the present embodiment, when the rotating electrical machine drive system 34 is used as a vehicular traveling power generation device, a signal representing a torque command Treq corresponding to the accelerator opening detection signal is sent from an external control device (not shown). The present invention can be applied to a configuration in which switching of the inverter 36 is controlled by vector control by setting d-axis and q-axis current command values in response to input to the control device 38. For example, when the switching unit 42 determines that the pulse current is superimposed on the stator current, the drive signal output means 44 spatially harmonics the rotating magnetic field generated by the rotor 14 and the stator 12 with respect to the fundamental wave of the stator current. The rotor windings 18n and 18s are controlled so as to cause a magnetic field fluctuation based on the pulse current at the most efficient timing according to the positional relationship with the wave component. For this reason, it is possible to easily superimpose the pulse current on the spatial harmonic component of the rotating magnetic field with the optimal positional relationship of the rotor 14, and it is easy to obtain a high torque even at a low speed. For example, an A-phase current and a B-phase current, which are rotor currents having different phases, flow through the rotor windings 18 n and 18 s adjacent in the circumferential direction of the rotor 14. The B-phase or A-phase rotor windings 18n and 18s corresponding to the q-axis magnetic path can easily coincide with the central axis direction of the magnetic field fluctuation caused by the pulse current of the stator current of each phase, and high torque can be easily obtained. Become.

Further, it is possible to determine whether or not the pulse current is superimposed on the stator current as follows. First, the torque rotation speed acquisition means 68 acquires the torque command Treq that is the required output torque from the external control device as described above, and the rotational position of the rotor 14 from the detection signal of the position sensor 46 provided in the rotating electrical machine 10. And the rotational speed of the rotor 14, that is, the rotational speed VR is calculated, that is, acquired from the acquired rotational position. The interphase voltage acquisition means 70 calculates a voltage command value corresponding to the torque command Treq, and calculates, that is, acquires an interphase voltage from the voltage command value V1. The interphase voltage acquisition means 70 calculates and acquires an interphase voltage relation value, which is a voltage corresponding to the interphase voltage, instead of calculating and acquiring the interphase voltage, and can use it for subsequent processing. Also good. For example, (Vd ² + Vq ² ) ^1/2 calculated when the d-axis voltage command is Vd and the q-axis voltage command is Vq can be obtained as the interphase voltage relationship value.

  Further, the sine wave torque calculating means 72 calculates a current command value corresponding to the torque command Treq, and is a torque that can be generated as a sine wave current from the acquired rotation speed VR of the rotating electrical machine 10 and the calculated current command value. A certain sine wave torque Ts is calculated. Further, the pulse superimposition condition determining means 74 satisfies any first pulse superimposition requirement condition (Va <Vx or Va ≦ Vx) in which the interphase voltage Va is less than the threshold value Vx or less than or equal to the threshold value Vx, and torque The command Treq is compared with the calculated sine wave torque Ts, and the second pulse superposition request condition (Treq ≧ Ts or Treq> Ts) where the torque command Treq is equal to or greater than the sine wave torque Ts or exceeds the sine wave torque. It is determined that the pulse superimposition condition is satisfied only when) is satisfied. For example, the second pulse superimposition request condition is that the torque command Treq is equal to or greater than the sine wave torque Ts. However, the second pulse superposition request condition may be that the torque command Treq exceeds the sine wave torque Ts. Whether or not to include the case where the torque command Treq matches the sine wave torque Ts is included in the switching unit 42 in advance in the second pulse superimposition request condition.

  Here, the case where the first pulse superposition request condition is set in advance to Va <Vx and the second pulse superposition request condition is set to Treq ≧ Ts will be described. In this case, for example, when the interphase voltage Va is equal to or higher than the threshold value Vx (Va ≧ Vx), that is, when the first pulse superposition request condition is not satisfied, the pulse superposition condition determination unit 74 determines that the pulse superposition condition is not satisfied. To do. Furthermore, even when the first pulse superposition request condition is satisfied, the pulse superposition condition determination unit 74, for example, when the torque command Treq is less than the sine wave torque Ts (Treq <Ts), that is, the second pulse superposition request condition is If not, it is determined that the pulse superposition condition is not satisfied. For example, when the preset coefficient is α, the threshold Vx is α · Vdc (Vx = α · Vdc), which is a value obtained by multiplying the DC voltage Vdc input to the inverter by α. For example, α is set to 0.61 (α = 0.61) corresponding to the upper limit modulation degree (1) of the modulation wave with respect to the carrier signal when the inverter performs sine wave PWM control. However, α is not limited to this value. For example, α can be changed to 0.4, 0.5, 0.78, etc. in consideration of controllability and the like. Therefore, when Va ≧ α · Vdc and the first pulse superimposition requirement condition is not satisfied, it is determined that the pulse superposition condition is not satisfied. If the current is constant, the interphase voltage Va increases in proportion to the number of rotations, so that the pulse superposition condition is not satisfied when the current is equal to or higher than a certain threshold number of rotations. In this case, the switching unit 42 drives the rotating electrical machine 10 by passing a sine wave current that does not superimpose a pulse current on the stator current.

  Conversely, when the first pulse superposition requirement condition of Va <α · Vdc is satisfied, and the second pulse superposition requirement condition where the torque command Treq is equal to or greater than the sine wave torque Ts is satisfied (Treq ≧ Ts), the pulse superposition is performed. It is determined that the condition is satisfied, and a pulse superimposed current for superimposing the pulse current on the stator current is supplied to drive the rotating electrical machine 10. Further, even when the first pulse superimposition requirement condition that Va <α · Vdc is satisfied, the torque command Treq is less than the sine wave torque Ts (Treq <Ts), and when the second pulse superimposition requirement condition is not satisfied, the pulse superimposition is performed. It is determined that the condition is not satisfied, a sine wave current is passed through the stator current, and the rotating electrical machine 10 is driven. The interphase voltage is not obtained from the voltage command as described above, but the interphase voltage actually detected by the voltage sensor can also be used.

  Note that Va ≦ α · Vdc may be satisfied as the first pulse superposition request condition, or the torque command Treq may exceed the sine wave torque Ts (Treq> Ts) as the second pulse superposition request condition. it can. For example, if the first pulse superposition requirement condition is Va ≦ α · Vdc and the second pulse superposition requirement condition is set as Treq> Ts, then Va> α · Vdc, and the first pulse superposition requirement condition is not satisfied, It is determined that the pulse superposition condition is not satisfied. Conversely, when the first pulse superposition requirement condition of Va ≦ α · Vdc is satisfied and the torque command Treq exceeds the sine wave torque Ts (Treq> Ts), the pulse superposition is performed when the second pulse superposition requirement condition is satisfied. It is determined that the condition is satisfied, and a pulse superimposed current for superimposing the pulse current on the stator current is supplied to drive the rotating electrical machine 10. Further, even when the first pulse superposition requirement condition that Va ≦ α · Vdc is satisfied, the torque command Treq is equal to or less than the sine wave torque Ts (Treq ≦ Ts), and when the second pulse superposition requirement condition is not satisfied, the pulse superposition is performed. It is determined that the condition is not satisfied, a sine wave current is passed through the stator current, and the rotating electrical machine 10 is driven.

FIGS. 4A and 4B show the time variation of the stator current when the pulse current is superimposed on the stator current and the time variation of the rotor current when the rotor is rotated at 200 min ⁻¹ according to this embodiment. It is a figure which shows the calculated | required experimental result. In the following description, it demonstrates using the code | symbol attached | subjected in FIGS. In FIG. 4A, a pulse current is superimposed three times, which is a predetermined number of times set in advance at a timing indicated by an arrow, for one period with respect to a fundamental wave current that is a sine wave of a stator current. In this case, as shown in FIG. 4B, as is clear from the comparison with the experimental result of the prior invention of FIG. 36A, according to the present embodiment, the rotor current flowing through the rotor windings 18n and 18s according to the superposition of the pulse currents. As a whole, the value of the rotor current can be increased. For this reason, it turns out that the torque of the rotary electric machine 10 which is a synchronous machine can be improved also at the time of low speed rotation.

FIG. 5 is a diagram showing experimental results for determining the relationship between the regenerative torque and the rotational speed of the rotating electrical machine 10 when the pulse current is superimposed on the stator current. In FIG. 5, the curve shown as “sine wave drive” represents the experimental result when the stator current is a sine wave current in which the pulse current is not superimposed, as in the case of the previous invention in which the experimental result is shown in FIG. ing. In addition, “1 pulse”, “3 pulse”, and “6 pulse” are pulses at a rate of once, three, and six times for one cycle of the sine wave current that is the fundamental wave of the stator current. This shows that the current is superimposed. As is clear from the results shown in FIG. 5, it has been confirmed that in this embodiment, the torque can be greatly improved in the region where the rotational speed of the rotating electrical machine 10 is less than 800 min ⁻¹ . That is, according to the present embodiment, the torque can be increased in a region between the “1 pulse”, “3 pulse”, and “6 pulse” curves and the sinusoidal drive curve in the same rotation speed region. It has also been found that the torque can be improved as the number of times the pulse current is superimposed on one cycle of the sine wave current, which is the fundamental wave of the stator current, is increased. The experimental results shown in FIG. 5 show the relationship between the regenerative torque and the rotational speed, but the relationship between the output torque of the rotating electrical machine 10 and the rotational speed has the same tendency.

  According to the rotating electrical machine drive system 34 as described above, the winding structure can be simplified for the same reason as in the previous invention. Moreover, according to the present embodiment, the torque in a wide rotation speed region can be effectively increased. That is, the pulse current can be superimposed on the stator current flowing through the stator windings 28u, 28v, and 28w in the low rotation speed region where the rotation speed of the rotating electrical machine 10 is less than the threshold value. Torque can be improved by causing magnetic field fluctuations other than the fundamental wave (sine wave) current of the magnetic field and increasing the rotor induced current of the rotor windings 18n and 18s. In addition, the switching unit 42 switches the pulse superposition state so that the pulse current is not superimposed on the stator current when the rotation speed of the rotating electrical machine 10 is equal to or greater than the threshold value. Torque can be sufficiently increased without being suppressed. Further, the interval at which the pulse current is superimposed depends on the frequency of the sine wave current that is the fundamental wave of the stator current. For this reason, it is possible to easily increase the torque in the low speed region.

  In addition, in the voltage to be applied, sine wave drive in a region where there is not enough room for pulse current superposition, i.e., sine wave drive with a sine wave stator current, only in a region where there is enough room for applied voltage, The torque can be increased by superimposing the pulse current. That is, it is not necessary to perform pulse superposition over the entire driving range of the rotating electrical machine, and sine wave driving can be performed more effectively in a wide driving range where torque shortage does not occur.

  The rotor windings 18n and 18s are connected to diodes 21n and 21s (see FIG. 24), which are rectifying elements whose forward directions are reversed between the rotor windings 18n and 18s adjacent in the circumferential direction of the rotor 14. The diodes 21n and 21s rectify the current flowing through the rotor windings 18n and 18s by the generation of the induced electromotive force, thereby changing the phase of the current flowing through the rotor windings 18n and 18s adjacent in the circumferential direction to A The phase and the B phase are alternately changed. For this reason, each rotor winding 18n, 18s is connected to a diode whose forward direction is the same as the circumferential direction between the rotor windings 18n, 18s adjacent to each other in the circumferential direction of the rotor 14, and each rotor winding 18n, A comparative configuration in which the magnetic characteristics of the salient poles 19, which are magnetic pole portions at a plurality of positions in the circumferential direction generated by the current flowing through 18s, can be considered, but it is easier to improve the torque than this comparative configuration. it can. That is, in the comparison configuration, the induced current flowing to generate the salient pole 19 having one magnetic characteristic is reduced to the induced current flowing to generate another salient pole 19 having another magnetic characteristic. In the present embodiment, such inconvenience can be prevented and the torque can be improved more easily.

  Further, by making the width θ of each rotor winding 18n, 18s in the circumferential direction of the rotor 14 substantially equal to a width corresponding to 90 ° in electrical angle, harmonics of the rotating magnetic field generated in the rotor windings 18n, 18s. Can be generated maximally, and the magnetic flux of the salient pole 19 which is a magnetic pole portion generated by the induced current flowing in each rotor winding 18n, 18s can be increased most efficiently. As a result, the torque acting on the rotor 14 can be increased more efficiently.

  The rotor windings 18n and 18s are arranged in q-axis magnetic paths with high inductance located at a plurality of locations in the circumferential direction of the rotor 14, and the rotor core 16 has a current rectified by the diodes 21n and 21s. The salient poles 19 function as magnets with fixed magnetic poles by being magnetized in accordance with the flow of the wires 18n and 18s, and a plurality of salient poles 19 arranged at intervals in the circumferential direction of the rotor 14 are provided. Including. For this reason, the torque which acts on the rotor 14 can be increased more efficiently.

  6-9 is a figure which shows the experimental result performed by embodiment different from this Embodiment. FIG. 6 is a diagram showing experimental results of temporal changes in the stator current when a pulse current is superimposed on the stator current in a low-speed rotation region according to another embodiment. FIG. 7 is a diagram illustrating an experimental result of obtaining the relationship between the regenerative torque and the rotational speed of the rotating electrical machine 10 when a pulse current is superimposed on the stator current according to another embodiment. FIG. 8 is a diagram illustrating an experimental result of a temporal change in the stator current when the rotating electrical machine 10 is stopped according to another embodiment. FIG. 9 is a diagram illustrating an experimental result of obtaining a relationship between the regenerative torque when the rotating electrical machine 10 is stopped and the superimposed frequency of the pulse current according to another embodiment. In another embodiment, when the pulse current is superimposed on the stator current, the drive signal output means 44 outputs the drive signal of the inverter 36 so that the pulse current is superimposed on the stator current of each phase at a predetermined frequency set in advance. And generating a drive signal. For example, when the drive signal output means 44 controls the inverter 36 and the rotating electrical machine 10 by vector control by setting the d-axis and q-axis current command values as described above, the drive signal output means 44 has a predetermined frequency set in advance for the q-axis current command value. To control to generate a pulse current. In this case, the pulse current is superimposed at a frequency that is not related to the frequency of the sine wave of the stator current. In this case, since the interval at which the pulse current is superimposed does not depend on the frequency of the sine wave current that is the fundamental wave of the stator current, compared to the embodiment shown in the experimental results shown in FIG. In addition, torque can be increased in the extremely low speed rotation region.

  For example, in FIG. 6, the pulse current is superimposed on the stator current at a constant frequency, that is, 10 msec (= 100 Hz). In this case, as shown in FIG. 7, as compared with the case of the previous invention driven by a sine wave current, the torque in the low speed region can only be improved as shown in the experimental result represented by the curve shown as “pulse superimposed 100 Hz”. As a result, it was confirmed that the torque in the extremely low speed rotation region can be improved as compared with the case of the embodiment whose experimental results are shown in FIG. In the present embodiment, the torque can be increased in a region between the curve shown as pulse superposition 100 Hz in FIG. 7 and the sinusoidal drive curve in the same rotation speed region.

  Moreover, in the case of this another embodiment, the torque at the time of the stop of the rotary electric machine 10 can also be improved. That is, as shown in FIG. 8, when the pulse current is superimposed on the stator current at a constant frequency, for example, 10 msec (= 100 Hz) when the rotating electrical machine 10 is stopped, the frequency at which the pulse current is superimposed as shown in FIG. It was confirmed that the torque of the rotating electrical machine 10 can be increased as compared with the case where the pulse current is not superimposed on the stator current when the motor is stopped. Further, it was confirmed that the torque at the time of stopping can be increased as the frequency at which the pulse current is superimposed on the stator current is increased.

  FIG. 10 is a diagram showing a configuration of the switching unit 42 in another embodiment of the present invention. As shown in FIG. 10, in this other embodiment, the switching unit 42 includes a torque rotation speed acquisition unit 68, an interphase voltage acquisition unit 70, a map storage unit 76, and a second pulse superposition condition determination unit 78. including. In the following description, the same parts as those in the above embodiment shown in FIGS. 1 to 3 are denoted by the same reference numerals, and overlapping illustrations and descriptions are omitted or simplified. In the present embodiment, when the interphase voltage Va is equal to or lower than the threshold value Vx or less than the threshold value Vx, and the required output torque can be generated in either case of the sine wave current or the pulse current, the rotating electrical machine 10 (see FIG. 1) ) Is characterized in that the drive current waveform is determined so as to minimize the loss.

First, using FIG. 11 to FIG. 13, the principle that can minimize the loss of the rotating electrical machine by switching the drive current waveform between the sine wave and the pulse superimposed waveform will be described. FIG. 11 is a diagram illustrating an example of a one-phase stator current (a) and a corresponding two-phase rotor current (b) when a sinusoidal current is passed through the stator. FIG. 12 is a diagram showing an example of a one-phase stator current (a) and a corresponding two-phase rotor current (b) when a pulse current is superimposed on the sine wave current of FIG. 11 on the stator. It is. FIG. 13 is a diagram illustrating an example in which the copper loss is reduced in the case where the pulse current is superimposed rather than in the case of the sine wave drive due to the increase in the torque of the rotating electrical machine. 11 and 12, in the case of the sine wave current, the amplitudes of the A-phase and B-phase rotor currents are small and the torque of the rotating electrical machine 10 is small, but when the pulse current is superimposed, Since the amplitude of the phase rotor current is increased, the torque of the rotating electrical machine 10 can be increased. On the other hand, the amplitude of the sine wave current needs to be increased in order to produce the same torque as in the case of driving with the pulse superimposed current in the case of driving with the sine wave current. However, as shown in FIG. 13, when the same torque as in the case of the pulse superimposed current is obtained by increasing the amplitude with a sine wave current, the increase in the copper loss of the stator 12 may become considerably large (torque 100 in FIG. 13). %in the case of). In contrast, when a torque of 100% is obtained by the pulse superimposed current, the induced current increases compared to the case of the sine wave drive, and the increase in the copper loss of the stator 12 is also greater than that in the case of the amplitude increase of the sine wave current. Become smaller. In this case, it can be seen that when the torque is generated by superimposing the pulse current, the copper loss of the stator 12 can be reduced and the efficiency can be improved. On the other hand, the copper loss may be lower when driving with a sine wave current than when driving with a pulse superimposed current. For this reason, it is possible to determine that the loss of the rotating electrical machine 10 is minimized by switching the drive current waveform, and the efficiency at the time of driving the rotating electrical machine 10 can be improved. In the case of such a configuration, for example, in the diagram showing the relationship between the torque and the rotational speed shown in FIG. 7, a pulse is generated in the torque region below the curve shown as “sine wave drive” at 800 min ⁻¹ or less. The rotating electrical machine 10 can be driven using an electric current.

  Based on such a principle, in the present embodiment, a fundamental wave current I1 that is a sine wave current that minimizes the loss of the rotating electrical machine 10 with respect to the rotational speed and torque of the rotating electrical machine 10, Map data representing the pulse current command I2 (or pulse voltage command V2) is created in advance and stored in the map storage means 76 (FIG. 10). Then, the second pulse superimposition condition determining means 78 shown in FIG. 10 refers to the map stored in the map storage means 76, and the fundamental wave current I1 corresponding to the torque command Treq and the rotational speed, and the pulse current command I2 ( Alternatively, the pulse voltage command V2) is acquired, and the rotating electrical machine 10 is driven using I1 and I2 (or V2). More specifically, the second pulse superimposition condition determination unit 78 has any first pulse superimposition request condition in which the interphase voltage Va acquired by the interphase voltage acquisition unit 70 is less than the threshold value Vx or less than or equal to the threshold value Vx. If satisfied (Va <Vx or Va ≦ Vx), a sine wave loss D1 that is a loss when the torque command Treq is obtained from a sine wave current from the torque command Treq that is the required output torque and the rotation speed, and Then, the pulse superposition loss D2 which is a loss when the torque command Treq is obtained by superimposing the pulse current on the sine wave current from the torque command Treq and the rotation speed is compared. Then, the second pulse superimposition condition determining means 78 is either the second pulse in which the first pulse superimposition requirement condition is satisfied and the sine wave loss D1 is greater than or equal to the pulse superimposition loss D2 or exceeds the pulse superimposition loss D2. It is determined that the pulse superposition condition is met only when the superposition request condition is met (D1 ≧ D2 or D1> D2). On the other hand, the second pulse superimposition condition determining means 78 is used when the interphase voltage Va is equal to or higher than the threshold value Vx or the first pulse superimposition requirement condition exceeding the threshold value Vx is not satisfied (Va ≧ Vx or Va> Vx). In addition, even when the first pulse superposition requirement condition where the interphase voltage is less than the threshold value Vx or less than the threshold value Vx is satisfied (Va <Vx or Va ≦ Vx), the sine wave loss D1 is less than the pulse superposition loss D2. Or, when the second pulse superposition request condition that is equal to or less than the pulse superposition loss D2 is not satisfied (D1 <D2 or D1 ≦ D2), it is determined that the pulse superposition condition is not satisfied. And the control apparatus 38 (refer FIG. 1) drives the rotary electric machine 10 (refer FIG. 1) according to the determination result of pulse superimposition conditions.

  Next, two specific examples of the control method for driving the rotating electrical machine in this way will be described with reference to FIGS. In the case of the example in FIG. 14, the control device 38 includes a current command generation unit 80, a current command synthesis unit 82, and a voltage command drive signal generation unit 84. The current command generation unit 80 includes a switching unit 42 (FIG. 10). The torque command Treq and the acquired value of the rotational speed of the rotating electrical machine 10 are input to the current command generation unit 80. The current command generation unit 80 refers to the data of the map storage means 76 (FIG. 10), and the fundamental wave current command I1 that minimizes the loss of the rotating electrical machine 10 based on the torque command Treq and the rotation speed. The pulse current command I2 is acquired. In this case, if the pulse current command I2 is 0, the current command is a command corresponding to a sine wave current. If the pulse current command I2 is other than 0, that is, a positive value, the current command is a command corresponding to the pulse superimposed current. It becomes. In this case, as a condition for determining the pulse superimposed current command, a condition that the interphase voltage Va is less than the threshold value Vx or less than or equal to the threshold value Vx is also used.

  In addition, in the map of the map storage means 76, the fundamental wave current command I1 and the pulse current command I2 are determined in advance under the condition that the interphase voltage Va is less than the threshold value Vx or less than or equal to the threshold value Vx. You can also keep it. The current command combining unit 82 combines the fundamental current command I1 and the pulse current command I2 (which may be 0), and the combined current command d-axis current command Id * and q-axis current command Iq * Is output. Further, the control device 38 acquires each phase current from a current sensor (not shown) provided in the rotating electrical machine 10, and calculates a detection value of the d-axis current Id and the q-axis current Iq from each acquired phase current. Ie get. Next, the deviation between the combined current commands Id * and Iq * and the detected currents Id and Iq is input to the voltage command drive signal generator 84. The voltage command drive signal generation unit 84 calculates a voltage command by PI calculation or the like from the deviation, and generates a drive signal for turning on and off the switching element of the inverter 36 from the calculated voltage command and the acquired rotational position of the rotor 14. Ask. The inverter 36 is driven by this drive signal, and drives the rotating electrical machine 10 by a sine wave current or a pulse superimposed current. According to this embodiment, the efficiency can be improved when the rotating electrical machine 10 is driven by the above principle.

  15, the control device 38 includes a current command generation unit 80a, a voltage command generation unit 86, a pulse voltage command addition unit 88, and a drive signal generation unit 90. The part including the current command generation unit 80 and the pulse voltage command addition unit 88 includes a switching unit 42 (FIG. 10). The torque command Treq and the acquired value of the rotation speed of the rotating electrical machine 10 are input to the current command generation unit 80a. The current command generation unit 80a acquires a d-axis current command Id * and a q-axis current command Iq *, which are fundamental wave current commands I1, based on the torque command Treq and the rotation speed. The current command generator 80a outputs a fundamental wave current command I1. In addition, the control device 38 acquires each phase current from a current sensor (not shown) provided in the rotating electrical machine 10, and calculates, that is, acquires a detection value of the d-axis current Id and the q-axis current Iq from each acquired phase current. To do. Next, the deviation between the current commands Id * and Iq * and the detected currents Id and Iq is input to the voltage command generator 86. The voltage command generator 86 calculates a voltage command from the deviation by PI calculation or the like, and outputs the calculated voltage command. The pulse voltage command adding unit 88 refers to the data of the map storage means 76 (FIG. 10), and generates a pulse voltage command V2 that minimizes the loss of the rotating electrical machine 10 based on the torque command Treq and the rotation speed. get. In this case, if the pulse voltage command V2 is 0, the voltage command is a command corresponding to a sine wave current. If the pulse voltage command V2 is other than 0, that is, a positive value, the voltage command is a command corresponding to the pulse superimposed current. It becomes. In this case, as a condition for determining the pulse voltage command, a condition that the interphase voltage Va is less than the threshold value Vx or less than or equal to the threshold value Vx is also used.

  In addition, in the map of the map storage means 76, the fundamental wave current command I1 and the pulse voltage command V2 are determined in advance under the condition that the interphase voltage Va is less than the threshold value Vx or less than or equal to the threshold value Vx. You can also keep it. The pulse voltage command V2 (may be 0) output from the pulse voltage command adding unit 88 is added to the voltage command corresponding to the fundamental wave current command I1 and input to the drive signal generating unit 90. Similarly to the case of FIG. 14, the drive signal generation unit 90 obtains a drive signal for driving the inverter 36 from the voltage command and the acquired rotational position of the rotor 14. The inverter 36 is driven by this drive signal, and drives the rotating electrical machine 10 by a sine wave current or a pulse superimposed current. In the case of this embodiment as well, efficiency can be improved when the rotating electrical machine 10 is driven by the above principle.

  Next, another configuration example of the rotating electrical machine constituting the rotating electrical machine drive system 34 of the above embodiment will be described. As shown below, in the present invention, various configuration examples of rotating electric machines can be used.

  For example, in the above embodiment, the rotor windings 18n and 18s are wound around the salient poles protruding in the radial direction of the rotor 14, but as shown in FIG. 16, a slit (gap) 48 is formed in the rotor core 16. Also, the magnetic resistance of the rotor 14 can be changed according to the rotation direction. As shown in FIG. 16, in the rotor core 16, a magnetic path having a high magnetic resistance, that is, a low inductance is defined as a d-axis magnetic path portion 50, and a magnetic path having a lower magnetic resistance than the d-axis magnetic path portion 50, that is, a high inductance. Is a q-axis magnetic path portion 52, slits 48 are formed so that the d-axis magnetic path portions 50 and the q-axis magnetic path portions 52 facing the stator 12 (tooth 30) are alternately arranged in the circumferential direction. The d-axis magnetic path portion 50 is located between the q-axis magnetic path portions 52 in the circumferential direction.

  Each of the rotor windings 18n and 18s passes through the slit 48 and is wound around the q-axis magnetic path portion 52 having a low magnetic resistance. In the configuration example shown in FIG. 16, a rotating magnetic field including a spatial harmonic component formed by the stator 12 is linked to each rotor winding 18n, 18s, so that each diode 21n, 21s is connected to each rotor winding 18n, 18s. As a result of the direct current rectified in FIG. 6 flowing and magnetizing each q-axis magnetic path portion 52, each q-axis magnetic path portion 52 functions as a magnet (magnetic pole portion) with a fixed magnetic pole. At that time, the width of each q-axis magnetic path portion 52 in the circumferential direction (the width θ of each rotor winding 18n, 18s) is set shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, and the rotor winding By winding the wires 18n and 18s around each q-axis magnetic path portion 52 with a short-pitch winding, the induced electromotive force due to the spatial harmonics generated in the rotor windings 18n and 18s can be efficiently increased. Furthermore, in order to maximize the induced electromotive force due to the spatial harmonics generated in the rotor windings 18n and 18s, the width θ of each rotor winding 18n and 18s in the circumferential direction is set to 90 ° in terms of the electrical angle of the rotor 14. It is preferable to make it equal (or substantially equal) to the corresponding width. Other configurations and operations are the same as those in the above embodiment.

  In the above embodiment, for example, as shown in FIG. 17, the permanent magnet 54 can be disposed on the rotor core 16. In the configuration example shown in FIG. 17, a plurality of magnetic pole portions 56 functioning as magnets with fixed magnetic poles are arranged to face the stator 12 (see FIG. 2) in a state of being spaced apart from each other in the circumferential direction. 56, the rotor windings 18n and 18s are wound. Each permanent magnet 54 is disposed opposite to the stator 12 (the teeth 30) in a portion located between the magnetic pole portions 56 in the circumferential direction. The permanent magnet 54 may be embedded in the rotor core 16 or exposed on the surface (outer peripheral surface) of the rotor core 16. Further, the permanent magnet 54 can be arranged in a V shape inside the rotor core 16. In the configuration example shown in FIG. 17, a rotating magnetic field including a spatial harmonic component formed by the stator 12 is linked to the rotor windings 18n and 18s, so that the diodes 21n and 21s are connected to the rotor windings 18n and 18s. As a result of the rectified direct current flowing and magnetizing each magnetic pole portion 56, each magnetic pole portion 56 functions as a magnet with a fixed magnetic pole. At that time, the width of each magnetic pole portion 56 in the circumferential direction (the width θ of each rotor winding 18n, 18s) is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, and the rotor windings 18n, By winding 18s around each magnetic pole part 56 with a short-pitch winding, the induced electromotive force due to the spatial harmonics generated in the rotor windings 18n and 18s can be efficiently increased. Furthermore, in order to maximize the induced electromotive force due to the spatial harmonics generated in the rotor windings 18n and 18s, the width θ of each rotor winding 18n and 18s in the circumferential direction is set to 90 ° in terms of the electrical angle of the rotor 14. It is preferable to make it equal (or substantially equal) to the corresponding width. Other configurations and operations are the same as those in the above embodiment.

  In the above embodiment, for example, as shown in FIG. 18, every other rotor winding 18 n arranged in the circumferential direction is electrically connected in series, and every other rotor arranged in the circumferential direction. The windings 18s can be electrically connected in series. That is, the rotor windings 18n wound around the salient poles 19 functioning as magnets with the same magnetic pole (N pole) are electrically connected in series, and wound around the salient poles 19 functioning as magnets with the same magnetic pole (S pole). The mounted rotor windings 18s can be electrically connected in series. However, the rotor windings 18n and 18s wound around the salient poles 19 adjacent to each other in the circumferential direction (where magnets having different magnetic poles are formed) are electrically separated from each other. The diodes 21n and 21s are provided for each of the electrically separated rotor windings 18n and 18s (two), and the diode 21n rectifies the current flowing through the electrically connected rotor winding 18n. The diode 21s rectifies the current flowing through the rotor winding 18s electrically connected in series. Also here, a magnet having different magnetic poles is formed between the salient pole 19 around which the rotor winding 18n is wound and the salient pole 19 around which the rotor winding 18s is wound (the salient poles 19 adjacent to each other in the circumferential direction). Thus, the rectification directions of the currents of the rotor windings 18n and 18s by the diodes 21n and 21s are opposite to each other. According to the configuration example shown in FIG. 18, the number of diodes 21n and 21s can be reduced to two. Other configurations and operations are the same as those in the above embodiment.

  In the above-described embodiment, for example, as shown in FIG. 19, the rotor windings 18n and 18s can be toroidal. In the configuration example shown in FIG. 19, the rotor core 16 includes an annular core portion 58, and each salient pole 19 projects from the annular core portion 58 radially outward (toward the stator 12). The rotor windings 18n and 18s are wound by toroidal winding at positions near the salient poles 19 in the annular core portion 58. Also in the configuration example shown in FIG. 19, the rotating magnetic field including the spatial harmonic component formed by the stator 12 is linked to the rotor windings 18n and 18s, so that the diodes 21n and 21s are connected to the rotor windings 18n and 18s. The rectified direct current flows, and each salient pole 19 is magnetized. As a result, the salient pole 19 located near the rotor winding 18n functions as the N pole, and the salient pole 19 located near the rotor winding 18s functions as the S pole. At that time, by setting the width θ of each salient pole 19 in the circumferential direction to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, induction by spatial harmonics generated in the rotor windings 18 n and 18 s. The electromotive force can be increased efficiently. Further, in order to maximize the induced electromotive force due to the spatial harmonics generated in the rotor windings 18n and 18s, the width θ of each salient pole 19 in the circumferential direction is a width corresponding to 90 ° in terms of the electrical angle of the rotor 14. Is preferably equal (or substantially equal). In FIG. 19, similarly to the configuration example shown in FIG. 18, the rotor windings 18 n and 18 s adjacent in the circumferential direction are electrically separated from each other, and every other rotor winding 18 n is arranged in the circumferential direction. Are electrically connected in series, and the rotor windings 18s arranged in every other circumferential direction are electrically connected in series. However, also in the example in which the rotor windings 18n and 18s are toroidally wound, the rotor windings 18n and 18s wound around the salient poles 19 are electrically separated from each other, similarly to the configuration example shown in FIGS. You can also Other configurations and operations are the same as those in the above embodiment.

  In the above embodiment, for example, as shown in FIG. 20, a common rotor winding 18 can be wound around each salient pole 19. In the configuration example shown in FIG. 20, since the rotor winding 18 is short-circuited via the diode 21, the direction of the current flowing through the rotor winding 18 is rectified in one direction (direct current) by the diode 21. The rotor winding 18 wound around each salient pole 19 is a portion wound around the salient pole 19 adjacent in the circumferential direction so that the magnetization directions of the salient poles 19 adjacent in the circumferential direction are opposite to each other. Are wound in opposite directions. Also in the configuration example shown in FIG. 20, a rotating magnetic field including a spatial harmonic component formed by the stator 12 is linked to the rotor winding 18, so that a DC current rectified by the diode 21 flows through the rotor winding 18. As a result of each salient pole 19 being magnetized, each salient pole 19 functions as a magnet having a fixed magnetic pole. At that time, magnets having different magnetic poles are formed between the salient poles 19 adjacent in the circumferential direction. According to the configuration example shown in FIG. 20, the number of diodes 21 can be reduced to one. However, in this case, the salient pole 19 having one magnetic characteristic is generated with respect to the case of the above-described prior art of FIGS. 29 to 31, the embodiment of FIG. 2, and the other configuration examples of FIGS. Therefore, the induced current flowing for the purpose affects the induced current flowing to generate another salient pole 19 having different magnetic characteristics in the direction in which the current is reduced, which may be inferior in terms of torque improvement.

  That is, in the configuration example shown in FIG. 20, since the common rotor winding 18 is used for the salient pole 19 that forms the N pole and the salient pole 19 that forms the S pole, spatial harmonics at each salient pole 19. Magnetic flux fluctuations (third order) due to the components may be canceled out, and the torque of the rotor 14 may not increase as effectively as in the other configuration examples. Here, in the configuration example shown in FIG. 20, the amplitude (variation width) of the interlinkage magnetic flux to the rotor winding 18 while changing the width θ in the circumferential direction of the rotor winding 18 wound around each salient pole 19. FIG. 21 shows the result of calculating. In FIG. 21, the coil width θ is shown converted to an electrical angle. As shown in FIG. 21, when the coil width θ decreases from 90 °, the fluctuation width of the interlinkage magnetic flux to the rotor winding 18 greatly decreases, and when the coil width θ increases from 120 °, the linkage to the rotor winding 18 increases. The fluctuation range of the magnetic flux greatly increases. Further, in consideration of the necessity of the coil width θ for sufficiently securing the cross-sectional area of the rotor winding 18, the induced current due to the spatial harmonics generated in the rotor winding 18 in the configuration example shown in FIG. 20 is increased. In order to achieve this, the width θ of the rotor winding 18 in the circumferential direction is made larger than the width corresponding to 90 ° in the electrical angle of the rotor 14 and smaller than the width corresponding to 120 ° in the electrical angle of the rotor 14 ( 90 ° <θ <120 ° is preferably satisfied). Furthermore, as shown in FIG. 21, when the coil width θ is 105 °, the amplitude of the interlinkage magnetic flux due to the spatial harmonics peaks. Therefore, in order to further increase the induced current due to the spatial harmonics generated in the rotor winding 18 in the configuration example shown in FIG. 20, the width θ of the rotor winding 18 in the circumferential direction is set to 105 ° in terms of the electrical angle of the rotor 14. It is preferable to make it equal (or substantially equal) to the width corresponding to.

  Further, in the configuration example shown in FIG. 22, the rotor winding 18 is wound around each salient pole 19 by wave winding (series winding), and the magnetization directions of the salient poles 19 adjacent to each other in the circumferential direction are opposite to each other. The winding directions of the portions wound around the salient poles 19 adjacent in the circumferential direction are opposite to each other. In the rotor winding 18 of FIG. 22, the solid line portion passes through one side (front side in the figure) of the end surface in the rotation axis direction of the salient pole 19, and the broken line portion indicates the other side of the end surface in the rotation axis direction of the salient pole 19. Side). In the circle, a current in the front direction of the drawing flows in the portion marked with ●, and a current in the back direction of the drawing flows in the portion marked with x in the circle. Also in the configuration example shown in FIG. 22, the rotating magnetic field including the spatial harmonic component formed by the stator 12 is linked to the rotor winding 18, so that the DC current rectified by the diode 21 flows through the rotor winding 18. As a result of each salient pole 19 being magnetized, each salient pole 19 functions as a magnet having a fixed magnetic pole. At that time, magnets having different magnetic poles are formed between the salient poles 19 adjacent in the circumferential direction. According to the configuration example shown in FIG. 22, the number of diodes 21 can be reduced to one, and the winding structure of the rotor 14 can be further simplified.

  Further, as shown in the following configuration example, the above embodiment employs a configuration in which each rotor winding of the rotating electrical machine is arranged in a d-axis magnetic path having a low inductance located at a plurality of locations in the circumferential direction of the rotor. You can also. FIG. 23 is a schematic view of the rotating electrical machine as viewed in a direction parallel to the rotation axis. FIG. 24 is a schematic view of the schematic configuration of the rotor of FIG. 23 viewed in a direction parallel to the rotation axis.

  The rotating electrical machine 10 of this configuration example includes a stator 12 fixed to a casing (not shown), and a rotor 14 that is disposed to face the stator 12 in a radial direction with a predetermined gap therebetween and is rotatable with respect to the stator 12. 23 to 24 show an example of a radial type rotating electrical machine 10 in which the stator 12 and the rotor 14 are arranged so as to face each other in the radial direction, and the rotor 14 is arranged inside the stator 12 in the radial direction. Yes. The stator 12 includes odd-phase stator windings 28u, 28v, 28w such as a three-phase wound around a plurality of teeth 30. For example, a three-phase alternating current is applied to the three-phase stator windings 28u, 28v, 28w. By flowing, a rotating magnetic field having a frequency including a harmonic component is generated in the tooth 30. The main feature of this configuration example is the structure of the rotor 14, and the configuration and operation of the stator 12 are the same as those of the configuration examples shown in FIGS.

  As shown in FIG. 24, the rotor 14 is disposed at a plurality of locations in the circumferential direction of the rotor core 16, the rotor core 16, the wound rotor windings 18 n and 18 s, and a permanent disposed at a plurality of locations in the circumferential direction of the rotor 14. Magnet 54. The rotor 14 is fixed to the rotating shaft 22. Magnetic pole portions 60 such as pillar portions extending in the radial direction are formed at a plurality of locations in the circumferential direction of the rotor core 16, and the rotor windings 18 n and 18 s are wound around the magnetic pole portions 60.

  The permanent magnets 54 are arranged, that is, embedded, in magnetic pole portions 60 provided at portions that coincide with the rotor windings 18 n and 18 s in the circumferential direction of the rotor 14 at a plurality of circumferential positions of the rotor 14. In other words, the rotor windings 18 n and 18 s are wound around each permanent magnet 54. The permanent magnet 54 is magnetized in the radial direction of the rotor 14, and the magnetizing direction is made different between the permanent magnets 54 adjacent in the circumferential direction of the rotor 14. In FIGS. 23 and 24 (the same applies to FIG. 25 described later), the solid line arrow disposed on the permanent magnet 54 represents the magnetization direction of the permanent magnet 54. The magnetic pole part 60 can also be constituted by salient poles or the like arranged to extend in the radial direction at a plurality of locations in the circumferential direction of the rotor 14.

  The rotor 14 has different magnetic salient pole characteristics with respect to the circumferential direction. Of the rotor 14, a magnetic path having a high inductance L, which is located in the circumferential direction away from each permanent magnet 54 and away from the magnetic pole portion 60 in the circumferential direction, is a q-axis magnetic path, and coincides with each permanent magnet 54 in the circumferential direction. When the magnetic path having a low inductance L is a d-axis magnetic path, the rotor windings 18 n and 18 s are arranged in d-axis magnetic paths located at a plurality of locations in the circumferential direction of the rotor 14.

  Further, the rotor windings 18n and 18s wound around the magnetic pole portions 60 are not electrically connected to each other and are separated (insulated). A diode 21n (or 21s), which is a rectifying element, is connected in parallel to the electrically separated rotor windings 18n and 18s. Further, the current flow directions of the diodes 21n connected to every other part of the rotor windings 18n in the circumferential direction of the rotor 14 and the diodes 21s connected to the remaining rotor windings 18s are reversed, so that each other The forward direction is reversed. For this reason, each rotor winding 18n, 18s is short-circuited via the diode 21n (or 21s). Therefore, the current flowing through each rotor winding 18n, 18s is rectified in one direction. Also in this configuration example, each of the diodes 21n and 21s rectifies the current flowing through the rotor windings 18n and 18s due to the generation of the induced electromotive force, so that the rotor windings 18n and 18s adjacent in the circumferential direction of the rotor 14 are rectified. The phase of the flowing current is alternately changed between the A phase and the B phase between the adjacent rotor windings 18n and 18s.

  When a direct current corresponding to the rectification direction of the diodes 21n and 21s flows through the rotor windings 18n and 18s, the magnetic pole portion 60 around which the rotor windings 18n and 18s are wound is magnetized, so that the magnetic pole portion 60 is a magnetic pole. Functions as a fixed magnet. The direction of the broken arrow shown on the outside of the rotor windings 18n and 18s in the radial direction of the rotor 14 in FIGS. 23 and 24 represents the magnetization direction of the magnetic pole part 60.

  Further, as shown in FIG. 24, the directions of the direct currents are opposite to each other between the rotor windings 18 n and 18 s adjacent in the circumferential direction of the rotor 14. The magnetization directions of the magnetic pole portions 60 adjacent to each other in the circumferential direction of the rotor 14 are opposite to each other. That is, in this configuration example, the magnetic characteristics of the magnetic pole portions 60 are alternately different with respect to the circumferential direction of the rotor 14. For example, in FIGS. 23 and 24, N poles are arranged on the radially outer side of a portion corresponding to the circumferential direction of the rotor winding 18 n and the rotor 14, which is every other magnetic pole part 60 in the circumferential direction of the rotor 14. The S pole is arranged on the outer side in the radial direction of the portion corresponding to the circumferential direction of the rotor winding 18 s and the rotor 14, which is the magnetic pole portion 60 adjacent to the circumferential direction of the magnetic pole portion 60. The two magnetic pole portions 60 (N pole and S pole) adjacent in the circumferential direction of the rotor 14 constitute one pole pair. In addition, the magnetization direction of each permanent magnet 54 is matched with the magnetization direction of the magnetic pole portion 60 that matches the circumferential direction of the rotor 14 with respect to each permanent magnet 54.

  In the example shown in FIGS. 23 and 24, an 8-pole magnetic pole portion 60 is formed, and the number of pole pairs of the rotor 14 is 4-pole pairs. Further, the number of pole pairs of the stator 12 (FIG. 23) and the number of pole pairs of the rotor 14 are all four, and the number of pole pairs of the stator 12 and the number of pole pairs of the rotor 14 are equal. However, the number of pole pairs of the stator 12 and the number of pole pairs of the rotor 14 may be other than four pole pairs.

  In this configuration example, the width of each magnetic pole portion 60 in the circumferential direction of the rotor 14 is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14. The width θ (FIG. 24) of each rotor winding 18n, 18s in the circumferential direction is set to be shorter than the width corresponding to 180 ° in electrical angle of the rotor 14, and the rotor windings 18n, 18s 60 is wound with a short winding. Preferably, the width θ of each rotor winding 18n, 18s in the circumferential direction of the rotor 14 is equal (or substantially equal) to a width corresponding to 90 ° in electrical angle.

  In such a rotating electrical machine 10, a rotating magnetic field having a frequency including harmonic components generated in the teeth 30 (FIG. 23) is generated by passing a three-phase alternating current through the three-phase stator windings 28 u, 28 v, 28 w. 14 acts. Accordingly, the reluctance torque Tre, the permanent magnet generation torque Tmg, and the rotor winding generation torque Tcoil act on the rotor 14 to synchronize the rotor 14 with the rotating magnetic field (fundamental wave component) generated by the stator 12. And rotate. Here, the reluctance torque Tre is a torque generated when each magnetic pole portion 60 is attracted to the rotating magnetic field generated by the stator 12. The permanent magnet generation torque Tmg is a torque generated by attraction and repulsion, which is an interaction between the magnetic field generated by each permanent magnet 54 and the rotating magnetic field of the stator 12. Further, the rotor winding generation torque Tcoil is a torque due to a current induced in the rotor windings 18n and 18s when the spatial harmonic component of the magnetomotive force generated by the stator 12 acts on the rotor windings 18n and 18s. The torque generated by attraction and repulsion, which is an electromagnetic interaction between the magnetic field generated by each magnetic pole portion 60 and the rotating magnetic field of the stator 12.

  Further, in the present configuration example, the permanent magnets 54 are arranged at a plurality of locations in the circumferential direction of the rotor 14, and the magnetization directions are made different between the permanent magnets 54 adjacent in the circumferential direction. The rotor windings 18n and 18s are arranged at positions corresponding to the permanent magnet 54 in the circumferential direction of the rotor 14, and the magnetization direction of each permanent magnet 54 and the magnetic pole corresponding to the circumferential direction of the rotor 14 with respect to each permanent magnet 54 are arranged. The magnetization direction of the portion 60 is matched. For this reason, the permanent magnet generation torque Tmg generated by the permanent magnet 54 and the rotor winding generation torque Tcoil generated by the induced current flowing through the rotor windings 18n and 18s have the same phase of the current advance angle. The maximum torque is obtained at the phase (for example, 0 °). Further, the permanent magnet generation torque Tmg and the rotor winding generation torque Tcoil become the minimum torque in another one phase (for example, 180 °) of the same phase of the current advance angle. Further, the reluctance torque Tre is minimized when the current advance angle is 45 °, for example, and is minimized when the current advance angle is 135 °. As a result, the total torque of the rotating electrical machine 10 becomes maximum near 30 ° and becomes minimum near 150 °. In addition, each such torque has the same torque-current advance characteristic regardless of the rotation direction of the rotor 14.

  According to the rotating electrical machine 10 of this configuration example, the torque of the rotating electrical machine 10 can be effectively increased. That is, since the rotor windings 18n and 18s are arranged in d-axis magnetic paths with low inductance located at a plurality of locations in the circumferential direction of the rotor 14, the current phase-torque characteristics are the same regardless of the rotation direction of the rotor 14, Moreover, the maximum value of the torque is increased, and the torque can be effectively increased. For example, when the power running torque is increased, the rotor 14 is rotated forward (when the rotor 14 rotates in the direction of arrow α in FIG. 24) and the rotor 14 is rotated backward (when the rotor 14 rotates in the direction of arrow β in FIG. 24). In both cases, the power running torque can be increased. Further, when increasing the regenerative torque, it is possible to increase the regenerative torque both when the rotor 14 is rotating forward and when the rotor 14 is rotating reversely. Therefore, it is possible to realize the rotating electrical machine 10 that can obtain a high torque in both the forward and reverse rotations of the rotor 14.

  In addition, the permanent magnets 54 magnetized in the radial direction of the rotor 14 are arranged at a plurality of locations in the circumferential direction of the rotor 14, and the magnetizing directions are made different between the permanent magnets 54 adjacent in the circumferential direction. The rotor windings 18n and 18s are arranged at a plurality of positions at positions corresponding to the circumferential direction of the rotor 14 with respect to the plurality of permanent magnets 54, and the magnetization direction of the permanent magnet 54 and the circumferential direction of the rotor 14 with respect to the permanent magnet 54 are arranged. The magnetization directions of the magnetic pole portions 60 that coincide are matched with each other. For this reason, the permanent magnet generation torque Tmg generated by the permanent magnet 54 and the rotor winding generation torque Tcoil generated by the induced current flowing in the rotor windings 18n and 18s are the same phase of the current advance angle and the maximum torque. Become. That is, due to the induced current in the rotor windings 18n and 18s, the rotor windings 18n and 18s function equivalently as electromagnets, and the magnetic flux linked to each permanent magnet 54 increases, and the torque of the rotating electrical machine 10 correspondingly increases. Will increase. For this reason, the torque of the rotating electrical machine 10 can be increased more effectively, and the torque characteristics are the same regardless of the rotation direction of the rotor 14.

  Moreover, since the magnetic flux fluctuation in each permanent magnet 54 is suppressed by the induced current flowing through the rotor windings 18n and 18s, the eddy current loss in each permanent magnet 54 can be suppressed, and the heat generation of the magnet can be reduced. As a result, eddy current loss in each permanent magnet 54 is suppressed, and heat generation from the magnet can be reduced.

  The rotor windings 18n and 18s are wound around the rotor 14 at a plurality of locations in the circumferential direction with short-pitch windings, and the induced current generated in the rotor windings 18n and 18s due to the induced electromotive force is rectified by the diodes 21n and 21s. . For this reason, the rotor windings 18n, 18s are not provided in the stator 12 with a type of winding other than the stator windings 28u, 28v, 28w, and the rotor 14 with a type of winding other than the rotor windings 18n, 18s. Inductive electromotive force due to harmonic components can be efficiently generated, and the winding structure of the rotating electrical machine 10 can be simplified. When the rotor windings 18n and 18s are arranged in the d-axis magnetic path as in this configuration example and the following configuration example, the rotating electrical machine is controlled by vector control by setting the d-axis and q-axis current command values. In this case, by controlling so as to generate a pulse current at a predetermined frequency set in advance in the d-axis current command value, similarly to the embodiment whose experimental results are shown in FIGS. Torque can be improved.

  FIG. 25 is a schematic diagram corresponding to FIG. 24 in another configuration example. In the present configuration example, among the plurality of rotor windings 18n and 18s, some of the rotor windings 18n arranged every other in the circumferential direction of the rotor 14 are electrically connected in series and one in the circumferential direction. The remaining rotor windings 18s arranged at intervals are electrically connected in series. That is, the rotor windings 18n (or 18s) wound around the magnetic pole portion 60 functioning as a magnet magnetized in the same direction are electrically connected in series. Further, the rotor windings 18n and 18s wound around the magnetic pole portion 60 adjacent in the circumferential direction of the rotor 14 are electrically separated. Then, two sets of rotor winding circuits 62a and 62b that are electrically separated from each other are configured by a circuit including the rotor windings 18n (or 18s) that are electrically connected to each other. That is, the rotor windings 18n and 18s are wound around the magnetic pole part 60 having the same magnetic characteristics and are electrically connected.

  Further, the two sets of rotor winding circuits 62a and 62b are rectifying elements, and diodes 21n and 21s having different polarities are connected in series to every other rotor winding 18n and 18s, respectively. The direction of the current flowing through the rotor winding circuits 62a and 62b is rectified in one direction. Of the two sets of rotor winding circuits 62a and 62b, the current flowing through one rotor winding circuit 62a and the current flowing through the other rotor winding circuit 62b are opposite to each other. About another structure and effect | action, it is the same as that of the structural example shown to said FIG.

  FIG. 26 is a schematic diagram corresponding to FIG. 24 in another configuration example. In the rotor 14 constituting the rotating electric machine of this configuration example, the permanent magnet 54 (see FIG. 25) provided in the rotor 14 is omitted in the configuration example shown in FIG. Further, the rotor core 16 has a configuration in which salient poles 64 projecting in the radial direction are provided at a plurality of circumferential positions on the outer peripheral surface, and each rotor winding 18n, 18s is disposed between the salient poles 64 adjacent in the circumferential direction of the rotor 14. Is arranged. That is, the rotor windings 18n and 18s are arranged in an air-core state in which the inside is a space portion. Further, a portion between the rotor windings 18n and 18s in the circumferential direction of the rotor 14 protrudes toward the stator 12 (see FIG. 23), and the rotor core 16 has a magnetic salient pole characteristic.

  In the case of such a rotor 14, the magnetic path that coincides with the salient pole 64 in the circumferential direction of the rotor 14 is a q-axis magnetic path with high inductance, and the position where the inductance deviates from the salient pole 64 in the circumferential direction of the rotor 14 It becomes a low d-axis magnetic path. The rotor windings 18n and 18s are arranged in the d-axis magnetic path.

  In such a configuration example, unlike the configuration examples of FIGS. 23 to 25 described above, the permanent magnet 54 (see FIG. 25) is not disposed on the rotor 14, but the torque of the rotating electrical machine is independent of the rotation direction of the rotor 14. Can be increased. That is, since the rotor windings 18n and 18s are arranged in d-axis magnetic paths with low inductance located at a plurality of locations in the circumferential direction of the rotor 14, the current phase-torque characteristics are the same regardless of the rotation direction of the rotor 14, Moreover, the maximum value of the torque is increased, and the torque can be effectively increased. For example, when the power running torque is increased, the power running torque can be increased both when the rotor 14 is rotating forward and when it is rotating in reverse. Further, when increasing the regenerative torque, it is possible to increase the regenerative torque both when the rotor 14 is rotating forward and when it is rotating in reverse. Therefore, it is possible to realize a rotating electrical machine that can obtain a high torque in both forward and reverse rotations of the rotor 14. About another structure and effect | action, it is the same as that of the structural example of said 23-24 or the structural example of FIG.

  FIG. 27 is a schematic diagram corresponding to FIG. 24 in another configuration example. Similarly to the case of the configuration example shown in FIG. 26, the rotor 14 constituting the rotary electric machine of this configuration example is not provided with the permanent magnet 54 (see FIG. 25 and the like). In this configuration example, the magnetic resistance of the rotor 14 is changed with respect to the rotation direction by forming a slit 48 that is a gap portion inside the rotor core 16 that constitutes the rotor 14. That is, a plurality of slits 48 extending in the axial direction with a substantially U-shaped cross section and opening radially outward are disposed at a plurality of circumferential positions of the rotor core 16 at intervals in the radial direction of the rotor 14. And the magnetic path of the position which corresponds to the circumferential center position of the some slit 48 in the circumferential direction several places of the rotor core 16 is made into d axis | shaft magnetic path with low inductance, and the magnetic path between the slits 48 adjacent to the circumferential direction is used. The q-axis magnetic path has a high inductance. In addition, d-axis magnetic paths and q-axis magnetic paths are alternately arranged in the circumferential direction of the rotor 14.

  Further, the rotor windings 18n and 18s are arranged and wound around the magnetic pole portions 66 corresponding to the respective d-axis magnetic paths at a plurality of locations in the circumferential direction of the rotor 14. Further, the rotor windings 18n and 18s are short-circuited by diodes 21n and 21s having different polarities between the adjacent rotor windings 18n and 18s. The rotor windings 18n short-circuited by the diodes 21n and the rotor windings 18s short-circuited by the diodes 21s are alternately arranged in the circumferential direction of the rotor 14, and a plurality of magnetic poles generated by the current flowing through the rotor windings 18n and 18s. The magnetic characteristics of the portions 66 are alternately varied with respect to the circumferential direction of the rotor 14.

  In the case of this configuration example, the rotating magnetic field from the stator 12 (see FIG. 23) is linked to the rotor windings 18n and 18s, so that each rotor winding 18n and 18s is connected to each diode 21n and 21s. The rectified direct current flows, the magnetic pole portions 66 at a plurality of circumferential positions located in each d-axis magnetic path are magnetized, and each magnetic pole portion 66 functions as a magnet with a fixed magnetic pole. Further, the width of each rotor winding 18n, 18s in the circumferential direction of the rotor 14 is set to be shorter than the width corresponding to 180 ° in electrical angle of the rotor 14, and the rotor windings 18n, 18s are shortened to each magnetic pole part 60. It is wound with a clause winding. Preferably, the width of each rotor winding 18n, 18s in the circumferential direction is equal (or substantially equal) to a width corresponding to 90 ° in electrical angle of the rotor 14.

  Even in this configuration example, no permanent magnet is arranged on the rotor 14, but the torque of the rotating electrical machine can be increased regardless of the rotation direction of the rotor 14. That is, since the rotor windings 18n and 18s are arranged in d-axis magnetic paths with low inductance located at a plurality of locations in the circumferential direction of the rotor 14, the current phase-torque characteristics are the same regardless of the rotation direction of the rotor 14, Moreover, the maximum value of the torque is increased, and the torque can be effectively increased. Therefore, it is possible to realize a rotating electrical machine that can obtain a high torque in both forward and reverse rotations of the rotor 14. About another structure and effect | action, it is the same as that of the structural example of said 23-24.

  FIG. 28 is a schematic diagram corresponding to FIG. 24 in another configuration example. In the rotor 14 constituting the rotating electrical machine of this configuration example, the rotor core 16 does not have magnetic salient pole characteristics in the rotor 14 constituting the configuration example shown in FIGS. Permanent magnets 54 are fixed at a plurality of locations in the circumferential direction. Further, rotor windings 18n and 18s are wound around each permanent magnet 54. In the present configuration example, a plurality of portions in the circumferential direction of the rotor 14 that coincide with the permanent magnets 54 in the circumferential direction are used as magnetic pole portions. In addition, the rotor windings 18n and 18s are short-circuited by diodes 21n and 21s having different polarities between the adjacent rotor windings 18n and 18s. About another structure and effect | action, it is the same as that of the structural example of said 23-24.

  In the above description of the embodiments and configuration examples, the case of a radial type rotating electrical machine in which the stator 12 and the rotor 14 are disposed to face each other in the radial direction orthogonal to the rotation shaft 22 has been described. However, the rotary electric machine constituting the above embodiment may be an axial type rotary electric machine in which the stator 12 and the rotor 14 are arranged to face each other in the direction parallel to the rotary shaft 22 (rotary axis direction).

  As mentioned above, although the form for implementing this invention was demonstrated, this invention is not limited to such embodiment at all, and it can implement with a various form in the range which does not deviate from the summary of this invention. Of course.

  10 rotating electrical machines, 12 stators, 14 rotors, 16 rotor cores, 18, 18n, 18s rotor windings, 19 salient poles, 21, 21n, 21s diodes, 22 rotating shafts, 26 stator cores, 28u, 28v, 28w stator windings, 30 Teeth, 31 slots, 34 Rotating electrical machine drive system, 36 Inverter, 38 Control device, 40 Power storage device, 42 Switching unit, 44 Drive signal output means, 46 Position sensor, 48 Slit, 50 d-axis magnetic path portion, 52 q-axis magnetism Road portion, 54 permanent magnet, 56 magnetic pole part, 58 annular core part, 60 magnetic pole part, 62a, 62b rotor winding circuit, 64 salient pole, 66 magnetic pole part, 68 torque rotational speed acquisition means, 70 interphase voltage acquisition means, 72 Sine wave torque calculation means, 74 pulse superimposition condition determination means, 76 map storage Stage, 78 second pulse superposition condition determining means, 80, 80a current command generation unit, 82 current command synthesis unit, 84 voltage command drive signal generation unit, 86 voltage command generation unit, 88 pulse voltage command addition unit, 90 drive signal generation Department.

Claims (18)

In a rotating electrical machine drive system that drives a rotating electrical machine in which a stator and a rotor are arranged to face each other,
The stator is
A stator core having a plurality of slots formed at intervals in the circumferential direction around the rotor rotation axis, and a multi-phase stator winding wound in a concentrated manner on the stator core through the slot, the stator A rotating magnetic field with a frequency including harmonic components is generated by the alternating current flowing through the windings.
The rotor
The rotor core is disposed at a plurality of locations in the circumferential direction of the rotor core, connected to each rotor winding, and a rotor winding in which an induced electromotive force is generated by a rotating magnetic field including harmonic components generated by the stator, And a rectifying element that rectifies the current flowing through each rotor winding by the generation of the induced electromotive force, and magnetic characteristics of magnetic pole portions at a plurality of circumferential directions generated by the current flowing through each rotor winding are alternately arranged in the circumferential direction. The width of each rotor winding in the circumferential direction is smaller than 180 degrees in terms of the electrical angle of the stator current of each phase, and is proportional to the rotor speed when the stator current is constant. The line voltage (1) of the rotating electrical machine that increases as a result, or a value (Vd ² + Vq ² ) ¹ calculated from the d-axis voltage command value Vd and the q-axis voltage command value Vq used when the stator current is vector-controlled. ^{/ 2} Voltage relationship value between a 2) line is less than the threshold, or the first pulse superimposing requirement is satisfied is equal to or less than the threshold, and only if the second pulse superimposing requirement set in advance is satisfied, the pulse it is determined that superimposed condition is satisfied, so to superimpose a pulse current to the stator current flowing through the stator windings, comprising a switching unit for switching the pulse superimposing condition, the rotary electric machine to be driven regardless of the switching by the switching unit When the pulse current is not superimposed on the stator current, the characteristic line that defines the relationship between the torque of the rotating electrical machine and the rotational speed has a characteristic that the torque decreases at the lower rotational speed with the predetermined rotational speed as a boundary. A rotating electric machine drive system that is characterized. In the rotating electrical machine drive system according to claim 1,
The switching part
Torque rotational speed acquisition means for acquiring the required output torque required for the rotating electrical machine and the rotational speed of the rotating electrical machine;
A line voltage acquisition means for acquiring a line voltage related value from the voltage command value corresponding to the required output torque;
Sine wave torque calculating means for calculating a sine wave torque that can be generated by a sine wave current from the rotation speed and a current command value corresponding to the required output torque;
Comparing the required output torque with the calculated sine wave torque, whether the required output torque is greater than or equal to the sine wave torque or exceeds the sine wave torque is used as the second pulse superposition request condition, and the pulse superposition condition is A rotating electrical machine drive system comprising: determination means for determining establishment. In the rotating electrical machine drive system according to claim 1,
The switching part
Torque rotational speed acquisition means for acquiring the required output torque required for the rotating electrical machine and the rotational speed of the rotating electrical machine;
A line voltage acquisition means for acquiring a line voltage related value from the voltage command value corresponding to the required output torque;
The required output torque is obtained by superimposing the sine wave current on the sine wave current from the required output torque and the rotation speed, and the sine wave loss when the required output torque is obtained from the required output torque and the rotation speed. The pulse superposition condition is established by comparing the sine wave loss to the pulse superposition loss or exceeding the pulse superposition loss as the second pulse superposition requirement condition. A rotating electrical machine drive system comprising: determining means for determining whether or not In the rotating electrical machine drive system according to any one of claims 1 to 3,
Each rotor winding is connected to a rectifying element whose forward direction is reversed between adjacent rotor windings in the circumferential direction of the rotor, and each rectifying element rectifies the current flowing through the rotor winding by the generation of the induced electromotive force. By doing so, the phase of the current flowing through the rotor windings adjacent in the circumferential direction is alternately changed between the A phase and the B phase. The rotating electrical machine drive system according to any one of claims 1 to 4,
A rotating electrical machine drive system, wherein the width of each rotor winding in the circumferential direction of the rotor is substantially equal to a width corresponding to 90 ° in electrical angle. In the rotating electrical machine drive system according to any one of claims 1 to 5,
Each rotor winding is arranged in a q-axis magnetic path with high inductance located at a plurality of locations in the circumferential direction of the rotor,
The rotor core is a magnetic pole portion that functions as a magnet with a fixed magnetic pole by being magnetized according to the current rectified by the rectifying element flowing in the rotor winding, and is arranged at intervals from each other in the circumferential direction of the rotor A rotating electrical machine drive system comprising a plurality of magnetic pole portions. In the rotating electrical machine drive system according to claim 6,
In a rotor core, each magnetic pole portion protrudes toward a stator. In the rotating electrical machine drive system according to claim 6,
In a rotor core, a permanent magnet is disposed in a portion located between magnetic pole portions in the circumferential direction of the rotor. In the rotating electrical machine drive system according to claim 6,
The rotor core includes an annular core portion,
The rotor winding is wound around the annular core with toroidal winding,
A rotating electrical machine drive system, wherein each magnetic pole portion protrudes from an annular core portion toward a stator. In the rotating electrical machine drive system according to any one of claims 1 to 3,
All of each rotor winding is electrically connected,
The rectifying element is connected in common to each rotor winding, rectifies the current flowing through each rotor winding by the generation of the induced electromotive force, and reverses the winding direction of two rotor windings adjacent in the circumferential direction. Thus, the rotating electrical machine drive system is characterized in that the magnetic characteristics of the magnetic pole portions at a plurality of locations in the circumferential direction generated by the current flowing through each rotor winding are alternately changed. The rotating electrical machine drive system according to claim 10,
A rotating electrical machine drive system characterized in that the width of each rotor winding in the circumferential direction of the rotor is larger than a width corresponding to 90 ° in electrical angle and smaller than a width corresponding to 120 ° in electrical angle. In the rotating electrical machine drive system according to any one of claims 1 to 5,
A rotating electrical machine drive system, wherein each rotor winding is arranged in a d-axis magnetic path with low inductance located at a plurality of locations in the circumferential direction of the rotor. The rotating electrical machine drive system according to claim 12,
A rotating electrical machine drive system, wherein a permanent magnet is disposed in a portion of the rotor core that coincides with the magnetic pole portion in the circumferential direction of the rotor. The rotating electrical machine drive system according to claim 12,
In the rotor core, a portion located between the magnetic pole portions in the circumferential direction of the rotor is protruded toward the stator. The rotating electrical machine drive system according to any one of claims 1 to 14,
Each rotor winding is electrically separated from each other,
A rotating electrical machine drive system, wherein a rectifying element is provided for each electrically separated rotor winding. The rotating electrical machine drive system according to any one of claims 1 to 15,
The rotor windings arranged adjacent to each other in the circumferential direction of the rotor are electrically separated from each other,
A rectifying element is provided for each electrically separated rotor winding,
A rotating electrical machine drive system characterized in that the rotor windings arranged every other circumferential direction are electrically connected to each other. The rotating electrical machine drive system according to any one of claims 1 to 16,
When a pulse current is superimposed on the stator current, an inverter drive signal is generated so that the pulse current is superimposed on the stator current of each phase a predetermined number of times set for one cycle, and a drive signal is output. A rotating electrical machine drive system comprising output means. The rotating electrical machine drive system according to any one of claims 1 to 17,
When a pulse current is superimposed on the stator current, drive signal output means is provided for generating a drive signal for the inverter so that the pulse current is superimposed on the stator current of each phase at a set predetermined frequency, and outputting the drive signal. Rotating electric machine drive system characterized by

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