JP5623346B2 - Rotating electric machine drive system - Google Patents

Description

  The present invention relates to a rotating electrical machine drive system including an electromagnet-type rotating electrical machine in which a stator and a rotor are opposed to each other, a drive unit that drives the electromagnet-type rotating electrical machine, and a control unit that controls the drive unit.

  Conventionally, as described in Patent Document 1, an electromagnetic rotating electrical machine in which a stator and a rotor are arranged to face each other, and salient poles provided at a plurality of locations in the circumferential direction of the rotor, and wound around each salient pole. 2. Description of the Related Art There is known an electromagnet type rotating electrical machine that includes mounted rotor windings and includes a rotor winding that is divided from each other and a diode that is connected to each rotor winding. Each diode rectifies the current flowing in each rotor winding so that the magnetization direction is reversed between salient poles adjacent in the circumferential direction of the rotor. The stator includes teeth provided at a plurality of locations in the circumferential direction of the stator core. A plurality of stator windings are wound around the stator teeth in a concentrated manner. A rotating magnetic field that rotates in the circumferential direction is generated in the stator by passing a plurality of phases of alternating current through the stator windings of the plurality of phases. Then, an induction current is generated in the rotor winding by spatial harmonics that are harmonic components generated in the magnetomotive force distribution generated in the stator, and N and S poles are alternately formed in the salient poles in the circumferential direction of the rotor, Torque is generated in the rotor. At this time, a current rectified by each diode flows through each rotor winding, whereby each salient pole is magnetized to generate a magnet with a fixed magnetic pole.

  In such an electromagnet type rotating electrical machine, the salient pole interacts with the rotating magnetic field of the stator, and torque acts on the rotor. Further, the torque acting on the rotor can be efficiently increased by utilizing the harmonic component of the magnetic field formed by the stator. The electromagnet type rotating electrical machine is driven by a rotating electrical machine drive system. The rotating electrical machine drive system includes an inverter that is a drive unit and a control unit that controls the inverter.

JP 2009-112091 A

  Such a rotating electrical machine drive system has room for improvement from the viewpoint of exerting high performance on the electromagnet-type rotating electrical machine. For example, in a rotating electrical machine drive system, there is room for improvement in terms of increasing the induced current generated in the rotor winding for forming an electromagnet in the rotor, and there is room for improvement in terms of increasing the torque of the electromagnet-type rotating electrical machine. . In addition, the rotating electrical machine drive system has room for improvement in terms of suppressing torque fluctuations of the electromagnet-type rotating electrical machine.

  An object of the present invention is to make an electromagnet type rotary electric machine exhibit high performance in a rotary electric machine drive system including an electromagnet type rotary electric machine.

  The rotating electrical machine drive system according to the present invention employs the following means in order to achieve the above object.

A first rotating electrical machine drive system according to the present invention includes an electromagnet-type rotating electrical machine in which a stator and a rotor are arranged to face each other, a driving unit that drives the rotating electrical machine, and a control unit that controls the driving unit. In the rotating electrical machine drive system, the stator is wound in a concentrated manner around the stator core having a plurality of first slots spaced apart from each other in the circumferential direction around the rotor rotation axis. The rotor has a plurality of stator windings, and the rotor includes a rotor core having a plurality of second slots spaced apart from each other in a circumferential direction around the rotor rotation axis, and at least a part of the rotor core A rotor winding wound around a plurality of locations in the circumferential direction of the rotor core so as to be disposed in the slot, and connected to each rotor winding, and the magnetic characteristics of each rotor winding A plurality of rotor windings that alternately vary in the circumferential direction, and the magnetic characteristics of the magnetic pole portions at a plurality of circumferential directions generated by the current flowing in each rotor winding are alternately arranged in the circumferential direction. The controller is configured to provide a d-axis current command for causing a current to flow in the stator winding so as to generate a field magnetic flux in the same direction as a magnetic pole direction that is a winding central axis direction of the rotor winding. In addition, the increasing pulse current increasing in a pulse shape is superimposed, and the d-axis current at the start of the d-axis pulse superposition period in which the increasing pulse current is superimposed on the d-axis current command is made larger than the d-axis current at the end. Thus, by reducing the current increase amount during the d-axis pulse superposition period to be smaller than the current decrease amount , the d-axis current is gradually increased during the d-axis non-pulse superposition period when the increase pulse current is not superimposed on the d-axis current command. To supplement the d-axis current command. Correctly, in the at least part of the d-axis non-pulse superposition period, the induced current generated in the rotor winding is larger than the case where the increase amount and the decrease amount of the d-axis current command in the d-axis pulse superposition period are the same. D-axis pulse superimposing correction means for increasing The increased pulse current refers to a pulse current that rapidly increases in a pulse shape and then decreases rapidly (the same applies throughout the present specification and claims). Further, the pulse-like waveform of the increased pulse current may be a rectangular wave, a triangular wave, a trapezoidal wave, or a waveform formed in a protruding shape from a plurality of curves or straight lines. The “rotor core” refers to an integral member other than the rotor winding in the rotor, and includes, for example, a case where the rotor core body and magnet made of a magnetic material are included (in the entire specification and claims). The same shall apply.) Further, the “second slot” is not limited to a portion having a groove shape opened on the circumferential surface of the rotor core. For example, the “second slot” does not open on the circumferential surface of the rotor core and is formed so as to penetrate the rotor core in the axial direction. (Same throughout the specification and in the claims).

According to the rotating electrical machine drive system of the present invention, the electromagnet-type rotating electrical machine can exhibit high performance. Further, by gradually increasing the d-axis current in the d-axis non-pulse superposition period in which the increase pulse current is not superimposed, the amount of decrease when the increase pulse current is decreased in the d-axis pulse superposition period is increased. For this reason, the current increase time of the rotor current induced in the rotor winding is extended, and the current increase amount is increased. Therefore, the torque can be compensated for the amount of decrease in the torque of the rotating electrical machine during the d-axis non-pulse superposition period. The current imbalance at the start and end of the d-axis pulse superposition period can be compensated by the change in d-axis current during the d-axis non-pulse superposition period. For this reason, the torque of the rotating electrical machine of the electromagnet type can be increased, and the rotating electrical machine can exhibit high performance.

Further, a second rotating electrical machine drive system according to the present invention includes an electromagnet-type rotating electrical machine in which a stator and a rotor are opposed to each other, a drive unit that drives the rotating electrical machine, and a control unit that controls the drive unit. The stator includes a stator core having a plurality of first slots formed at intervals in a circumferential direction around a rotor rotation axis, and concentrated winding on the stator core through the first slot. A plurality of stator windings wound around the rotor, wherein the rotor has a plurality of second slots spaced apart from each other in a circumferential direction around the rotor rotation axis, and at least a part of the rotor core A rotor winding wound around a plurality of locations in the circumferential direction of the rotor core so as to be disposed in the second slot, and connected to each of the rotor windings; A plurality of rotor windings that alternately vary the circumferential direction in the circumferential direction, and the magnetic properties of the magnetic pole portions at a plurality of circumferential directions generated by the current flowing through the rotor windings in the circumferential direction. The control unit is configured to cause the stator winding to generate a field magnetic flux in a direction advanced by 90 degrees in electrical angle with respect to a magnetic pole direction that is a winding central axis direction of the rotor winding. Q-axis pulse superimposing means for superimposing a decreasing pulse current that decreases in a pulse shape on a q-axis current command for flowing current, and a field magnetic flux in the same direction as the magnetic pole direction that is the winding center axis direction of the rotor winding In a d-axis current command for causing a current to flow through the stator winding so as to generate a d-axis current at the start of a q-axis pulse superposition period in which a decrease pulse current is superimposed on a q-axis current command. Q axis power A rotary electric machine drive system and having a d-axis correction means for correcting the d-axis current command to gradually reduce the d-axis current command to not superimposed decreasing pulse current is a q-axis non-pulse overlap period. Note that the reduced pulse current means a pulse current that rapidly decreases in a pulse shape and then increases rapidly (the same applies throughout the present specification and claims). The pulse waveform of the reduced pulse current may be a rectangular wave, a triangular wave, a trapezoidal wave, or a waveform formed in a protruding shape from a plurality of curves or straight lines.

  According to the rotating electrical machine drive system of the present invention, the torque of the rotating electrical machine is reduced in the q-axis non-pulse superimposed period by gradually decreasing the d-axis current in the q-axis non-pulse superimposed period in which the reduced pulse current is not superimposed. Can be suppressed. For this reason, the torque fluctuation of the electromagnet-type rotary electric machine can be suppressed, and the rotary electric machine can exhibit high performance.

Also, in the rotating electrical machine drive system according to the present invention, preferably, each of the rotor windings is a rectification unit that is a rectifying unit such that the forward direction is reversed between the rotor windings adjacent in the circumferential direction of the rotor. Each rectifying element is connected to an element, and the current flowing in the rotor winding adjacent to the circumferential direction is rectified by rectifying the current flowing in the rotor winding by the generation of the induced electromotive force. It is different for each phase.

  In the rotating electrical machine drive system according to the present invention, preferably, the rectifying elements are a first rectifying element and a second rectifying element connected to the corresponding rotor winding, respectively, The second rectifier element rectifies the current flowing through the corresponding rotor winding by the generation of the induced electromotive force, and the magnetic pole portions at a plurality of positions in the circumferential direction generated by the current flowing through the rotor windings. Magnetic characteristics are alternately varied in the circumferential direction.

In the rotating electrical machine drive system according to the present invention, preferably, the rotor has a circumferential width of rotor teeth provided between the rotor slots arranged in the circumferential direction corresponding to an electrical angle of 180 °. is smaller than the width of the rotor winding, the are wound in Tanfushi around the respective rotor teeth.

  In the rotating electrical machine drive system according to the present invention, preferably, the width of each rotor winding in the circumferential direction of the rotor is equal to a width corresponding to 90 ° in electrical angle.

  According to the rotating electrical machine drive system of the present invention, the electromagnet-type rotating electrical machine can exhibit high performance.

It is a figure which shows schematic structure of the rotary electric machine drive system which concerns on embodiment of this invention. In embodiment of this invention, it is a schematic sectional drawing which shows a part of part which the stator and rotor oppose. It is the A section enlarged view of FIG. In embodiment of this invention, it is a schematic diagram which shows a mode that the magnetic flux produced | generated by the induced current which flows into a rotor coil | winding flows in a rotor. In an embodiment of the present invention, it is a figure showing an equivalent circuit of a connection circuit of two rotor windings wound around a main salient pole adjacent in the circumferential direction of a rotor. It is a figure corresponding to Drawing 5A which shows another example which reduced the number of diodes connected to a rotor winding. In embodiment of this invention, it is a schematic diagram which shows a mode that a magnetic flux flows into a rotor from a stator, passing an auxiliary salient pole. In embodiment of this invention, it is a block diagram which shows the structure of a control apparatus. In an embodiment of the present invention, a d-axis current command (Id salient pole axis current component) and q-axis current command (Iq concave pole axis current component) corresponding to the stator current, and a rotor current (Irc) induced in the rotor winding ) And the torque of the rotating electrical machine. In embodiment of this invention, it is a schematic diagram which shows an example of a mode that a magnetic flux passes a stator and a rotor by d-axis current. In a rotating electrical machine control system of a comparative example, it is a diagram showing a temporal change of a d-axis current command (Id salient pole current component) corresponding to a stator current and a rotor current (Irc) induced in a rotor winding. . FIG. 3 is a diagram showing a result of calculating the amplitude of the interlinkage magnetic flux to the rotor winding while changing the width θ of the rotor winding in the circumferential direction in the rotating electrical machine of FIG. 2. In the first example of another example of the embodiment of the present invention, the increase pulse current is superimposed on the d-axis current command, and the d-axis current is gradually decreased in the d-axis non-pulse superposition period, corresponding to FIG. It is a figure to do. It is a figure which shows the structure of the control apparatus of the 2nd example of another example of embodiment of this invention. 8 corresponds to FIG. 8, showing a case where a reduced pulse current is superimposed on the q-axis current command and the d-axis current is gradually decreased in the q-axis non-pulse superimposed period in the second example of another example of the embodiment of the present invention. It is a figure to do. FIG. 5 is a schematic cross-sectional view showing a part of a portion where a stator and a rotor face each other in another configuration example of a rotating electrical machine that constitutes an embodiment of the present invention. It is the schematic which shows a part of part which the stator and rotor oppose in the other structural example of the rotary electric machine which comprises embodiment of this invention. It is a figure which shows a mode that the magnetic flux produced | generated by the induced current which flows into a rotor coil | winding flows in a rotor in the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention. It is the schematic which shows the rotor of the other structural example of the rotary electric machine which comprises embodiment of this invention.

  Hereinafter, embodiments of the present invention will be described with reference to the drawings. 1 to 9 and 11 are diagrams showing an embodiment of the present invention. FIG. 1 is a diagram showing a schematic configuration of a rotating electrical machine drive system according to the present embodiment. FIG. 2 is a schematic cross-sectional view showing a part of the facing portion between the stator and the rotor in the present embodiment. FIG. 3 is an enlarged view of a portion A in FIG. FIG. 4 is a schematic diagram showing how the magnetic flux generated by the induced current flowing in the rotor winding flows in the rotor in the present embodiment. As shown in FIG. 1, the rotating electrical machine drive system 34 of the present embodiment includes a rotating electrical machine 10 that is an electromagnet-type rotating electrical machine, an inverter 36 that is a drive unit that drives the rotating electrical machine 10, and a control unit that controls the inverter 36. , And a power storage device 40 as a power supply unit, and drives the rotating electrical machine 10. First, the rotating electrical machine 10 will be described. As shown in FIG. 2, the rotating electrical machine 10 that functions as an electric motor or a generator is disposed in a stator 12 fixed to a casing (not shown) and opposed to the stator 12 radially inward with a predetermined gap between the stator 12 and the stator 12. And a rotatable rotor 14. The “radial direction” means a radial direction orthogonal to the rotation center axis of the rotor (hereinafter, the meaning of “radial direction” is the same unless otherwise specified).

  The stator 12 includes a stator core 16 made of a magnetic material, and a plurality of phases (more specifically, for example, three phases of a U phase, a V phase, and a W phase) disposed on the stator core 16. 20w. A plurality of teeth 18, which are a plurality of first teeth protruding inward in the radial direction (toward the rotor 14), are disposed at a plurality of locations in the circumferential direction of the stator core 16, and slots that are first slots between the teeth 18. 22 is formed. The “circumferential direction” refers to a direction along a circle drawn around the rotation center axis of the rotor (hereinafter, the meaning of “circumferential direction” is the same unless otherwise specified).

  That is, a plurality of teeth 18 projecting radially inward (toward the rotor 14) are spaced apart from each other along the circumferential direction around the rotation center axis that is the rotation axis of the rotor 14 on the inner peripheral surface of the stator core 16. The slots 22 are formed between the teeth 18 at intervals in the circumferential direction. That is, a plurality of slots 22 are formed in the stator core 16 at intervals in the circumferential direction around the rotation axis of the rotor 14.

  The stator windings 20u, 20v, and 20w of each phase are wound around the teeth 18 of the stator core 16 through the slots 22 in a concentrated manner with short nodes. As described above, the stator windings 20u, 20v, and 20w are wound around the teeth 18 to form a magnetic pole. The teeth 18 arranged in the circumferential direction are magnetized by causing a plurality of phases of alternating current to flow through the plurality of stator windings 20u, 20v, 20w, and a rotating magnetic field that rotates in the circumferential direction is generated in the stator 12. Can do. The stator windings 20u, 20v, and 20w are not limited to the configuration in which the stator windings 20 are wound around the teeth 18 of the stator 12 as described above. It is also possible to generate a rotating magnetic field in the stator 12 by using a toroidal winding for winding the phase stator winding.

  The rotating magnetic field formed on the teeth 18 acts on the rotor 14 from the tip surface. In the example shown in FIG. 2, one pole pair is configured by three teeth 18 around which three-phase (U-phase, V-phase, W-phase) stator windings 20u, 20v, 20w are wound.

  On the other hand, the rotor 14 includes a rotor core 24 made of a magnetic material and a plurality of rotor windings 28n and 28s. There are a plurality of magnetic pole portions projecting outward in the radial direction (toward the stator 12) at a plurality of locations in the circumferential direction of the outer circumferential surface of the rotor core 24, the projecting portions, and the second teeth. The salient poles 26 are arranged at intervals from each other along the circumferential direction of the rotor core 24, and each main salient pole 26 faces the stator 12. The annular portion of the rotor core 24 and the plurality of main salient poles 26 are integrally provided by a magnetic material such as a laminate in which a plurality of magnetic steel plates are laminated. More specifically, with respect to the circumferential direction of the rotor 14, every other main salient pole 26 is wound with a plurality of first rotor windings 28n by concentrated winding, and the first rotor winding 28n is wound around the main salient pole 26. A plurality of second rotor windings 28s are wound around the other main salient poles 26 adjacent to each other in the circumferential direction every other main salient pole 26 by concentrated winding. The rotor 14 has a slot 29 (FIGS. 3 and 4) that is a second slot formed between the main salient poles 26 adjacent in the circumferential direction. That is, a plurality of slots 29 are formed in the rotor core 24 at intervals in the circumferential direction around the rotation axis of the rotor 14.

  Further, as shown in FIGS. 2 to 4, each first rotor winding 28 n includes a first induction winding 30 wound on the distal end side (the upper end side in FIGS. 2 to 4) of the main salient pole 26, And a first common winding 32 connected to one induction winding 30. The first common winding 32 is wound on the base side (the lower end side in FIGS. 2 to 4) with respect to the first induction winding 30 in the main salient pole 26 around which the first induction winding 30 is wound. Each of the second rotor windings 28s has a second induction winding wound around the tip of another main salient pole 26 adjacent to the main salient pole 26 around which the first rotor winding 28n is wound in the circumferential direction. 44 and a second common winding 46 connected to the second induction winding 44. The second common winding 46 is wound on the base side of the second induction winding 44 at the main salient pole 26 around which the second induction winding 44 is wound. 2 to 4, the induction windings 30 and 44 and the common windings 32 and 46 wound around each main salient pole 26 are respectively in the length direction around the main salient pole 26 (see FIG. 4 are arranged in an aligned winding in which a plurality of layers are aligned in the circumferential direction of the main salient pole 26 (left-right direction in FIG. 4). In addition, the induction windings 30 and 44 wound around the front end side of each main salient pole 26 may be configured to be wound around the main salient pole 26 a plurality of times, that is, a plurality of turns in a spiral shape.

  As shown in FIG. 4 and FIG. 5A, a first induction winding 30 wound around one main salient pole 26 in each set, with two main salient poles 26 adjacent in the circumferential direction of the rotor 14 as one set. And one end of the second induction winding 44 wound around another main salient pole 26 via the first diode 48 and the second diode 50 which are two magnetic characteristic adjusting units and are rectifying elements. Connected. That is, FIG. 5A shows an equivalent circuit of a connection circuit of two rotor windings 28n and 28s wound around main salient poles 26 adjacent to each other in the circumferential direction of the rotor 14 (FIG. 4) in the present embodiment. FIG. As shown in FIG. 5A, one end of the first induction winding 30 and the second induction winding 44 is connected at a connection point R via a first diode 48 and a second diode 50 whose forward directions are opposite to each other. ing.

  Also, as shown in FIGS. 4 and 5A, one end of the first common winding 32 wound around one main salient pole 26 in each group has a second common winding wound around another main salient pole 26. Connected to one end of line 46. The first common winding 32 and the second common winding 46 are connected in series to form a common winding set 52. Further, the other end of the first common winding 32 is connected to the connection point R, and the other end of the second common winding 46 is opposite to the connection point R of the first induction winding 30 and the second induction winding 44. Is connected to the other end. Further, the winding central axes of the induction windings 30 and 44 and the common windings 32 and 46 of the rotor windings 28n and 28s coincide with the radial direction of the rotor 14 (FIG. 2). The induction windings 30 and 44 and the common windings 32 and 46 are wound around the corresponding main salient poles 26 via an insulator (not shown) having electrical insulation made of resin or the like. You can also.

  In such a configuration, as will be described later, a rectified current flows through the first induction winding 30, the second induction winding 44, the first common winding 32, and the second common winding 46, thereby causing the main salient pole. 26 is magnetized and functions as a magnetic pole part. Returning to FIG. 2, the stator 12 generates a rotating magnetic field by passing an alternating current through the stator windings 20 u, 20 v, and 20 w, and this rotating magnetic field is not only a fundamental wave component magnetic field but also a fundamental wave. It contains a higher order harmonic component magnetic field.

  More specifically, the distribution of magnetomotive force that generates a rotating magnetic field in the stator 12 depends on the arrangement of the stator windings 20u, 20v, 20w of each phase and the shape of the stator core 16 by the teeth 18 and the slots 22 (basic It does not have a sinusoidal distribution (only of waves), but includes harmonic components. In particular, in the concentrated winding, the stator windings 20u, 20v, 20w of the respective phases do not overlap each other, so that the amplitude level of the harmonic component generated in the magnetomotive force distribution of the stator 12 increases. For example, when the stator windings 20u, 20v, and 20w are three-phase concentrated windings, the harmonic component is a temporal third-order component of the input electrical frequency, and the amplitude level of the spatial second-order component increases. The harmonic components generated in the magnetomotive force due to the arrangement of the stator windings 20u, 20v, 20w and the shape of the stator core 16 are called spatial harmonics.

  When a rotating magnetic field including this space-emphasized wave component acts on the rotor 14 from the stator 12, the fluctuation of the leakage magnetic flux leaking into the space between the main salient poles 26 of the rotor 14 is generated due to the fluctuation of the spatial harmonic magnetic flux. Thus, an induced electromotive force is generated in at least one of the induction windings 30 and 44 shown in FIG. In addition, the induction windings 30 and 44 near the stator 12 on the tip side of the main salient pole 26 mainly have a function of generating an induction current, and the common windings 32 and 46 far from the stator 12 are mainly used. The main salient pole 26 has a function of magnetizing, that is, functions as an electromagnet. Further, as understood from the equivalent circuit of FIG. 5A, the sum of the currents flowing through the induction windings 30 and 44 wound around the adjacent main salient poles 26 (FIGS. 2 to 4) is the common windings 32 and 46. The currents that flow through Further, since the adjacent common windings 32 and 46 are connected in series, the same effect can be obtained as when the number of turns is increased in both, and the magnetic flux flowing through each main salient pole 26 is kept the same. The current flowing through each common winding 32, 46 can be reduced.

  When an induced electromotive force is generated in each induction winding 30, 44, diodes 48, 50 are connected to the first induction winding 30, the second induction winding 44, the first common winding 32, and the second common winding 46. A direct current corresponding to the commutation direction flows, and the main salient pole 26 around which the rotor windings 28n and 28s are wound is magnetized, so that the main salient pole 26 functions as a magnetic pole portion which is a magnet with a fixed magnetic pole. . As shown in FIG. 4, the winding directions of the first rotor winding 28n and the second rotor winding 28s adjacent to each other in the circumferential direction are reversed, and the magnetization directions are reversed between the main salient poles 26 adjacent to each other in the circumferential direction. Become. In the illustrated example, an N pole is generated at the tip of the main salient pole 26 around which the first rotor winding 28n is wound, and an S pole is at the tip of the main salient pole 26 around which the second rotor winding 28s is wound. It is generated. For this reason, the N pole and the S pole are alternately arranged in the circumferential direction of the rotor 14. As described above, each of the diodes 48 and 50 (FIG. 4) has a magnetic characteristic generated in the plurality of main salient poles 26 by the induced electromotive force generated in the plurality of rotor windings 28n and 28s wound around the main salient poles 26. In the circumferential direction, they are alternately changed.

  The diodes 48 and 50 are connected to the corresponding induction windings 30 and 44, and the induction windings 30 and 44 are generated by the induction electromotive force generated by the rotating magnetic field including the spatial harmonics generated by the stator 12. By rectifying the current flowing in the rotor 14, the phases of the current flowing in the induction windings 30 and 44 adjacent to each other in the circumferential direction of the rotor 14 are alternately changed between the A phase and the B phase. The A phase generates an N pole on the tip side of the corresponding main salient pole 26, and the B phase generates an S pole on the tip side of the corresponding main salient pole 26.

  As shown in FIG. 2, the width θ of each induction winding 30, 44 and each common winding 32, 46 in the circumferential direction of the rotor 14 is shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14. The induction windings 30 and 44 and the common windings 32 and 46 are wound around the main salient pole 26 with a short-pitch winding. More preferably, the width θ of each induction winding 30, 44 and each common winding 32, 46 in the circumferential direction of the rotor 14 is equal to or substantially equal to a width corresponding to 90 ° in electrical angle of the rotor 14. Yes. The width θ of each induction winding 30, 44 and each common winding 32, 46 here is determined in consideration of the cross-sectional area of each induction winding 30, 44 and each common winding 32, 46. It can be represented by the center width of the cross section of the lines 30 and 44 and the common windings 32 and 46. That is, the width of each induction winding 30, 44 and each common winding 32, 46 is an average value of the width of the inner peripheral surface and the width of the outer peripheral surface of each induction winding 30, 44 and each common winding 32, 46. θ can be expressed. The electrical angle of the rotor 14 is represented by a value obtained by multiplying the mechanical angle of the rotor 14 by the number of pole pairs p of the rotor 14 (electrical angle = mechanical angle × p). Therefore, the width θ of each induction winding 30, 44 and each common winding 32, 46 in the circumferential direction is from the rotation center axis of the rotor 14 to each induction winding 30, 44 and each common winding 32, 46. When the distance is r, the following expression (1) is satisfied.

θ <π × r / p (1)
The reason why the width θ is regulated in this way will be described in detail later.

  In the present embodiment, the rotor 14 includes auxiliary salient poles 54 that protrude from both circumferential sides of the main salient poles 26 arranged at a plurality of locations in the circumferential direction. Auxiliary salient poles 54 extend substantially in the axial direction of each main salient pole 26 (the front and back directions in FIGS. 2 and 3) from the both circumferential sides of each main salient pole 26 in a direction inclined with respect to the circumferential direction. A projecting plate-like magnetic body. For example, in the illustrated example, the auxiliary salient poles 54 are inclined with respect to the circumferential direction so as to be radially outward of the rotor 14 toward the distal ends at the radial intermediate portions on both circumferential sides of each main salient pole 26. ing. The plurality of auxiliary salient poles 54 are arranged between the first induction winding 30 and the first common winding 32 and between the second induction winding 44 and the second common winding on both circumferential sides of the main salient pole 26. Projecting from each line 46. That is, the auxiliary salient pole 54 is magnetically connected to the main salient pole 26.

  Further, the two auxiliary salient poles 54 disposed in the same slot 29 are not directly coupled to each other in the slot 29, and the tip portions are separated from each other. Such an auxiliary salient pole 54 can be formed of the same magnetic material as the rotor core 24 and the main salient pole 26. For example, the rotor core 24, the main salient poles 26, and the auxiliary salient poles 54 can be integrally formed of a laminated body of magnetic steel plates.

  Of the rotor windings 28n and 28s wound around the main salient poles 26, the induction windings 30 and 44 and the common windings 32 and 46 are partitioned by the auxiliary salient poles 54 in the corresponding slots 29. Are separated. The induction windings 30 and 44 and the common windings 32 and 46 wound around the same main salient pole 26 are auxiliary salient poles such as one or both coil end sides (not shown) provided outside the axial end surface of the rotor core 24. They are connected to each other at a portion away from 54. The induction windings 30 and 44 and the common windings 32 and 46 can be formed of different materials. For example, each of the common windings 32 and 46 is formed of a conductive material such as a copper wire, and each of the induction windings 30 and 44 is made of a conductive material constituting the common windings 32 and 46 such as aluminum or aluminum alloy. Alternatively, it can be formed of another light conductive material. Further, as shown in FIG. 3, flanges 58 projecting on both sides in the circumferential direction are formed at the tip of each main salient pole 26 to prevent the induction windings 30 and 44 (see FIG. 2 for 44). You can also

  Such a rotating electrical machine 10 is driven by the rotating electrical machine drive system 34 of FIG. The power storage device 40 provided in the rotating electrical machine drive system 34 is provided as a direct current power source and is chargeable / dischargeable, and is configured by, for example, a secondary battery. The inverter 36 includes U-phase, V-phase, and W-phase three-phase arms Au, Av, and Aw, and each phase arm Au, Av, and Aw has two switching elements Sw connected in series. The switching element Sw is a transistor, an IGBT, or the like. Further, a diode Di is connected in antiparallel to each switching element Sw. Further, the midpoint of each arm Au, Av, Aw is connected to one end side of the corresponding phase stator windings 20u, 20v, 20w constituting the rotating electrical machine 10. In the stator windings 20u, 20v, 20w, stator windings of the same phase are connected in series with each other, and stator windings 20u, 20v, 20w of different phases are connected at a neutral point.

  Further, the positive electrode side and the negative electrode side of the power storage device 40 are respectively connected to the positive electrode side and the negative electrode side of the inverter 36, and a capacitor 56 is connected in parallel to the inverter 36 between the power storage device 40 and the inverter 36. Has been. The control device 38 calculates a torque target of the rotating electrical machine 10 according to an acceleration command signal input from, for example, an accelerator pedal sensor (not shown) of the vehicle, for example, and changes each according to a current command value according to the torque target or the like. The switching operation of the switching element Sw is controlled. The control device 38 includes a signal representing a current value detected by a current sensor 60 provided on the stator winding (for example, 20u, 20v) side of at least two phases of the three phases, and a rotation angle detection unit such as a resolver. A signal indicating the rotation angle of the rotor 14 of the rotating electrical machine 10 detected at 62 (FIG. 7) is input. The control device 38 includes a microcomputer having a CPU, a memory, and the like, and controls the torque of the rotating electrical machine 10 by controlling the switching of the switching element Sw of the inverter 36. The control device 38 can also be configured by a plurality of control devices divided for each function.

  Such a control device 38 converts the DC power from the power storage device 40 into three-phase AC power of U phase, V phase, and W phase by the switching operation of each switching element Sw constituting the inverter 36, and It is possible to supply electric power of a phase corresponding to each phase of the windings 20u, 20v, and 20w. The rotating electrical machine drive system 34 is used, for example, as a vehicular travel power generator mounted on a hybrid vehicle, a fuel cell vehicle, an electric vehicle, or the like that includes an engine and a travel motor as drive sources. Note that a DC / DC converter that is a voltage conversion unit may be connected between the power storage device 40 and the inverter 36 so that the voltage of the power storage device 40 can be boosted and supplied to the inverter 36.

  In the rotating electrical machine 10 described above, a rotating magnetic field (fundamental wave component) formed in the teeth 18 is applied to the rotor 14 by passing a three-phase alternating current through the three-phase stator windings 20u, 20v, and 20w. Accordingly, the main salient pole 26 is attracted to the rotating magnetic field of the teeth 18 so that the magnetic resistance of the rotor 14 is reduced. As a result, torque (reluctance torque) acts on the rotor 14.

  Further, when the rotating magnetic field including the spatial harmonic component formed in the teeth 18 is linked to the rotor windings 28n and 28s of the rotor 14, the rotor windings 28n and 28s have a rotor caused by the spatial harmonic component. The induced electromotive force is generated in each of the rotor windings 28n and 28s due to the magnetic flux fluctuation having a frequency different from the rotational frequency of 14 (the fundamental wave component of the rotating magnetic field). The current flowing through the rotor windings 28n and 28s along with the generation of the induced electromotive force is rectified by the diodes 48 and 50 to be unidirectional (direct current). The main salient poles 26 are magnetized in response to the direct current rectified by the diodes 48 and 50 flowing through the rotor windings 28n and 28s. It functions as a magnet fixed to one of the south poles. As described above, since the rectification directions of the currents of the rotor windings 28n and 28s by the diodes 48 and 50 are opposite to each other, the magnets generated in the main salient poles 26 have N and S poles alternately in the circumferential direction. It will be arranged.

  FIG. 6 is a schematic diagram illustrating a state in which magnetic flux flows from the stator 12 to the rotor 14 while passing through the auxiliary salient poles 54 in the present embodiment. For example, as shown in FIG. 6, the teeth 18 wound with the stator windings 20u, 20v, and 20w of the respective phases of the stator 12 are completely in the radial direction on the main salient poles 26 wound with the rotor windings 28n and 28s. Consider a case where (all) are not opposed to each other and at least one tooth 18 is opposed to a central position between two main salient poles 26 adjacent to each other in the circumferential direction of the rotor 14. Further, in this state, as indicated by a broken line arrow in FIG. 6, a case where a q-axis magnetic flux, which is a magnetic flux of a spatial second-order spatial harmonic, flows from the stator 12 to the rotor 14 as the magnetomotive force of the stator 12 is considered. . In this case, the presence of the auxiliary salient pole 54 induces a large amount of spatial harmonics from the teeth 18 (W-phase in FIG. 6) of the stator 12 to the main salient pole 26 via the auxiliary salient pole 54. Can be induced to another tooth (U-phase and V-phase in FIG. 6), and a large amount of magnetic flux can be linked to the induction windings 30 and 44. FIG. 6 shows a state corresponding to the phase angle at which the maximum q-axis magnetic flux flows from one tooth 18, and the direction and magnitude of the q-axis magnetic flux change in one electrical cycle. In FIG. 6, the broken line arrow α indicates the magnetic flux interlinking with the induction winding 30, and the broken arrow β indicates the magnetic flux interlinking with the induction winding 44. In this case, the second diode 50 (FIG. 4) is connected to the second induction winding 44 wound around the main salient pole 26, which is the S pole, and the second diode 50 defines the corresponding main salient pole 26 as the S pole. Current in the direction of For this reason, the magnetic flux tends to flow in the direction where the S pole becomes the N pole due to the q-axis magnetic flux on the main salient pole 26 on the S pole side, and the induced current tends to flow in the second induction winding 44 in a direction that prevents this. The flow is not hindered by the second diode 50. As a result, a magnetic flux caused by the induced current flows through the main salient pole 26 as indicated by a solid arrow in FIG. Further, in some cases, q-axis magnetic flux tends to flow from the teeth 18 of the stator 12 to the auxiliary salient pole 54 via the N-pole main salient pole 26, and the magnetic flux is directed in the direction in which the N-pole main salient pole 26 is the S pole. Is about to flow, an induced current tends to flow through the first induction winding 30 wound around the N-pole main salient pole 26 in a direction that prevents this. In this case, the first diode 48 (FIG. 4) connected to the first induction winding 30 causes a current to flow in the direction in which the corresponding main salient pole 26 is the N pole. In this case also, as indicated by the solid line arrow in FIG. For this reason, each main salient pole 26 is magnetized to N pole or S pole. As described above, since the auxiliary salient poles 54 protrude from both side surfaces of each main salient pole 26, there is no auxiliary salient pole 54, that is, a space between the main salient poles 26 adjacent in the circumferential direction in each slot 29. Compared with the case where there is only one, the maximum value of the amplitude of the magnetic flux interlinking with each induction winding 30 and 44 can be increased, so that the change of the interlinkage magnetic flux can be increased.

  Then, the magnetic field of each main salient pole 26 (magnet with a fixed magnetic pole) interacts with the rotating magnetic field (fundamental wave component) generated by the stator 12, thereby causing attraction and repulsion. Torque (torque corresponding to magnet torque) is also applied to the rotor 14 by electromagnetic interaction (attraction and repulsion) between the rotating magnetic field (fundamental wave component) generated by the stator 12 and the magnetic field of the main salient pole 26 (magnet). The rotor 14 is driven to rotate in synchronization with the rotating magnetic field (fundamental wave component) generated by the stator 12. As described above, the rotating electrical machine 10 can function as an electric motor that generates power (mechanical power) in the rotor 14 by using power supplied to the stator windings 20u, 20v, and 20w.

  Further, since the phases of the induced current flowing through the first induction winding 30 and the induced current flowing through the second induction winding 44 are out of phase, the first induction winding 30 and the second induction winding 44 are out of phase with each other. Half-wave rectification is generated. On the other hand, the first common winding 32 and the second common winding 46 have a current having the magnitude of the sum of the currents flowing through the first induction winding 30 and the second induction winding 44. For example, a large direct current flows continuously. For this reason, it becomes easy to form a magnetic pole in each main salient pole 26, and the torque of the rotor 14 can be increased.

  In addition, according to the rotating electrical machine 10 of the present embodiment, the rotor 14 protrudes from the circumferential side surface of each main salient pole 26 and includes the auxiliary salient pole 54 having magnetism, so that it is included in the rotating magnetic field generated by the stator 12. Thus, the spatial harmonics that are the harmonic components interlinking with the rotor windings 28n and 28s, for example, the spatial secondary harmonic components that are the third order of time, can be effectively increased by the auxiliary salient poles 54. For example, many magnetic fluxes of harmonic components of the magnetomotive force distribution generated in the stator 12 are guided from the teeth 18 of the stator 12 to the main salient poles 26 via the auxiliary salient poles 54, and are transferred to the rotor windings 28n and 28s. Many magnetic fluxes can be linked. It is also possible to induce a large amount of magnetic flux of higher harmonic components from the tooth 18 to the auxiliary salient pole 54 via the main salient pole 26 and to link a lot of magnetic flux to the rotor windings 28n and 28s. Therefore, the change in the magnetic flux density of the magnetic flux interlinking with the rotor windings 28n and 28s can be increased, the induced current induced in the rotor windings 28n and 28s can be increased, and the electromagnet formed on the main salient pole 26. The magnetic force of the magnetic pole can be increased. For this reason, the torque of the rotating electrical machine 10 can be improved without increasing the rotor magnetic force and increasing the size of the rotating electrical machine 10. Further, since a desired torque can be obtained even if the stator current passed through the stator windings 20u, 20v, and 20w is reduced, copper loss can be reduced and efficiency can be improved. As a result, the torque and efficiency of the rotating electrical machine 10 can be improved.

  Further, the control device 38 provided in the rotating electrical machine drive system 34 of FIG. 1 generates a field magnetic flux in the same direction as the magnetic pole direction that is the winding central axis direction of the rotor windings 28n and 28s (FIG. 2). A d-axis pulse that superimposes an increasing pulse current that is increased in a pulse shape on a d-axis current command for causing current to flow through the windings 20u, 20v, and 20w, and that corrects the d-axis current command outside the overlapping period of the increasing pulse current. Superposition correcting means 64 (FIG. 7) is provided. This will be described in detail with reference to FIG. FIG. 7 is a diagram illustrating a configuration of an inverter control unit in the control device 38. The control device 38 includes a current command calculation unit (not shown), a d-axis pulse superimposition correction unit 64, subtraction units 66 and 68, PI calculation units 70 and 72, a three-phase / two-phase conversion unit 74, a two-phase / A three-phase converter 76, a rotation angle detector 62, a PWM signal generator and a gate circuit (not shown) are included.

  The current command calculation unit corresponds to the d-axis and q-axis current command values according to the torque command value of the rotating electrical machine 10 calculated according to the acceleration instruction input from the user according to a table created in advance. Id * and Iq * are calculated. Here, the d-axis refers to the magnetic pole direction that is the winding central axis direction of the rotor windings 28n and 28s with respect to the circumferential direction of the rotating electrical machine 10, and the q-axis is a direction advanced by 90 degrees in electrical angle with respect to the d-axis. Say. For example, when the rotation direction of the rotor 14 is defined as shown in FIG. 2 above, the d-axis direction and the q-axis direction are defined by the relationship shown by the arrows in FIG. The current command values Id * and Iq * are a d-axis current command value that is a command value for the d-axis current component and a q-axis current command value that is a command value for the q-axis current component, respectively. Using such d-axis and q-axis, the current flowing through the stator windings 20u, 20v, and 20w can be determined by vector control.

  As shown in FIG. 7, the three-phase / two-phase conversion unit 74 includes the rotation angle θ of the rotating electrical machine 10 detected by the rotation angle detecting unit 62 provided in the rotating electrical machine 10 and 2 detected by the current sensor 60. A d-axis current value Id and a q-axis current value Iq, which are two-phase currents, are calculated from the phase currents (for example, V-phase and W-phase currents Iv and Iw). The reason why only the two-phase current is detected by the current sensor 60 is that the sum of the two-phase currents is 0, so that the one-phase current can be obtained by calculation. However, the U-phase, V-phase, and W-phase currents can be detected, and the d-axis current value Id and the q-axis current value Iq can be calculated from the current values.

  The d-axis pulse superimposing correction means 64 has a d-axis pulse generation correction unit 78 that generates an increased pulse current to be superimposed on the d-axis current command and calculates a correction amount of the d-axis current command. FIG. 8 shows a d-axis current command (Id salient pole axis current component) and q-axis current command (Iq concave pole axis current component) corresponding to the stator current, and rotor windings 28n and 28s (FIG. 2). FIG. 6 is a diagram showing a temporal change in the rotor current (Irc) induced by) and the torque of the rotating electrical machine 10 (FIG. 2). In the following description, the same elements as those shown in FIGS. The “Irc rotor current” shown in FIG. 8 is an induced current flowing through each common winding 32 and 46 (the same applies to FIGS. 10, 12 and 14 described later). As shown in FIG. 8, the d-axis pulse generation correction unit 78 generates a pulse current to be superimposed on the d-axis current command value and calculates a correction amount. That is, the d-axis pulse generation correction unit 78 generates an increased pulse current that increases in a pulse shape, that is, increases rapidly and then decreases rapidly. The “Id salient pole current component” in FIG. 8 is the superposed d-axis current command value after the pulse current is superimposed on the d-axis current command and corrected by the correction amount.

  In this case, the current increase amount Wu is made smaller than the current decrease amount Wd during the d-axis pulse superposition period Tpd in which the increase pulse current is superimposed (Wu <Wd). Along with this, the d-axis pulse generation correction unit 78 calculates a correction amount that gradually increases the d-axis current command in the d-axis non-pulse superposition period Tnpd in which the increase pulse current is not superimposed on the d-axis current command. . The increased pulse current and the correction amount generated by the d-axis pulse generation correction unit 78 are superimposed on the d-axis current command Id * of FIG. 7 by the adding unit, that is, added, and the superimposed d-axis current command value Idsum * Is generated. In this case, the increase pulse current is superimposed on the d-axis current command value Id * at a constant period. Next, the superposed d-axis current command value Idsum * is output to the corresponding subtracting unit 66. Therefore, the d-axis pulse superimposing correction unit 64 reduces the current increase amount Wu in the d-axis current during the d-axis pulse superimposition period Tpd to be smaller than the current decrease amount Wd, so that after the superimposition in the d-axis non-pulse superimposition period Tnpd. The d-axis current command Id * is corrected so as to gradually increase the Id salient pole shaft current component that is the d-axis current command value Idsum *.

  Further, the subtracting unit 66 obtains a deviation δId between the superposed d-axis current command value Idsum * and the d-axis current Id converted by the three-phase / 2-phase converting unit 74 and obtains a PI calculation unit 70 corresponding to the d-axis. The deviation δId is input to.

  The subtractor 68 corresponding to the q axis obtains a deviation δIq between the q axis current command value Iq * and the q axis current Iq converted by the three-phase / 2-phase converter 74, and PI corresponding to the q axis. The deviation δIq is input to the calculation unit 72. The q-axis current command value Iq * is a constant value calculated corresponding to the torque command. The PI calculation units 70 and 72 calculate the control deviation by performing PI calculation with a predetermined gain for the deviations δId and δIq input thereto, respectively, and the d-axis voltage command value Vd * and the q-axis voltage command value according to the control deviation. Vq * is calculated.

  The two-phase / three-phase conversion unit 76 is a 1.5 control cycle obtained from the rotation angle θ of the rotating electrical machine 10 based on the voltage command values Vd * and Vq * input from the PI calculation units 70 and 72. The prediction angle predicted to be positioned later is converted into three-phase voltage command values Vu, Vv, and Vw of U phase, V phase, and W phase. The voltage command values Vu, Vv, Vw are converted into PWM signals by a PWM signal generator (not shown), and the PWM signal is output to a gate circuit (not shown). The gate circuit controls on / off of the switching element Sw by selecting the switching element Sw to which the control signal is applied. As described above, the control device 38 converts the stator current flowing through the stator windings 20u, 20v, and 20w into the dq axis coordinate system into the d axis current component and the q axis current component, and performs the target by vector control including feedback control. The inverter 36 is controlled so that a stator current of each phase corresponding to the torque is obtained.

  Since the control device 38 is configured in this way, as shown in FIG. 8, a rotor current that is an induced current is generated in each of the common windings 32 and 46 that are the rotor windings 28n and 28s. In this case, in the d-axis pulse superposition period Tpd, the d-axis current increases rapidly and then decreases rapidly. As a reaction, the rotor current decreases rapidly and then increases rapidly. As described above, since the increase amount Wu of the d-axis current command is smaller than the decrease amount Wd, the increase amount is larger than the decrease amount in the rotor current. Further, since the d-axis current gradually increases in the d-axis non-pulse superposition period Tnpd, as a reaction, the rotor current gradually decreases in the d-axis non-pulse superposition period Tnpd, but the rotor current in the d-axis pulse superposition period Tpd. As the increase amount increases, the absolute amount of the rotor current in the d-axis non-pulse superposition period Tnpd increases. A broken line α in FIG. 8 indicates a rotor current in a comparative example of FIG. 10 described later. In the comparative example, the increase amount and the decrease amount of the d-axis pulse superposition period Tpd are the same in the d-axis current. In this way, the d-axis pulse superimposing correction means 64 superimposes the increased pulse current on the d-axis current command, and also uses the induced current generated in the rotor windings 28n and 28s in at least part of the d-axis non-pulse superimposing period Tnpd. The d-axis current command Id * is corrected so as to increase a certain rotor current.

  The change of the rotor current in the d-axis pulse superposition period Tpd will be described in more detail with reference to FIG. FIG. 9 is a schematic diagram showing an example of how the magnetic flux passes through the stator 12 and the rotor 14 by the d-axis current in the present embodiment. As indicated by a solid arrow in FIG. 9, when the d-axis current rises rapidly, which is the first period of the d-axis pulse superposition period Tpd, the d-axis current causes the main collision of the S pole of the rotor 14 from one tooth 18. In some cases, the magnetic flux sequentially flows through the pole 26, the annular portion of the rotor core 24, and the main salient pole 26 of the N pole, and then flows into another tooth 18. In this case, the current flowing through the common windings 32 and 46 (FIG. 6) of the rotor windings 28n and 28s is rapidly reduced so as to prevent the flow of magnetic flux. In FIG. 9, auxiliary salient poles are omitted for simplification of description, the distinction between the induction winding and the common winding is omitted, and the rotor windings 28n and 28s are shown as being separated.

  On the other hand, as indicated by a broken line arrow in FIG. 9, when the d-axis current rapidly decreases, which is the latter stage of the d-axis pulse superposition period Tpd, the d-axis current apparently indicates the solid line arrow in FIG. 9. The magnetic flux changes so as to flow in the direction opposite to the direction. In this case, a magnetic flux flows in the direction of becoming the S pole at the N-pole main salient pole 26, and an induced current tends to flow through the rotor winding 28 n in a direction to prevent it, and at the S-pole main salient pole 26. Magnetic flux flows in the direction of becoming the N pole, and an induced current tends to flow through the rotor winding 28s in a direction that prevents the magnetic flux. For this reason, the current flowing through the common windings 32 and 46 of the rotor windings 28n and 28s rapidly increases in the directions of the arrows X and Y in FIG. 9 and the flow is not blocked by the diodes 48 and 50. In particular, as shown in FIG. 8, since the increase amount of the d-axis current is smaller than the decrease amount in the d-axis pulse superposition period Tpd, the rotor current flowing through the rotor windings 28n and 28s is increased, and the torque of the rotating electrical machine 10 is increased. Also increases. A broken line β in FIG. 8 indicates the torque of the rotating electrical machine in the comparative example of FIG. 10 described later, in which the increase amount and the decrease amount of the d-axis pulse superposition period Tpd are the same in the d-axis current. As shown in FIG. 8, the rotor current and the torque of the rotating electrical machine 10 gradually decrease due to the DC resistance component of the rotor windings 28n and 28s in the d-axis non-pulse overlapping period Tnpd.

  Note that the increased pulse current superimposed on the d-axis current command Id * is not limited to a triangular wave as shown in FIG. 8, but is a rectangular wave, a trapezoidal wave, a waveform formed in a protruding shape from a plurality of curves or straight lines. (The same applies to the case of the reduced pulse current superimposed on the q-axis current command Iq * described in another embodiment shown in FIG. 14 described later).

  According to such a rotating electrical machine drive system 34, by gradually increasing the d-axis current in the d-axis non-pulse superimposed period Tnpd in which the increased pulse current is not superimposed, the increased pulse current in the d-axis pulse superimposed period Tpd is increased. The decrease amount Wd at the time of decrease increases. For this reason, the current increase time of the rotor current induced in the rotor windings 28n and 28s increases, and the current increase amount Pu (FIG. 8) increases. Therefore, the torque can be sufficiently compensated for the amount of decrease in the torque of the rotating electrical machine 10 during the d-axis non-pulse superposition period Tnpd. The current imbalance at the start and end of the d-axis pulse superposition period Tpd can be compensated by the change of the d-axis current in the d-axis non-pulse superposition period Tnpd. In addition, it is not necessary to excessively increase the peak value when the increased pulse current increases with the d-axis current. As a result, the torque of the rotating electrical machine 10 that is an electromagnet type can be effectively increased, and the rotating electrical machine 10 can exhibit high performance. Further, by superimposing the increased pulse current on the d-axis current, it is possible to effectively increase the torque when the rotating electrical machine 10 rotates at a low speed or stops.

  On the other hand, FIG. 10 shows a d-axis current command (Id salient pole axis current component) corresponding to the stator current and the rotor current (Irc) induced in the rotor winding in the rotating electrical machine control system of the comparative example. It is a figure which shows the time change of. In the case of the comparative example of FIG. 10, the control unit applies an increased pulse current to the d-axis current command Id * at a constant period instead of the d-axis pulse superimposition correction unit 64 (FIG. 7) included in the above-described embodiment. D-axis pulse superimposing means (not shown) for superimposing is provided. In the comparative example, other configurations are the same as those in the above embodiment. For this reason, as shown in FIG. 10, in the Id salient pole current component that is the superimposed d-axis current command in which the increased pulse current is superimposed on the d-axis current command Id *, the d-axis pulse command period before and after the d-axis pulse superimposed period Tpd. The d-axis current matches. That is, the increase amount and the decrease amount of the d-axis current are the same in the d-axis pulse superposition period Tpd.

  Along with this, the rotor current, which is an induced current generated in the common winding of the rotor windings, rapidly decreases in the first half of the d-axis pulse superposition period Tpd and increases rapidly in the second half. However, in the d-axis non-pulse superimposition period Tnpd in which the increased pulse current is not superimposed on the d-axis current command Id *, the magnetic energy stored in the rotor winding is consumed due to the DC resistance component of the rotor winding, and the rotor The current gradually decreases. For this reason, in the comparative example, in the configuration in which the increased pulse current is superimposed on the d-axis current command Id *, there is room for improvement in terms of increasing the rotor current and increasing the torque of the rotating electrical machine. According to the present embodiment described above, such inconvenience can be solved, and the torque of the rotating electrical machine of the present embodiment indicated by the solid line γ in FIG. 8 can be increased more than the torque of the comparative example indicated by the broken line β in FIG. In addition, in the “Id salient pole axis current component” which is the d-axis current command after superimposition in FIG. 8, the increased pulse current rises from a positive value in the previous period and decreases to a negative value in the latter period. The entire axial current component can be shifted in the positive direction (upward in FIG. 8) or in the negative direction (downward in FIG. 8). For example, the increase pulse current may rise from 0 and decrease to a smaller value with a negative value.

  Further, in the present embodiment, in each rotor winding 28n, 28s shown in FIG. 1, the width θ in the circumferential direction of the rotor 14 is restricted as described in the above equation (1). For this reason, the induced electromotive force due to the spatial harmonics of the rotating magnetic field generated in the rotor windings 28n and 28s can be further increased. That is, the amplitude (variation width) of the interlinkage magnetic flux to the rotor windings 28n and 28s due to the spatial harmonics is affected by the width θ of the rotor windings 28n and 28s in the circumferential direction. Here, FIG. 11 shows a result of calculating the amplitude (variation width) of the interlinkage magnetic flux to the rotor windings 28n and 28s while changing the width θ of the rotor windings 28n and 28s in the circumferential direction. In FIG. 11, the coil width θ is shown in terms of electrical angle. As shown in FIG. 11, since the fluctuation width of the linkage flux to the rotor windings 28n and 28s increases as the coil width θ decreases from 180 °, the coil width θ is made smaller than 180 °. By setting the rotor windings 28n and 28s to short-pitch windings, it is possible to increase the amplitude of the interlinkage magnetic flux due to spatial harmonics compared to full-pitch windings.

  Therefore, in the rotating electrical machine 10 (FIG. 2), the width of each main salient pole 26 in the circumferential direction is made smaller than the width corresponding to 180 ° in electrical angle, and the rotor windings 28n and 28s are shorted to each main salient pole 26. By winding with the node winding, the induced electromotive force due to the spatial harmonics generated in the rotor windings 28n and 28s can be efficiently increased. As a result, the torque acting on the rotor 14 can be increased efficiently.

  Furthermore, as shown in FIG. 11, when the coil width θ is 90 °, the amplitude of the interlinkage magnetic flux due to the spatial harmonics is maximized. Therefore, in order to further increase the amplitude of the interlinkage magnetic flux to the rotor windings 28n and 28s due to the spatial harmonics, the width θ of each rotor winding 28n and 28s in the circumferential direction is 90 ° in terms of the electrical angle of the rotor 14. It is preferably equal (or nearly equal) to the corresponding width. Therefore, when the number of pole pairs of the rotor 14 is p and the distance from the rotation center axis of the rotor 14 to the rotor windings 28n and 28s is r, the width θ of each rotor winding 28n and 28s in the circumferential direction is It is preferable that the following expression (2) is satisfied (or substantially satisfied).

  θ = π × r / (2 × p) (2)

  By doing so, the induced electromotive force due to the spatial harmonics generated in the rotor windings 28n and 28s can be maximized, and the magnetic flux generated in each main salient pole 26 by the induced current can be increased most efficiently. Can do. As a result, the torque acting on the rotor 14 can be increased more efficiently. That is, when the width θ greatly exceeds the width corresponding to 90 °, the magnetomotive forces in the direction of canceling each other easily interlink with the rotor windings 28n and 28s, but smaller than the width corresponding to 90 °. Therefore, the possibility becomes low. However, if the width θ is greatly reduced from a width corresponding to 90 °, the magnitude of the magnetomotive force linked to the rotor windings 28n and 28s is greatly reduced. For this reason, such inconvenience can be prevented by setting the width θ to a width corresponding to about 90 °. For this reason, it is preferable that the width θ of each rotor winding 28n, 28s in the circumferential direction is substantially equal to a width corresponding to 90 ° in electrical angle.

  As described above, in the present embodiment, when the width θ of the rotor windings 28n and 28s in the circumferential direction of the rotor 14 is substantially equal to a width corresponding to 90 ° in electrical angle, the rotor windings 28n and 28s are generated. The induced electromotive force due to the spatial harmonics of the rotating magnetic field can be increased, and the magnetic flux of the main salient pole 26, which is the magnetic pole portion generated by the induced current flowing in each rotor winding 28n, 28s, is increased most efficiently. be able to. As a result, the torque acting on the rotor 14 can be increased more efficiently.

  In the present embodiment, the case has been described in which the control device 38 (FIG. 7) superimposes the increased pulse current on the d-axis current command Id *, but does not superimpose the pulse current on the q-axis current command Iq *. However, at the same time as the superposition of the increasing pulse current on the d-axis current command Id *, the control device 38 decreases the pulse current to the q-axis current command Iq *, that is, the decreasing pulse current that rapidly increases and then increases rapidly. It can also be superimposed.

  Further, in the present embodiment, as shown in FIG. 3, the auxiliary salient pole 54 is formed to protrude on the circumferential side surface of the main salient pole 26 in a direction inclined with respect to the circumferential direction. It can also be formed so as to protrude in the circumferential direction on both sides in the circumferential direction and bend in the radial direction at the intermediate portion. In addition, a wide portion having a larger width in the circumferential direction can be provided at the tip of the auxiliary salient pole 54.

  Further, in the present embodiment, auxiliary salient poles 54 are formed so as to protrude on both side surfaces of each main salient pole 26, arranged in each slot 29, and the tips of the auxiliary salient poles 54 adjacent to each other in the circumferential direction are separated from each other. Yes. However, the tips of the auxiliary salient poles 54 that are arranged in the slots 29 and are adjacent to each other in the circumferential direction can be connected in the slot 29.

  In the configuration shown in FIG. 4 and FIG. 5A described above, the two main salient poles 26 adjacent in the circumferential direction of the rotor 14 are regarded as one set, and each set is wound around one main salient pole 26. One end of one induction winding 30 and one end of a second induction winding 44 wound around another main salient pole 26 are connected via a first diode 48 and a second diode 50 which are two rectifier elements. Explained when to do. However, in this embodiment, it can also be configured as shown in FIG. 5B. FIG. 5B is a diagram corresponding to FIG. 5A, showing another example in which the number of diodes connected to the rotor winding is reduced. In another example shown in FIG. 5B, in the present embodiment, a plurality of first induction windings 30 wound around the distal end side of every other main salient pole 26 (see FIG. 6) in the circumferential direction that becomes the north pole of the rotor. Are connected in series to form a first induction winding set 118, and a plurality of second induction windings 44 wound around the distal end side of every other main salient pole 26 in the circumferential direction that becomes the S pole of the rotor. Are connected in series to form the second induction winding set 120. One end of the first induction winding set 118 and the second induction winding set 120 is connected at a connection point R via a first diode 48 and a second diode 50 whose forward directions are opposite to each other.

  Further, as shown in FIG. 5B, when the two main salient poles 26 (see FIG. 6) of the N pole and the S pole adjacent in the circumferential direction of the rotor are set as one set, the first common winding 32 in each set. The second common windings 46 are connected in series to form a common winding set 52, and all the common winding sets 52 related to all the main salient poles 26 are connected in series. Furthermore, among the plurality of common winding sets 52 connected in series, one end of the first common winding 32 of one common winding set 52 serving as one end is connected to the connection point R, and another common winding serving as the other end is connected. One end of the second common winding 46 of the wire set 52 is connected to the other end opposite to the connection point R of the first induction winding set 118 and the second induction winding set 120. In such a configuration, unlike the configurations shown in FIGS. 4 and 5A described above, the total number of diodes provided in the rotor can be reduced to two, that is, the first diode 48 and the second diode 50. Even in this case, auxiliary salient poles 54 (see FIG. 6) are formed on the side surfaces of the respective main salient poles 26, and the induction windings 30 and 44 are respectively provided in the radially outer and radially inner spaces partitioned by the auxiliary salient poles 54. And common windings 32, 46 can be arranged.

  FIG. 12 shows a case where an increase pulse current is superimposed on a d-axis current command and the d-axis current is gradually decreased in a d-axis non-pulse overlap period in the first example of another example of the embodiment of the present invention. It is a figure corresponding to FIG. In the first example of another example of FIG. 12, unlike the embodiment shown in FIGS. 1 to 9 described above, the purpose is not to increase the torque of the rotating electrical machine 10 (FIG. 2), but the torque of the rotating electrical machine 10 is increased. It aims to make it more stable. That is, as described in the comparative example of FIG. 10, the d-axis non-pulse superposition period Tnpd (FIG. 10) in which the increase pulse current is not superimposed by simply superimposing the increase pulse current on the d-axis current command Id *. The rotor current generated in the rotor winding gradually decreases due to the DC resistance component of the rotor winding. In this case, there is room for improvement from the viewpoint of increasing torque fluctuation of the rotating electrical machine and reducing vibration and noise. The first example of another example of FIG. 12 is considered for the purpose of eliminating such inconvenience. In the following description, the same elements as those in the embodiment shown in FIGS.

  For the above purpose, in the first example of another example of FIG. 12, in the embodiment shown in FIG. 7, the d-axis pulse superimposing correction unit 64 superimposes the increased pulse current on the d-axis current. By making the current increase amount Wu larger than the current decrease amount Wd in the d-axis pulse superposition period Tpd (Wu> Wd), the Id salient pole axis current which is the post-superimposition d-axis current command in the d-axis non-pulse superposition period Tnpd The d-axis current command Id * is corrected so as to gradually decrease the component. Therefore, as can be seen from the comparison of the Id salient pole axis current component in FIG. 12 and the embodiment shown in FIG. 8, in the example of FIG. The increase amount Wu becomes larger than the decrease amount Wd, and the d-axis current in the d-axis non-pulse superposition period Tnpd gradually decreases. For this reason, there is a possibility that the effect of increasing the rotor current by superimposing the increased pulse current on the d-axis current command and increasing the torque of the rotating electrical machine 10 may be smaller than in the case of the above-described embodiments of FIGS. However, the change in the rotor current can be reduced or eliminated in the d-axis non-pulse overlapping period Tnpd. That is, in the d-axis non-pulse superimposition period Tnpd, as the d-axis current decreases, the rotor current tends to increase as a reaction thereof, and thus the rotor current decreases due to the DC resistance component of the rotor winding. Is canceled out, and the change in the rotor current in the d-axis non-pulse superposition period Tnpd can be suppressed. For this reason, it can suppress that the torque of the rotary electric machine 10 reduces in d-axis non-pulse superimposition period Tnpd, for example, it can maintain substantially constant. As a result, torque fluctuation of the rotating electrical machine 10 that is an electromagnet type can be suppressed, and the driving force of the rotating electrical machine 10 can be stabilized, and vibration and noise can be suppressed. Therefore, the rotating electrical machine 10 can exhibit high performance. .

  In FIG. 12, the broken line α and the broken line β indicate the rotor current and the torque of the rotating electrical machine in the comparative example of FIG. 10 described above (the same applies to the case of FIG. 14 described later). As described above, since the d-axis pulse superimposing correction unit 64 gradually decreases the d-axis current command Id * in the d-axis non-pulse superimposing period Tnpd, at least part of the d-axis non-pulse superimposing period Tnpd The d-axis current command Id * is increased so as to increase the induced current generated in the rotor windings 28n and 28s (for example, in the later stage of the d-axis non-pulse superposition period Tnpd, which is the range indicated by the arrow Q in FIG. 12). Is corrected. For this reason, the torque of the rotating electrical machine 10 increases at least partly of the d-axis non-pulse superimposition period Tnpd (for example, in the latter period of the d-axis non-pulse superimposition period Tnpd, which is the range indicated by the arrow T in FIG. 12). . Other configurations and operations are the same as those of the embodiment shown in FIGS.

  FIG. 13 is a diagram illustrating a configuration of a control device of a second example of another example of the embodiment of the present invention. FIG. 14 is a diagram corresponding to FIG. 8, showing a case where a decrease pulse current is superimposed on a q-axis current command and a d-axis current is gradually decreased in a q-axis non-pulse overlap period in another second example. It is. In the second example of the other examples of FIGS. 13 to 14, the increased pulse current is not superimposed on the d-axis current command Id * in the first example of the other example of FIG. 12 described above, but is added to the q-axis current command Iq *. A decreasing pulse current that periodically decreases in a pulse shape, that is, rapidly decreases and then rapidly increases is superimposed. At the same time, the d-axis current command Id * is corrected so as to suppress the change in the rotor current in the q-axis non-pulse superimposed period Tnpq (FIG. 14) in which the reduced pulse current is not superimposed on the q-axis current command Iq *. Yes. For this purpose, as shown in FIG. 13, in a second example of another example, the control device 38 includes a d-axis correction unit 82 and a q-axis pulse superimposing unit 84. However, unlike the embodiments of FIGS. 1 to 9 described above, the d-axis pulse superimposing correction means 64 (FIG. 7) is not provided. Other configurations and operations are the same as those of the above-described embodiments of FIGS. In the following, the same elements as those in the embodiment shown in FIGS.

  The q-axis pulse superimposing means 84 periodically superimposes the decreasing pulse current on the q-axis current command. Further, as shown in FIG. 14, the d-axis correction unit 82 is configured to generate a q-axis pulse in which a decrease pulse current is superimposed on the q-axis current command Iq * (FIG. 7) in the d-axis current command Id * (FIG. 7). The d-axis current d1 at the start T1 of the superposition period Tpq is made smaller than the d-axis current d2 at the end T2 (d1 <d2), and the d-axis current is gradually decreased in the q-axis non-pulse superposition period Tnpq. The d-axis current command Id * is corrected. For example, as indicated by a solid line δ in “Id salient pole current component” in FIG. 14, the Id salient pole axis current component which is the corrected d axis current command in the q axis pulse superposition period Tpq is changed to the q axis non-pulse superposition period. It is decreased at the same slope as the d-axis current decreasing at Tnpq, and then increased rapidly. As a result, the d-axis current d1 at the start T1 of the q-axis pulse superposition period Tpq is smaller than the d-axis current d2 at the end T2. Note that, as indicated by a one-dot chain line η in FIG. 14, the q-axis pulse overlap period is increased by increasing the d-axis current substantially linearly from the start time T1 to the end time T2 of the q-axis pulse overlap period Tpq. The d-axis current at the start T1 of Tpq can be made smaller than the d-axis current at the end T2 (d1 <d2).

  In any case, by correcting the d-axis current command Id * in this way, the d-axis current gradually decreases in the q-axis non-pulse superposition period Tnpq. As the d-axis current gradually decreases in the q-axis non-pulse superimposition period Tnpq, the rotor current tends to increase as a reaction thereof. Therefore, the rotor windings 28n and 28s in the q-axis non-pulse superimposition period Tnpq The decrease in the rotor current due to the DC resistance component is canceled out, and the change in the rotor current can be reduced or eliminated. For this reason, it can suppress that the torque of the rotary electric machine 10 reduces in q-axis non-pulse superimposition period Tnpq, for example, can maintain substantially constant. As a result, as shown in FIG. 14, the torque fluctuation of the electromagnet-type rotating electrical machine 10 can be suppressed, and the rotating electrical machine can exhibit high performance. Other configurations and operations are the same as those of the embodiment shown in FIGS.

  Next, another configuration example of the rotating electrical machine that constitutes the rotating electrical machine drive system of the above embodiment will be described. As shown below, in the present invention, various configuration examples of rotating electric machines can be used.

  For example, FIG. 15 is a schematic cross-sectional view showing a part of a portion where the stator and the rotor face each other in another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the rotating electrical machine 10 having the configuration example of FIG. 15, an auxiliary pole 86 made of a magnetic material is provided between the main salient poles 26 adjacent to each other in the circumferential direction of the rotor 14. The auxiliary pole 86 is coupled to the distal end portion of a column portion 88 made of a non-magnetic material that protrudes in the radial direction from the circumferential central portion of each slot 29 on the outer peripheral surface of the rotor core 24. The base portion of the column portion 88 is coupled to the bottom portion of the slot 29 on the outer peripheral surface of the rotor core 24. The column part 88 is made of a magnetic material, and on the assumption that strength can be secured, the cross-sectional area of the column part 88 in the circumferential direction of the rotor 14 is sufficiently larger than the cross-sectional area in the circumferential direction of the auxiliary pole 86. It can also be made smaller.

  According to such a configuration, it is possible to easily form a magnetic path through which spatial harmonic components pass in a portion including the auxiliary pole 86, and a large amount of spatial harmonics included in the rotating magnetic field generated in the stator 12 passes through the auxiliary pole 86. Therefore, the magnetic flux fluctuation of the spatial harmonic can be increased. For this reason, the induced current generated in the rotor windings 28n and 28s can be increased to increase the torque of the rotating electrical machine 10. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11 or the other examples of FIGS.

  FIG. 16 is a schematic diagram showing a part of a portion where the stator and the rotor face each other in another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the above embodiment, the case where the induction windings 30 and 44 and the common windings 32 and 46 are wound around the main salient poles 26 of the rotor 14 has been described. On the other hand, in the rotating electric machine having the configuration example of FIG. 16, the rotor windings 90n and 90s are wound around the main salient poles 26, and the rotor windings are wound around every other main salient pole 26 in the circumferential direction. The wire 90n and the main salient pole 26 around which the rotor winding 90n is wound and another rotor winding 90s wound around another main salient pole 26 are electrically separated from each other. . In other words, the rotor 14 has a plurality of first rotor windings 90n wound around every other main salient pole 26 in the circumferential direction by concentrated winding, and is adjacent to the main salient pole 26 wound with the first rotor winding 90n. A plurality of second rotor windings 90 s are wound around each other main salient pole 26 in the circumferential direction every other main salient pole 26 by concentrated winding.

  Also, a second rotor winding circuit in which one first diode 48 is connected to a first rotor winding circuit 92n in which a plurality of first rotor windings 90n are connected in series, and a plurality of second rotor windings 90s are connected in series. One second diode 50 is connected to 92s. That is, the plurality of first rotor windings 90n arranged every other in the circumferential direction of the rotor 14 are electrically connected in series and connected endlessly, and a first diode is partly disposed therebetween. 48 is connected in series with each first rotor winding 90n to form a first rotor winding circuit 92n. Each first rotor winding 90n is wound around a main salient pole 26 that functions as the same magnetic pole (N pole).

  The plurality of second rotor windings 90s are electrically connected in series and are connected in an endless manner, and a second diode 50 is connected in series with each second rotor winding 90s in part between them. Thus, the second rotor winding circuit 92s is configured. Each second rotor winding 90s is wound around the main salient pole 26 that functions as the same magnetic pole (S pole). The rotor windings 90n and 90s wound around the main salient poles 26 adjacent to each other in the circumferential direction (where magnets having different magnetic poles are formed) are electrically separated from each other.

  Further, the current rectification directions of the rotor windings 90n and 90s by the diodes 48 and 50 are reversed so that the main salient poles 26 adjacent to each other in the circumferential direction of the rotor 14 have different magnetic poles. Yes. That is, the direction of the current flowing in the first rotor winding 90n and the second rotor winding 90s arranged adjacent to each other in the circumferential direction (rectification direction by the diodes 48 and 50), that is, the forward direction is opposite to each other. The diodes 48 and 50 are connected to the rotor windings 90n and 90s. The diodes 48 and 50 are connected to the rotor windings 90n and 90s in opposite directions.

  Each of the diodes 48 and 50 rectifies the current flowing through the corresponding rotor windings 90n and 90s by the generation of an induced electromotive force by a rotating magnetic field including spatial harmonics generated by the stator 12, so that the circumferential direction of the rotor 14 is increased. The phases of the currents flowing through the rotor windings 90n and 90s adjacent to each other are alternately made different between the A phase and the B phase. The diodes 48 and 50 independently rectify the current flowing through the corresponding rotor windings 90n and 90s by the generation of the induced electromotive force, and a plurality of circumferential directions generated by the current flowing through the rotor windings 90n and 90s. The magnetic characteristics of the main salient poles 26 are alternately changed in the circumferential direction. In this configuration, the number of diodes 48 and 50 can be reduced to two as a whole, and the winding structure of the rotor 14 can be simplified.

  In addition, the auxiliary salient poles 54 projecting on both sides in the circumferential direction of each main salient pole 26 divide the rotor windings 90n and 90s wound around each main salient pole 26 into the tip side and the root side. The tip side and the base side of the windings 90n and 90s are connected in series. Also in the configuration shown in FIG. 16, the rotating electrical machine 10 can exhibit high performance. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11 or the other examples of FIGS.

  In addition, as in another configuration example of the rotating electrical machine illustrated in FIG. 17, the first diode 48 or the second diode 50 is short-circuited for each of the rotor windings 90 n and 90 s wound around the main salient poles 26. You can also connect as you do. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11 or the other examples of FIGS.

  Further, as in the other configuration example of the rotating electrical machine 10 shown in FIG. 18, auxiliary protrusions that protrude from both circumferential sides of the salient poles 114 that are second teeth that protrude from a plurality of circumferential positions on the outer circumferential surface of the rotor core 24. The pole 54 (see FIGS. 2, 16, 17, etc.) can be eliminated. In this case, the torque of the rotating electrical machine 10 is inferior to that of the configuration example of FIG. 16 described above, but the rotating electrical machine 10 can exhibit high performance even in the configuration example of FIG. Other configurations and operations are the same as those in the configuration example of FIG.

  In the configuration example in which the rotor windings 90n and 90s wound around the main salient poles 26 adjacent in the circumferential direction are electrically separated from each other like the rotating electrical machine 10 in the configuration example of FIG. Only a part of the auxiliary salient pole 54, for example, only the auxiliary salient pole 54 arranged on one side in the circumferential direction with respect to the main salient pole 26 may be omitted. Although not shown, one first diode 48 or one second diode for each of the rotor windings 90n and 90s wound around the main salient poles 26 as in the configuration example of FIG. The auxiliary salient poles 54 can be partially or entirely eliminated by being connected so as to be short-circuited at 50.

  FIG. 19 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the configuration example of FIG. 19, a slit (gap) 94 that is a second slot is formed in the rotor core 24, and the magnetic resistance of the rotor 14 is changed according to the rotation direction. In the configuration example of FIG. 19, in the rotor core 24, the magnetic path in the central portion in the circumferential direction of the portion formed so as to arrange the plurality of slits 94 in the radial direction is the q-axis magnetic path portion 96, and the rotor windings 90 n and 90 s are arranged. The arranged magnetic path in the direction of the magnetic pole portion is a d-axis magnetic path portion 98. Slits 94 are formed so that the d-axis magnetic path portions 98 and the q-axis magnetic path portions 96 facing the stator 12 (see FIG. 2) are alternately arranged in the circumferential direction, and the d-axis magnetic path portions in the circumferential direction are formed. 98 is located between the q-axis magnetic path portions 96.

  Each rotor winding 90n, 90s passes through a slit 94 and is wound around a q-axis magnetic path portion 98 having a low magnetic resistance. In this case, the slits 94 are formed in the rotor core 24 at intervals in the circumferential direction around the rotating shaft 100 to which the rotor 14 is fixed, and the rotor windings 90n and 90s are partially arranged in the slit 94. As shown, the outer periphery of the rotor core 24 is wound around a plurality of locations in the circumferential direction. In the configuration example shown in FIG. 19, a rotating magnetic field including a spatial harmonic component formed by the stator 12 is linked to each rotor winding 90n, 90s, so that each diode 48, 50 is connected to each rotor winding 90n, 90s. As a result of the rectified direct current flowing and magnetizing each d-axis magnetic path portion 98, each d-axis magnetic path portion 98 functions as a magnet (magnetic pole portion) with a fixed magnetic pole. Further, the width of each d-axis magnetic path portion 98 in the circumferential direction (the width θ of each rotor winding 90n, 90s) is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, and the rotor windings 90n, 90n, By winding 90s around each d-axis magnetic path portion 98 with a short-pitch winding, it is possible to efficiently increase the induced electromotive force due to the spatial harmonics generated in the rotor windings 90n and 90s. Furthermore, in order to maximize the induced electromotive force due to the spatial harmonics generated in the rotor windings 90n and 90s, the width θ of each rotor winding 90n and 90s in the circumferential direction is set to 90 ° in terms of the electrical angle of the rotor 14. It is preferable to make it equal (or substantially equal) to the corresponding width. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11 or the other examples of FIGS.

  FIG. 20 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the configuration example of FIG. 20, the rotor core 24 includes a rotor core body 102 made of a magnetic material and a plurality of permanent magnets 104, and the permanent magnets 104 are disposed on the rotor core 24. In the configuration example of FIG. 20, a plurality of magnetic pole portions 106 that function as magnets with fixed magnetic poles are arranged to face the stator 12 (see FIG. 2) in a circumferentially spaced manner. The rotor windings 90n and 90s are wound around the rotor. In this case, slits 108 as second slots are formed at a plurality of locations in the circumferential direction of the rotor core 24, and the rotor windings 90 n and 90 s are arranged on the outer periphery of the rotor core 24 so that a part of each is disposed in the slit 108. It is wound around a plurality of locations in the circumferential direction. Each permanent magnet 104 is disposed opposite to the stator 12 at a portion located between the magnetic pole portions 106 in the circumferential direction. The permanent magnet 104 here may be embedded in the rotor core 24 or may be exposed on the surface (outer peripheral surface) of the rotor core 24. Also, the permanent magnet 104 can be arranged in a V shape inside the rotor core 24. In the configuration example of FIG. 20, a rotating magnetic field including a spatial harmonic component formed by the stator 12 is linked to each rotor winding 90n, 90s, so that each rotor winding 90n, 90s is provided with each diode 48, 50. As a result of the rectified direct current flowing and magnetizing each magnetic pole portion 106, each magnetic pole portion 106 functions as a magnet with a fixed magnetic pole.

  Further, the width of each magnetic pole portion 106 in the circumferential direction (the width θ of each rotor winding 90n, 90s) is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, and more preferably, the electrical The angle is equal to (or substantially equal to) the width corresponding to 90 °. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11, or the first example or the second example of another example of FIGS.

  FIG. 21 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the configuration example of FIG. 21, the rotor windings 90n and 90s are toroidal wound. In other words, in the configuration example of FIG. 21, the rotor core 24 includes the annular core portion 110, and a plurality of salient poles 114 project radially outward from a plurality of locations in the circumferential direction of the annular core portion 110. The rotor windings 90n and 90s are wound by toroidal winding at positions near the salient poles 114 in the annular core portion 110. Further, the rotor windings 90 n and 90 s are wound around a plurality of locations in the circumferential direction of the rotor core 24 so that a part of each of the rotor windings 90 n and 90 s is disposed in the slot 29. Also in the configuration example of FIG. 21, a rotating magnetic field including a spatial harmonic component formed by the stator 12 (see FIG. 2) is linked to each rotor winding 90n, 90s, so that each rotor winding 90n, 90s A direct current rectified by the diodes 48 and 50 flows, and each salient pole 114 is magnetized. As a result, the salient pole 114 located near the rotor winding 90n functions as the N pole, and the salient pole 114 located near the rotor winding 90s functions as the S pole. Further, the width θ of each salient pole 114 in the circumferential direction is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14, and more preferably equal to the width corresponding to 90 ° in terms of the electrical angle of the rotor 14. (Or almost equal).

  Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11, or the first example or the second example of another example of FIGS. In the configuration example of FIG. 21, the rotor windings 90n and 90s wound around all the salient poles 114 can be electrically separated from each other.

  FIG. 22 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the rotating electrical machine 10 having the configuration example of FIG. 22, the rotor 14 includes a rotor core 24 and a plurality of circumferentially wound rotor windings 90 n and 90 s. The rotor core 24 is made of a magnetic material. The rotor core main body 112 made from a product and the permanent magnet 104 arrange | positioned in the circumferential direction several places of the rotor 14 are included. Magnetic pole portions 106 such as pillar portions extending in the radial direction are formed at a plurality of locations in the circumferential direction of the rotor core 24, and the rotor windings 90 n and 90 s are wound around the magnetic pole portions 106. That is, slits 108 as second slots are formed at a plurality of locations in the circumferential direction of the rotor core 24, and the rotor windings 90 n and 90 s are arranged on the outer periphery of the rotor core 24 so that a part of each is disposed in the slit 108. It is wound around several places in the circumferential direction.

  The permanent magnets 104 are arranged, that is, embedded in the magnetic pole portions 106 provided at portions corresponding to the rotor windings 90 n and 90 s in the circumferential direction of the rotor 14 at a plurality of locations in the circumferential direction of the rotor 14. In other words, the rotor windings 90 n and 90 s are wound around each permanent magnet 104. The permanent magnet 104 is magnetized in the radial direction of the rotor 14, and the magnetizing direction is made different between the permanent magnets 104 adjacent in the circumferential direction of the rotor 14. In FIG. 22 (the same applies to FIG. 23 described later), a solid arrow arranged on the permanent magnet 104 represents the magnetization direction of the permanent magnet 104. Note that the magnetic pole portion 106 can also be constituted by salient poles or the like arranged to extend in the radial direction at a plurality of locations in the circumferential direction of the rotor 14.

  The rotor 14 has different magnetic salient pole characteristics with respect to the circumferential direction. Of the rotor 14, the magnetic path in the central portion in the circumferential direction between the magnetic pole portions 106 adjacent to each other in the circumferential direction, which is deviated from each permanent magnet 104 in the circumferential direction and deviated from the magnetic pole portion 106 in the circumferential direction, is q-axis magnetism. A magnetic path that coincides with the winding center axis of each rotor winding 90n, 90s in the circumferential direction is a d-axis magnetic path. Each permanent magnet 104 is disposed in d-axis magnetic paths located at a plurality of locations in the circumferential direction of the rotor 14.

  Further, the rotor windings 90n and 90s wound around the magnetic pole portions 106 are not electrically connected to each other and are separated (insulated). A diode 48 (or 50) is connected to each rotor winding 90n, 90s that is electrically separated. Further, the current flow directions of the diodes 48 connected to every other rotor winding 90n in the circumferential direction of the rotor 14 and the diodes 50 connected to the remaining rotor winding 90s are reversed, The forward direction of each other is reversed. For this reason, each rotor winding 90n, 90s is short-circuited via the diode 48 (or 50). Therefore, the current flowing through each rotor winding 90n, 90s is rectified in one direction.

  When a direct current corresponding to the rectification direction of the diodes 48 and 50 flows through the rotor windings 90n and 90s, the magnetic pole portion 106 around which the rotor windings 90n and 90s are wound is magnetized, so that the magnetic pole portion 106 is the magnetic pole. Functions as a fixed magnet. The direction of the broken-line arrow shown on the outer side of the rotor windings 90 n and 90 s with respect to the radial direction of the rotor 14 in FIG. 22 represents the magnetization direction of the magnetic pole portion 106.

  Further, as shown in FIG. 22, the directions of the direct currents are opposite to each other between the rotor windings 90 n and 90 s adjacent in the circumferential direction of the rotor 14. The magnetization directions of the magnetic pole portions 106 adjacent to each other in the circumferential direction of the rotor 14 are opposite to each other. For example, in FIG. 22, N poles are arranged on the radially outer sides of the rotor windings 90 n and portions that coincide with the circumferential direction of the rotor 14, which are every other magnetic pole portion 106 in the circumferential direction of the rotor 14. The S pole is arranged on the radially outer side of the portion that coincides with the circumferential direction of the rotor winding 90 s and the rotor 14, which is the magnetic pole portion 106 that is adjacent to the portion 106 in the circumferential direction. Two pole portions 106 (N pole and S pole) adjacent in the circumferential direction of the rotor 14 constitute one pole pair. In addition, the magnetization direction of each permanent magnet 104 is matched with the magnetization direction of the magnetic pole portion 106 that matches the circumferential direction of the rotor 14 with respect to each permanent magnet 104.

  The width of each magnetic pole portion 106 in the circumferential direction of the rotor 14 is set to be shorter than the width corresponding to 180 ° in terms of the electrical angle of the rotor 14. The width θ of each rotor winding 90n, 90s in the circumferential direction is set to be shorter than the width corresponding to 180 ° in electrical angle of the rotor 14, and more preferably equal to the width corresponding to 90 ° in electrical angle ( Or almost equal).

  In such a rotating electrical machine 10, a rotating magnetic field having a frequency including harmonic components generated in the stator 12 (FIG. 2) is generated by passing a three-phase alternating current through the three-phase stator windings 20 u, 20 v, and 20 w. 14 acts. Accordingly, the reluctance torque Tre, the permanent magnet generation torque Tmg, and the rotor winding generation torque Tcoil act on the rotor 14 to synchronize the rotor 14 with the rotating magnetic field (fundamental wave component) generated by the stator 12. And rotate. Here, the reluctance torque Tre is a torque generated when each magnetic pole portion 106 is attracted to the rotating magnetic field generated by the stator 12. The permanent magnet generation torque Tmg is a torque generated by attraction and repulsion, which is an interaction between the magnetic field generated by each permanent magnet 104 and the rotating magnetic field of the stator 12. Further, the rotor winding generation torque Tcoil is a torque generated by a current induced in the rotor windings 90n and 90s when a spatial harmonic component of the magnetomotive force generated by the stator 12 acts on the rotor windings 90n and 90s. The torque generated by attraction and repulsion, which is an electromagnetic interaction between the magnetic field generated by each magnetic pole portion 106 and the rotating magnetic field of the stator 12.

  According to the rotating electrical machine 10 of this configuration example, the torque of the rotating electrical machine 10 can be effectively increased. Moreover, since the magnetic flux fluctuation in each permanent magnet 104 is suppressed by the induced current flowing through the rotor windings 90n and 90s, the eddy current loss in each permanent magnet 104 can be suppressed, and the heat generation of the magnet can be reduced. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11, or the first example or the second example of another example of FIGS.

  FIG. 23 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the configuration example of FIG. 23, among the plurality of rotor windings 90n and 90s, some of the rotor windings 90n arranged every other in the circumferential direction of the rotor 14 are electrically connected in series, and in the circumferential direction. The remaining rotor windings 90s arranged every other are electrically connected in series. Further, two sets of rotor winding circuits 92n and 92s which are electrically separated from each other are configured by a circuit including the rotor winding 90n (or 90s) electrically connected to each other.

  In addition, diodes 48 and 50 having different polarities are respectively connected to the two sets of rotor winding circuits 92n and 92s in series with the other rotor windings 90n and 90s. The direction of the current flowing through 92n and 92s is rectified in one direction. Other configurations and operations are the same as those in the configuration example of FIG.

  FIG. 24 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. The rotor 14 constituting the rotating electrical machine of the configuration example of FIG. 24 has a rotor core 24 and a plurality of rotor windings 90n and 90s. The rotor core 24 has a configuration in which salient poles 114 projecting in the radial direction are provided at a plurality of circumferential positions on the outer peripheral surface, and each rotor winding 90 n and 90 s is disposed between salient poles 114 adjacent in the circumferential direction of the rotor 14. doing. That is, each of the rotor windings 90n and 90s is arranged in an air core state in which the inside becomes a space portion. Further, a portion between the rotor windings 90n and 90s in the circumferential direction of the rotor 14 protrudes toward the stator 12 (see FIG. 2), and the rotor core 24 has a magnetic salient pole characteristic. In this case, the rotor windings 90 n and 90 s are wound at a plurality of locations in the circumferential direction of the outer peripheral portion of the rotor core 24 so that part or all of the rotor windings 90 n and 90 s are arranged in the slot 29.

  In such a rotor 14, the magnetic path that coincides with the salient pole 114 in the circumferential direction of the rotor 14 is the q-axis magnetic path, and the position that coincides with the rotor windings 90 n and 90 s in the circumferential direction of the rotor 14 is the d-axis magnetic path. It becomes.

  In such a configuration example, no permanent magnet is disposed on the rotor 14, but the torque of the rotating electrical machine can be increased regardless of the rotation direction of the rotor 14. That is, regardless of the rotation direction of the rotor 14, the current phase-torque characteristics are the same, the maximum value of the torque is increased, and the torque can be effectively increased. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11, or the first example or the second example of another example of FIGS.

  FIG. 25 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the rotor 14 that constitutes the rotating electrical machine of the configuration example of FIG. 25, in the rotor core 24 of the configuration example shown in FIG. 19, the central portion in the circumferential direction of the portion formed so as to arrange the plurality of slits 94 in the radial direction is provided. The magnetic path is a d-axis magnetic path portion 98, and rotor windings 90 n and 90 s are arranged on the d-axis magnetic path portion 98. Further, in the rotor core 24, a portion between the d-axis magnetic path portions 98 adjacent in the circumferential direction is a q-axis magnetic path portion 96. Slits 94 are formed so that the d-axis magnetic path portions 98 and the q-axis magnetic path portions 96 facing the stator 12 (see FIG. 2) are alternately arranged in the circumferential direction, and the d-axis magnetic path portions in the circumferential direction are formed. 98 is located between the q-axis magnetic path portions 96.

  Even in such a configuration example, no permanent magnet is disposed on the rotor 14, but the torque of the rotating electrical machine can be increased regardless of the rotation direction of the rotor 14. Other configurations and operations are the same as those of the configuration example of FIG. 19 or FIG.

  FIG. 26 is a schematic diagram showing a rotor of another configuration example of the rotating electrical machine that constitutes the embodiment of the present invention. In the rotor 14 constituting the rotating electrical machine of the configuration example of FIG. 26, the rotor core 24 is constituted by a rotor core body 116 made of a magnetic material and a plurality of permanent magnets 104. The rotor core body 116 does not have magnetic salient pole characteristics, and the permanent magnets 104 are fixed at a plurality of locations in the circumferential direction of the outer peripheral surface of the rotor core body 116. In the rotor core 24, slots 29 are formed between the permanent magnets 104 at intervals in the circumferential direction around the rotation center axis of the rotor 14. In addition, rotor windings 28n and 28s are wound around each permanent magnet 104. In this case, the rotor windings 90 n and 90 s are wound at a plurality of locations in the circumferential direction of the outer peripheral portion of the rotor core 24 so that a part of each of the rotor windings 90 n and 90 s is disposed in the slot 29. In the present configuration example, a plurality of portions in the circumferential direction of the rotor 14 that coincide with the permanent magnets 104 in the circumferential direction are used as magnetic pole portions. Further, the rotor windings 90n and 90s are short-circuited by diodes 48 and 50 having different polarities between the adjacent rotor windings 90n and 90s. Other configurations and operations are the same as those of the above-described embodiments of FIGS. 1 to 9 and 11, or the first example or the second example of another example of FIGS.

  In the above description of the embodiment and configuration examples, the case of a radial type rotating electrical machine in which the stator 12 and the rotor 14 are disposed to face each other in the radial direction orthogonal to the rotation axis has been described. However, the rotary electric machine constituting the above embodiment may be an axial type rotary electric machine in which the stator and the rotor are arranged to face each other in the direction parallel to the rotation axis (rotation axis direction). In the above description, the case where the rotor is disposed opposite to the inner side in the radial direction of the stator has been described. However, the present invention can also be implemented with a configuration in which the rotor is disposed opposite to the outer side in the radial direction of the stator.

  In addition, although illustration is abbreviate | omitted, in said embodiment, while a control part makes the q-axis current command superimpose the reduction | decrease pulse current which decreases in a pulse form, the q-axis current command does not superimpose the increase pulse current. It is also possible to adopt a configuration of a rotating electrical machine drive system having q-axis pulse superposition correction means for correcting a q-axis current command so as to increase the induced current generated in the rotor winding in at least a part of the non-pulse superposition period.

  As mentioned above, although the form for implementing this invention was demonstrated, this invention is not limited to such embodiment at all, and it can implement with a various form in the range which does not deviate from the summary of this invention. Of course. In the present invention, for example, a configuration including an axial gap type rotating electrical machine or the like may be employed.

  10 rotating electrical machines, 12 stators, 14 rotors, 16 stator cores, 18 teeth, 20u, 20v, 20w stator windings, 22 slots, 24 rotor cores, 26 main salient poles, 28n first rotor windings, 28s second rotor windings, 29 slots, 30 first induction winding, 32 first common winding, 34 rotating electrical machine drive system, 36 inverter, 38 control device, 40 power storage device, 44 second induction winding, 46 second common winding, 48 second 1 diode, 50 second diode, 52 common winding set, 54 auxiliary salient pole, 56 capacitor, 58 collar, 60 current sensor, 62 rotation angle detection unit, 64 d-axis pulse superimposition correction means, 66, 68 subtraction unit, 70, 72 PI calculation unit, 74 3-phase / 2-phase conversion unit, 76 2-phase / 3-phase conversion unit, 78 d-axis pulse generation correction unit, 0 addition unit, 82 d-axis correction unit, 84 q-axis pulse superimposition unit, 86 auxiliary pole, 88 column part, 90n first rotor winding, 90s second rotor winding, 92n first rotor winding circuit, 92s second Rotor winding circuit, 94 slit, 96 q-axis magnetic path portion, 98 d-axis magnetic path portion, 100 rotating shaft, 102 rotor core body, 104 permanent magnet, 106 magnetic pole portion, 108 slit, 110 annular core portion, 112 rotor core body, 114 salient poles, 116 rotor core body, 118 first induction winding set, 120 second induction winding set.

Claims (5)

In a rotating electrical machine drive system including an electromagnet-type rotating electrical machine in which a stator and a rotor are arranged to face each other, a driving unit that drives the rotating electrical machine, and a control unit that controls the driving unit,
The stator is
A stator core in which a plurality of first slots are formed spaced apart from each other in the circumferential direction around the rotor rotation axis, and a multi-phase stator winding wound around the stator core in a concentrated manner through the first slot. Have
The rotor is
A rotor core having a plurality of second slots spaced apart from each other in the circumferential direction around the rotor rotation axis, and wound around a plurality of locations in the circumferential direction of the rotor core so that at least a portion thereof is disposed in the second slot Each of the rotor windings, and a rectifying unit that is connected to the rotor windings and alternately changes the magnetic characteristics of the rotor windings in the circumferential direction among the plurality of rotor windings. The magnetic characteristics of the magnetic pole portions at multiple locations in the circumferential direction generated by the current flowing in the winding are alternately varied in the circumferential direction,
The control unit pulsates a d-axis current command for causing a current to flow through the stator winding so as to generate a field magnetic flux in the same direction as the magnetic pole direction that is the winding central axis direction of the rotor winding. While increasing the increasing pulse current , the d-axis pulse is made larger than the d-axis current at the end of the d-axis pulse superposition period in which the increasing pulse current is superimposed on the d-axis current command. By making the current increase amount smaller than the current decrease amount in the superposition period, the d-axis current is gradually increased so that the d-axis current is gradually increased in the d-axis non-pulse superposition period in which the increase pulse current is not superimposed on the d-axis current command. Compared to the case where the increase and decrease of the d-axis current command in the d-axis pulse superimposition period are made the same in at least part of the d-axis non-pulse superimposition period after correcting the command , this occurs in the rotor winding. Increase induced current Rotating electrical machine drive system and having a d-axis pulse superimposing correcting means for. In a rotating electrical machine drive system including an electromagnet-type rotating electrical machine in which a stator and a rotor are arranged to face each other, a driving unit that drives the rotating electrical machine, and a control unit that controls the driving unit,
The stator is
A stator core in which a plurality of first slots are formed spaced apart from each other in the circumferential direction around the rotor rotation axis, and a multi-phase stator winding wound around the stator core in a concentrated manner through the first slot. Have
The rotor is
A rotor core having a plurality of second slots spaced apart from each other in the circumferential direction around the rotor rotation axis, and wound around a plurality of locations in the circumferential direction of the rotor core so that at least a portion thereof is disposed in the second slot Each of the rotor windings, and a rectifying unit that is connected to the rotor windings and alternately changes the magnetic characteristics of the rotor windings in the circumferential direction among the plurality of rotor windings. The magnetic characteristics of the magnetic pole portions at multiple locations in the circumferential direction generated by the current flowing in the winding are alternately varied in the circumferential direction,
The controller is
The q-axis current command for causing a current to flow in the stator winding so as to generate a field magnetic flux in a direction advanced 90 degrees in electrical angle with respect to the magnetic pole direction which is the winding central axis direction of the rotor winding is pulsed. Q-axis pulse superimposing means for superimposing a decreasing pulse current that decreases in a shape,
In a d-axis current command for causing a current to flow through the stator winding so as to generate a field magnetic flux in the same direction as the magnetic pole direction that is the winding central axis direction of the rotor winding, a reduced pulse current is added to the q-axis current command. The d-axis current in the q-axis non-pulse superposition period in which the d-axis current at the start of the q-axis pulse superposition period is made smaller than the d-axis current at the end and the reduced pulse current is not superimposed on the q-axis current command. A dynamo-electric machine drive system comprising d-axis correction means for correcting a d-axis current command so as to gradually reduce the d-axis. In the rotating electrical machine drive system according to claim 1 or 2 ,
Each of the rotor windings is connected to a rectifying element that is the rectifying unit so that the forward direction is reversed between the rotor windings adjacent to each other in the circumferential direction of the rotor. The rotation is characterized in that the current flowing in the rotor windings adjacent to each other in the circumferential direction is alternately changed between the A phase and the B phase by rectifying the current flowing in the rotor winding due to the generation. Electric drive system. In the rotating electrical machine drive system according to claim 3 ,
The rectifying elements are a first rectifying element and a second rectifying element connected to the corresponding rotor winding, respectively.
The first rectifying element and the second rectifying element rectify a current flowing through the corresponding rotor winding by generating the induced electromotive force, and generate a plurality of circumferential directions generated by the current flowing through the rotor windings. A rotating electrical machine drive system, wherein magnetic properties of the magnetic pole portions at different locations are alternately varied in the circumferential direction. In the rotating electrical machine drive system according to claim 3 or 4 ,
The rotor has a width in the circumferential direction of the rotor teeth provided between the rotor slots arranged in the circumferential direction, which is smaller than a width corresponding to an electrical angle of 180 °. A rotating electrical machine drive system, wherein the rotor teeth are wound in a short-pitch winding.

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