JP3385849B2 - Comparator with hysteresis adjustment function and current detection circuit - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a comparator with a hysteresis adjusting function and a current detection circuit including the comparator.

[0002]

2. Description of the Related Art A comparator with a hysteresis adjusting function of this type is proposed in, for example, Japanese Patent Laid-Open No. 5-167405. The comparator that makes this hysteresis variable is
The input voltage and the threshold value are compared to output a binary voltage to the output terminal, and the hysteresis is made variable according to the input voltage.

When a conventional comparator with a hysteresis adjusting function is applied to form an output current detection circuit, it is necessary to convert the output current into a voltage by a detection resistor.

[0004]

However, there is a problem that the output current cannot be accurately detected due to the variation in the absolute value of the detection resistor. Further, the output current to be detected, that is, the output current from the electric load, has a ripple due to the output current when the electric load is on / off controlled by PMW driving or the like. The function of varying the hysteresis of the detection circuit is essential. That is, a current detection circuit with a hysteresis automatic adjustment function, which can change the hysteresis not by the voltage but by the current, is required.

Therefore, the object of the present invention is that the hysteresis changes depending on the current value. Therefore, as compared with a comparator in which the hysteresis is variable in proportion to the input voltage, there is no decrease in the detection accuracy due to variations in the detection resistance. It is an object of the present invention to provide a current detection circuit using a comparator and a comparator with a hysteresis adjusting function.

[0006]

In order to solve the above problems, the invention of claim 1 is a comparator including a differential circuit for comparing a detection voltage with a threshold voltage and outputting a binary voltage to the output side. In the above, while configuring the differential circuit,
Depending on the detection voltage and the threshold voltage,
A current mirror circuit is configured for the transistors Q4 and Q5.
Transistors Q6 and Q7 that form a constant current load
And one of the transistors Q of the differential pair.
4 and one of the transistors Q6 serving as the constant current load
At the connection point, a pair of transistors Q13 and Q14 are connected in series.
The circuit is connected to the other transistor Q5 of the differential pair.
Connection with the other transistor Q7 serving as the constant current load
The point is a series circuit of a pair of transistors Q15 and Q16.
And a pair of transistors that form each of the series circuits.
One of the transistors Q14 and Q16 is a constant current
Configure a current mirror circuit that serves as a load, and
Of the pair of transistors that make up the path, the other transistor
The transistors Q13 and Q15 are connected to each other by the binary voltage on the output side.
On the contrary, by configuring to turn on and off,
When the two series circuits are turned on, whether they are the transistors of the differential pair.
Differential current bypass to bypass some current flowing from the
As a circuit, a pair of transistors Q1 is connected between the power supply and GND.
Bypass current setting circuit with 8 and Q17 series circuit
Provided, one transistor of the bypass current setting circuit
Q17 is a constant current load of the differential stage current bypass circuit.
With each transistor Q14, Q16
By configuring the mirror circuit, the other transistor
When Q18 is on, the current flowing in the bypass current setting circuit
Flow to the differential stage current bypass circuit when the current value changes.
The gist is a comparator with a hysteresis adjusting function, which is characterized in that the current value to be changed is changed .

According to a second aspect of the invention, there is provided a voltage-current conversion circuit for flowing a current proportional to the detection current flowing through the detection resistor based on the detection voltage of the detection resistor, and the voltage-current conversion circuit is
The number of times a current proportional to the detection current flowing through the detection resistor is passed.
Connect the transistor Q19 to the
The transistor Q19 and the transistor Q19 are connected to the transistor Q19.
In the comparator with hysteresis adjustment function described in
To the other transistor Q18 of the bypass current setting circuit
According to claim 1, the current mirror circuit is further configured.
Connect the described comparator, the comparator is the
The detection voltage of the detection resistor and the threshold voltage are compared and output to the output side.
The gist of the present invention is a current detection circuit characterized by outputting a binary voltage . In the present invention, the term “proportional” includes a 1: 1 relationship.

According to the invention of claim 1, one of the differential stage current bypass circuits of the transistors of the differential pair is turned on when the voltage on the output side becomes high level, and the other is turned off. Let The on-operation differential stage current bypass circuit bypasses a part of the current flowing from one transistor of the differential pair. In addition, the bypass current setting circuit causes the bypass current setting circuit to change the value of the current flowing through the bypass current setting circuit.
When changed, the current value is proportional to the current. When the voltage on the output side becomes low level, one differential stage current bypass circuit is turned off and the other differential stage current bypass circuit is turned on. The differential stage current bypass circuit that is on-state bypasses a part of the current flowing from the other transistor of the differential pair. Also, this bypassed current is set by the bypass current setting circuit.
When the value of the current flowing through the circuit changes, the current value becomes proportional to the current.

According to the second aspect of the invention, the voltage-current conversion circuit causes a current proportional to the detection current flowing through the detection resistor to flow based on the detection voltage of the detection resistor. Comparator of the differential stage current bypass circuit of the transistor of the differential <br/> pair,
One of them turns on when the voltage on the output side becomes high level, and the other turns off. The differential stage current bypass circuit that is on-state bypasses a part of the current flowing from one transistor of the differential pair. Further, the bypassed current has a current value proportional to the current related to the detection voltage of the detection resistor by the bypass current setting circuit. When the voltage on the output side becomes low level, one differential stage current bypass circuit is turned off and the other differential stage current bypass circuit is turned on. The differential stage current bypass circuit that is on-state bypasses a part of the current flowing from the other transistor of the differential pair. Further, the bypassed current has a current value proportional to the current related to the detection voltage of the detection resistor by the bypass current setting circuit.

Therefore, the comparator of the current detection circuit has a hysteresis corresponding to the detection current of the detection resistor, so that the detection accuracy of the current detection circuit does not deteriorate due to the variation of the detection resistor.

[0011]

BEST MODE FOR CARRYING OUT THE INVENTION An embodiment of the present invention will be described below with reference to FIGS. 1 to 3 and 5.

FIG. 1 shows an electric circuit of the current detection circuit. FIG. 2 shows an electric circuit of the comparator with hysteresis adjusting function. FIG. 3 is a characteristic diagram of the current detection voltage generating circuit, and FIG. 5 is a characteristic diagram of the comparator with hysteresis adjusting function.

The transistor Q1 described below is used.
~ Q5, Q9, Q18, Q19, Q21 are P channel M
It is composed of an OS transistor, and also a transistor Q6.
-Q8, Q10-Q17, and Q20 are composed of N-channel MOS transistors.

As shown in FIG. 1, the current detection circuit 1 of the present embodiment includes a voltage / current conversion circuit 2, a comparator with hysteresis adjustment function (hereinafter referred to as comparator) 3, a current detection voltage generation circuit 4, and an output control circuit 5. Etc., and is made into an IC chip.

The electric load 6 is connected to the power supply VBB via the transistor Q21, and is driven by the transistor Q21 being on / off controlled based on a control signal applied from the output control circuit 5. The ground side terminal of the electric load 6 is grounded via the detection resistor RS. The output control circuit 5 applies a control signal to the transistor Q21 based on an output ON / OFF signal from a control circuit (not shown). A protective diode D is connected between the drain and source of the transistor Q21.

A transistor Q1 is connected between the power source Vcc and GND.
A series circuit of 9, Q20 and resistor R1 is connected. The gate of the transistor Q19 is connected to the drain. The resistor R1 has the same resistance value as the resistor RS. The operational amplifier 7 has its non-inverting input terminal connected to the connection point a between the electric load 6 and the detection resistor RS, and its inverting input terminal connected to the connection point b between the resistor R1 and the transistor Q20. The output terminal of the operational amplifier 7 is connected to the gate of the transistor Q20. In the operational amplifier 7, an output current I1 as a detection current flows through the detection resistor RS when the electric load 6 is driven, and a voltage drop V1 due to the detection resistor RS.
When the (detection voltage) is applied to the non-inverting input terminal, the output control voltage is applied to the gate of the transistor Q20 so that the applied voltage V1 and the voltage at the connection point b (voltage drop due to the resistor R1) become the same. Is being done. That is, the operational amplifier 7 causes the current I2 having the same current value as the output current I1 flowing through the resistor RS to flow through the resistor R1.

The operational amplifier 7 and the transistor Q2
The voltage-current conversion circuit 2 is composed of 0 and the resistor R1. The comparator 3 is composed of an operational amplifier, its non-inverting input terminal IN + is connected to the connection point a, and its inverting input terminal IN− is connected to the current detection voltage generating circuit 4. As shown in FIG. 3, the current detection voltage generation circuit 4 has a characteristic that the voltage Vref as a threshold voltage applied to the inverting input terminal IN- linearly decreases as the applied voltage VBB increases. The comparator 3 is driven by a single power source. The VR terminal of the comparator 3 is the transistor 19
Is connected to the gate. Further, the output terminal OUT of the comparator 3 is connected to the output control circuit 5, and the output control voltage of the comparator 3 is applied to the output control circuit 5. When the high level (H) of the output control voltage is applied while the output ON / OFF signal is being input, the output control circuit 5 invalidates the output ON / OFF signal and stops the ON control of the transistor Q21. Is being done.

The electric circuit of the comparator 3 will be described with reference to FIG. The comparator 3 includes a differential amplifier circuit 11 as a differential circuit, a voltage amplifier circuit 12, and a power amplifier circuit 1.
3, a bias current setting circuit 14, and a hysteresis voltage adjusting circuit 15.

As shown in FIG. 2, the differential amplifier circuit 11 comprises transistors Q4, Q5, Q6, Q7 and a transistor Q1 serving as a constant current source. A current mirror circuit is formed by the transistors Q6 and Q7,
The constant current load is applied to the transistors Q4 and Q5.

As shown in FIG. 2, the voltage amplifier circuit 12 is composed of a transistor Q8 and a transistor Q2 serving as a constant current source, and amplifies the signal from the differential amplifier circuit 11 by voltage amplification. The power amplifier circuit 13 is composed of transistors Q9 and Q10, and power-amplifies the signal from the voltage amplifier circuit 12.

The bias current setting circuit 14 is composed of transistors Q11 and Q12, a resistor R2 and a transistor Q3 serving as a constant current source, and sets the bias current of the comparator 3. A current mirror circuit is constituted by Q11 and Q12, and is a constant current load. Further, a current mirror circuit is constituted by the transistors Q1, Q2 and Q3, each of which serves as a constant current source.

The hysteresis voltage setting circuit 15 is composed of a differential stage current bypass circuit (hereinafter referred to as a bypass circuit) 15a and a bypass current setting circuit 15b. The bypass circuit 15a includes a transistor Q13, which is connected between the connection point between the transistors Q4 and Q6 and GND.
Series circuit composed of Q14, and transistors Q5 and Q7
Transistor Q connected between the connection point and GND
And a series circuit including Q16.

Further, the bypass current setting circuit 15b is connected to the power source V
Transistors Q18 and Q17 connected between cc and GND
It is composed of a series circuit of. Q14, Q16,
A current mirror circuit is formed by Q17 and serves as a constant current load. Further, a current mirror circuit is constituted by Q18 and Q19, which serves as a constant current source.

In the current mirror circuits described above, the transistor Q19 and the transistor Q18 have different channel lengths so that the current ratio becomes Q19: Q.
18 = 1: X (X is any value less than 1),
Each of the other remaining current mirror circuits has a current ratio of 1: 1 between the transistors forming the circuits.

First, the operation of the comparator 3 configured as described above will be described. The differential amplifier circuit 11 will be described. In FIG. 2, transistors Q4, Q6,
The currents flowing in Q13 are IA0, IA1, and IA2,
The currents flowing through the transistors Q5, Q7 and Q15 are IB0, IB1 and IB2, respectively.

If the differential amplifier circuit 11 is not provided with the bypass circuit 15a, the difference between the voltage V (IN-) applied to the inverting input terminal and the voltage V (IN +) applied to the non-inverting input terminal is The output voltage is as follows.

When V (IN-) = V (IN +), IA0 = IB0
When Vout = Vcc V (IN-)> V (IN +), or V (IN-) <V (I
When N +), Vout = (V (IN +)-V (IN-)) A0 + Vcc where A0 is the amplification degree of the comparator 3.

Next, Vout now exceeds Vcc and is "high".
At the level (hereinafter referred to as H), the transistor Q13
Is turned on and the transistor Q14 is turned on by the VR voltage. At this time, the transistor Q15 is off because the voltage at the connection point c between the gates of the transistors Q9 and Q10 is "low" level. In this state, the differential stage current bypass circuit 15 of the differential amplifier circuit 11
Since the current IA2 is shunted to the transistor Q13 of a, IA0 = IA1 + IA2, IB0 = IB1. Since the transistors Q6 and Q7 are constant current loads, IA1 = IB1 (= IB0) As a result, IA0> IB0.

That is, because of the shunt IA2 flowing through the transistor Q13 of the bypass circuit 15a, the transistor Q4
That is, the current IA0 flowing through it increases. Therefore, in order to balance the currents IA0 and IB0 flowing through the transistors Q4 and Q5, the applied voltage V (IN
When-) is kept constant, it is necessary to lower the applied voltage V (IN +) to the non-inverting input terminal than when there is no hysteresis.

Transistor Q of this bypass circuit 15a
When IA0 = IB0 when 13 is on, that is, when the difference between the voltages applied to both input terminals when Vout is 0 is Vh2, V (IN +)-V (IN-) =-Vh2 , As shown in FIG. Note that Vh2> 0.

That is, when the difference in applied voltage between both input terminals becomes -Vh2 or less, the output voltage of the comparator 3 changes so as to become L along the line α as shown in FIG. Conversely, when Vout is at a "low" level (hereinafter referred to as "L") that is less than Vcc, the transistor Q13 is turned off and the transistor Q16 is driven by the VR voltage.
It shall be turned on. At this time, the transistor Q15 is turned on because the voltage at the connection point c between the gates of the transistors Q9 and Q10 is "high" level. In this state, the current IB2 is shunted to the transistor Q15 of the differential stage current bypass circuit 15a of the differential amplifier circuit 11, so that IB0 = IB1 + IB2 and IA0 = IA1. Since the transistors Q6 and Q7 are constant current loads, IB1 = IA1 (= IA0) As a result, IB0> IA0.

That is, due to the shunt IB2 flowing through the transistor Q15 of the bypass circuit 15a, the transistor Q5
That is, the current IB0 flowing through is increased. Therefore, in order to balance the currents IA0 and IB0 flowing through the transistors Q4 and Q5, the applied voltage V (IN
When-) is kept constant, it is necessary to increase the applied voltage V (IN +) of the non-inverting input terminal as compared with the case where there is no hysteresis.

Transistor Q of this bypass circuit 15a
When 5 is on and IA0 = IB0, that is,
If the difference between the voltages applied to both input terminals when Vout becomes 0 is Vh1, then V (IN +)-V (IN-) = Vh1 is obtained, as shown in FIG. Note that Vh1> 0.

That is, when the difference in applied voltage between both input terminals becomes Vh1 or more, the output voltage of the comparator 3 changes so as to become H along the line β as shown in FIG. In this embodiment, since the current ratio of Q14 and Q16 is 1: 1, Vh1 = Vh2.

The current I3 flowing through the transistor Q18
Is X times the current I2 flowing in the transistor Q19 (X <
1), that is, X times the current I1. As a result, a slight change in the current I1 is reduced by a factor of X. The transistors Q14 and Q16 are the transistors Q1.
7 and the current mirror circuit, the current flowing through the transistors Q14 and Q16 has the same current value as the reduced current. These transistors Q14 and Q16
When the value of the current flowing in the bypass circuit changes, the value of the current flowing in the bypass circuit 15a also changes. As a result, the Vh
The magnitudes of 1 and Vh2 change, that is, the hysteresis of the comparator 3 changes due to the change of the output current I1.

Next, the operation of the current detection circuit 1 having the comparator 3 will be described. The transistor Q21 is turned on based on the control signal applied from the output control circuit 5.
When controlled to be off, the electric load 6 is driven. When the output current I1 of the operational amplifier 7 flows from the electric load 6, the voltage drop V1 due to the detection resistor RS is applied to the non-inverting input terminal. As a result, the operational amplifier 7 applies the output control voltage to the gate of the transistor Q20 so that the applied voltage V1 and the voltage at the connection point b (voltage drop due to the resistor R1) become the same. That is, the resistance RS
I2, which has the same current value as the output current I1 flowing through the resistor R
Flows to 1.

The comparator 3 has its non-inverting input terminal I
When the voltage drop V1 of the detection resistor RS is applied to N +, the applied voltage V1 (= V (IN +)) is compared with the voltage Vref (= V (IN-)) applied from the current detection voltage generation circuit 4. , A0 (V1-Vref) + Vcc output voltage is applied to the output control circuit 5.

The output control circuit 5 outputs the output ON / OF.
When the F signal is input, this output control voltage is V
When a voltage higher than cc, that is, a high (H) level voltage is applied, the output ON / OFF signal is invalidated and the ON control of the transistor Q21 is stopped. Further, the output control circuit 5, when the output ON / OFF signal is input,
When this output control voltage is lower than Vcc, that is, a low (L) level voltage is applied, the output is turned on / off.
The transistor Q21 is turned on / off based on the signal I.

(A) Comparator 3 of this embodiment
According to the above, the transistor Q19 and the transistor Q18 have different channel lengths so that the current ratio is Q1.
9: Q18 = 1: X (X is an arbitrary value less than 1). As a result, even when the absolute values are different such that the output current I1 changes from a low current value to a high current value, for example, a low current value is 10 milliamperes and a high current value is 10 amperes, the absolute values are different. The hysteresis can be changed by following the change.

(B) Further, in the current detection circuit 1 including the comparator 3, since the comparator 3 operates with an accurate hysteresis corresponding to the output current I1 flowing through the resistor RS, it depends on the variation of the detection resistor RS and the like. It is possible to realize a hysteresis voltage that does not occur. or,
This makes it possible to provide a current detection circuit having excellent noise resistance even when noise is superimposed on the output current.

(C) In this embodiment, as shown in FIG. 3, the current detection voltage generation circuit 4 linearly changes the voltage Vref applied to the inverting input terminal IN- as the applied voltage VBB increases. It has a small property. As a result,
By applying this voltage to the inverting input single yarn, the power consumed by the IC can be made constant.

Further, when this circuit is used, when the output current I1 is continuously changed by the voltage VBB applied to the inverting input terminal, conventionally, the voltage drop (detection voltage) of the detection resistor RS and the hysteresis corresponding thereto are provided. It was necessary to prepare several types of comparators, but it is possible to configure the current detection circuit 1 with one comparator 3.

(D) Further, the current detection circuit 1 is
Since the hysteresis width can be accurately controlled according to the output current, noise and the like that are uniquely generated by the driving method can be removed, and it is possible to drive the load with high stability.

The present invention is not limited to the above embodiment, but can be carried out as follows. (A) In the above embodiment, the transistors Q14 and Q1
Although the current ratio to 6 is set to 1: 1, other current ratios may be used. By doing so, the magnitude relationship between Vh1 and Vh2 in FIG. 5 can be established, and hysteresis can be obtained as necessary.

(B) In the above embodiment, the transistor Q19 and the transistor Q18 have different channel lengths so that the current ratio is Q19: Q18 = 1: X (X
Is any value less than 1). Instead, by making the channel lengths of the transistor Q19 and the transistor Q18 the same, the current ratio becomes Q19: Q18 =
It may be 1: 1. In addition, if you want to detect a small current and obtain hysteresis with this small current, set X to 1
The above may be applied. By doing so, a suitable hysteresis can be obtained even with a small detection current I1.

(C) In the above embodiment, the voltage VBB applied to the inverting input terminal IN- of the comparator 3 becomes smaller as the voltage VBB applied to the electric load 6 has a larger characteristic of the current detection voltage generating circuit 4. However, as shown in FIG. 4, if the temperature Tc of the electric load 6 increases, the voltage Vref applied to the inverting input terminal IN- of the comparator 3 may decrease. In this way, when the temperature rises, noise tends to be superimposed, but there is also hysteresis for this noise, so there is no problem,
The temperature rise of the electric load 6 during driving can be made constant. Even in this case, the output current value I1 changes from about several tens of milliamps to several tens of amps, so that erroneous detection can be prevented.

(D) The MOS transistor of the above embodiment may be constituted by a bipolar transistor .

[0048]

[0049]

[0050]

As described above in detail, according to the first aspect of the present invention, since the hysteresis changes depending on the current value, the variation in the detection resistance is greater than that in the comparator in which the hysteresis is variable in proportion to the input voltage. It has an excellent effect that the detection accuracy does not decrease due to.

According to the second aspect of the invention, it is possible to realize a hysteresis voltage that is not affected by variations in the detection resistance and the like. Further, this makes it possible to provide a current detection circuit having excellent noise resistance even when noise is superimposed on the output current.

[Brief description of drawings]

FIG. 1 is an electric circuit diagram of a current detection circuit according to an embodiment.

FIG. 2 is a circuit diagram of a comparator having a hysteresis adjusting function.

FIG. 3 is a characteristic diagram of a current detection voltage generation circuit.

FIG. 4 is a characteristic diagram of another current detection voltage generation circuit.

FIG. 5 is a characteristic diagram of a comparator with a hysteresis adjusting function.

[Explanation of symbols]

1 ... Current detection circuit, 2 ... Current-voltage conversion circuit, 3 ... Comparison with hysteresis adjustment function, 4 ... Current detection voltage generation circuit, 5 ... Output circuit, 6 ... Electrical load, 7 ... Operational amplifier, 11 ... Differential circuit Differential amplifier circuit, 12 ... Voltage amplifier circuit, 13 ... Power amplifier circuit, 14 ... Bias current setting circuit, 15 ... Hysteresis voltage adjusting circuit, 15a ... Differential stage current bypass circuit, 15b ... Bypass current setting circuit, Q1. Q21 ... Transistor, R1 ... Resistor, RS ...
Detection resistance.

Claims (2)

(57) [Claims] 1. A comparator including a differential circuit for comparing a detected voltage with a threshold voltage and outputting a binary voltage to an output side, wherein the differential circuit is configured and the detected voltage and the threshold voltage are combined.
Each transistor Q of the differential pair that operates by pressure
4 and Q5 form a current mirror circuit and
Connect transistors Q6 and Q7, which are current loads, respectively
And the one transistor Q4 of the differential pair and the constant current load
At the connection point with one transistor Q6
By connecting a series circuit of transistors Q13 and Q14,
The other transistor Q5 of the differential pair and the constant current load
The other transistor Q7 connected to
Connect a series circuit of transistors Q15 and Q16 to
One of the pair of transistors that make up the column circuit
The transistors Q14 and Q16 are currents that are constant current loads.
A pair of mirror circuits is formed, and each of the series circuits is formed.
Of the transistors, the other transistor Q13, Q1
5 is turned on / off in reverse due to the binary voltage on the output side
By adopting a configuration that operates, both series circuits are
Part of the current that flows from the differential pair transistor when
And a pair of transistors Q18 and Q17 between the power supply and GND.
The bypass current setting circuit comprising a series circuit formed of, one transistor of the bypass current setting circuit Q17
Is a constant current load of the differential stage current bypass circuit.
Current mirror with transistors Q14 and Q16
By configuring the circuit, the other transistor Q18
When is on, the current value flowing in the bypass current setting circuit is
Current that flows through the differential stage current bypass circuit when it changes
A comparator with a hysteresis adjustment function, which is characterized by changing the value . 2. A voltage-current conversion circuit for flowing a current proportional to the detection current flowing through the detection resistor based on the detection voltage of the detection resistor is provided, and the detection current flowing through the detection resistor by the voltage-current conversion circuit.
Transistor Q19 for the circuit that supplies a current proportional to
Is connected to the transistor Q19 with respect to the transistor Q1.
9 and the comparator with the hysteresis adjusting function according to claim 1 .
The other transistor in the bypass current setting circuit
So as to form a current mirror circuit with
The comparator according to claim 1 is connected to the comparator , and the comparator includes a detection voltage of the detection resistor and a threshold voltage.
Characterized by comparing with pressure and outputting a binary voltage to the output side
And current detection circuit.