JP2011118019A - Display and display drive method - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To improve uniformity by preventing shading in a unit, while securing the threshold correction time by threshold correction of a device unit. <P>SOLUTION: In a display, a plurality of horizontal lines are regarded as a single unit, to simultaneously perform threshold correction operation in each pixel circuit of the inside of the same unit. Since each pixel circuit of the inside of the unit simultaneously performs threshold correction operation, the display generates a difference in waiting time up to writing of a video signal voltage from threshold correction operation completion, and gives a leak suppression voltage V1 to a gate of each drive transistor, after threshold correction completion so that a difference due to a leakage current does not generate in fluctuation of a voltage between the gate and a source of a drive transistor of each pixel circuit during the waiting time. <P>COPYRIGHT: (C)2011,JPO&INPIT

Description

  The present invention relates to a display device having a pixel array in which pixel circuits are arranged in a matrix, and a display driving method thereof, for example, a display device using an organic electroluminescence element (organic EL element) as a light emitting element.

JP 2007-133282 A JP 2003-255856 A JP 2003-271095 A

For example, as can be seen in Patent Documents 2 and 3, image display apparatuses using organic EL elements as pixels have been developed. Since the organic EL element is a self-luminous element, it has advantages such as higher image visibility than a liquid crystal display, no need for a backlight, and high response speed. Further, the luminance level (gradation) of each light emitting element can be controlled by the value of the current flowing therethrough (so-called current control type).
In the organic EL display, similarly to the liquid crystal display, there are a simple matrix method and an active matrix method as driving methods. Although the former has a simple structure, there is a problem that it is difficult to realize a large-sized and high-definition display. Therefore, the active matrix method is actively developed at present. In this method, a current flowing through a light emitting element in each pixel circuit is controlled by an active element (generally a thin film transistor: TFT) provided in the pixel circuit.

By the way, as a pixel circuit configuration using an organic EL element, improvement in display quality by eliminating luminance unevenness for each pixel, high luminance, high definition, and high frame rate (high frequency) are strongly demanded. Yes. Development of larger panels is also underway.
From these viewpoints, various configurations are being studied. For example, as in Patent Document 1, various pixel circuit configurations and operations have been proposed in which variations in the threshold voltage and mobility of the drive transistor for each pixel are canceled to eliminate luminance unevenness for each pixel.
An object of the present invention is to realize a pixel circuit operation suitable for high frequency and large panel as a display device using an organic EL element.

The display device of the present invention is electrically connected to a light emitting element and a driving transistor that applies a current corresponding to a gate-source voltage to the light emitting element by applying a driving voltage between the drain and the source. A sampling transistor that inputs a signal line voltage to the gate of the drive transistor, and a storage capacitor that is connected between the gate and source of the drive transistor and holds the threshold voltage of the drive transistor and the input video signal voltage. When a pixel array having a pixel array arranged in a matrix and a plurality of horizontal lines for each pixel circuit of the pixel array as one unit, in a plurality of horizontal periods corresponding to the number of horizontal lines of one unit, As the signal line voltage, a threshold correction reference voltage, a leak is applied to each signal line arranged in a row on the pixel array. A signal selector that supplies a suppression voltage and a video signal voltage to each of the pixel circuits in the unit, and a power pulse is applied to each power control line arranged in a row on the pixel array, and the driving of the pixel circuit A drive control scanner for applying a drive voltage to the transistors, a scanning pulse is applied to each write control line arranged in a row on the pixel array to control the sampling transistors of the pixel circuit, and As the scanning pulse for each pixel circuit in the unit, the threshold correction reference voltage is input to each pixel circuit so that the threshold correction operation is simultaneously performed within the period of one light emission cycle of each pixel circuit, and the threshold correction operation is completed. Later, the leak suppression voltage is input to each pixel circuit, and then the video signal voltage is sequentially input to each pixel circuit in the unit. And a write scanner for outputting the scan pulses for controlling the sampling transistor so that.
Further, the writing scanner performs a plurality of threshold correction operations in each pixel circuit within a period of one light emission cycle, and after the last threshold correction operation of the plurality of threshold correction operations, the leak suppression voltage The scan pulse is output so as to be input to each pixel circuit.
The leak suppression voltage is lower than the threshold correction reference voltage.

  According to the display driving method of the present invention, when the signal selector uses a plurality of horizontal lines as one unit for each pixel circuit of the pixel array, each signal line is output in a plurality of horizontal periods corresponding to the number of horizontal lines of one unit. Further, as the signal line voltage, a threshold correction reference voltage, a leakage suppression voltage, and a video signal voltage for each of the pixel circuits in the unit are supplied, and the writing scanner applies to each of the pixel circuits in one unit. The threshold correction reference voltage is input to each pixel circuit so that the threshold correction operation is simultaneously performed within one light emission cycle period of each pixel circuit, and the leak suppression voltage is input to each pixel circuit after the threshold correction operation is completed. After that, by sequentially inputting the video signal voltage to each pixel circuit in the unit, the luminance corresponding to the video signal voltage input in each pixel circuit is generated. It is to be performed.

In the present invention, an STC (Simultaneous Threshold Cancel) driving method is adopted in which a plurality of horizontal lines are set as one unit, and each pixel circuit in the same unit performs a threshold correction operation simultaneously. For example, if three horizontal lines are taken as one unit, each pixel of the three lines simultaneously performs a threshold value correcting operation. With this STC drive, the threshold correction operation period can be extended even when a high frame rate is achieved.
In this case, the signal selector supplies the threshold correction reference voltage to the signal line in order to use the gate of the driving transistor as the threshold correction reference voltage during the threshold correction operation. Further, in order to sequentially apply the video signal voltage to each pixel circuit (drive transistor) in the unit, the signal selector sequentially supplies the video signal voltage to each pixel circuit to the signal line. For example, when one unit has three lines, in three horizontal periods, the threshold correction reference voltage, the video signal voltage for the pixel circuit on the first line in the unit, the video signal voltage for the pixel circuit on the second line, A video signal voltage is supplied to the pixel circuit on the third line.
Then, each pixel circuit in the unit performs the threshold correction operation at the same time, so that there is a difference in waiting time from the completion of the threshold correction operation to the writing of the video signal voltage.
Here, in the present invention, during the waiting time, a leakage suppression voltage is applied so that a difference due to a leakage current does not occur in the variation of the gate-source voltage of the driving transistor of each pixel circuit.

According to the present invention, in the STC drive, each pixel circuit in the unit has a different waiting time from the completion of the threshold correction operation to the writing of the video signal voltage. The leakage current of each driving transistor is suppressed. As a result, the difference in waiting time can be prevented from appearing as the difference in light emission luminance between the pixel circuits.
That is, in STC driving suitable for high frame rate, it is possible to prevent shading in the same unit caused by leakage current flowing between the drain and source of the driving transistor, and display with good uniformity (uniformity) Can be realized.

It is explanatory drawing of a structure of the display apparatus of embodiment of this invention. It is a circuit diagram of a pixel circuit of an embodiment. It is explanatory drawing of pixel circuit operation | movement in the case of performing division | segmentation threshold value correction | amendment. It is explanatory drawing of pixel circuit operation | movement in the case of performing STC drive. It is explanatory drawing of the threshold value correction period by STC drive. It is explanatory drawing of the gate-source voltage fluctuation | variation by the leak in STC drive. It is explanatory drawing of the shading at the time of STC drive. It is explanatory drawing of STC drive of embodiment. It is explanatory drawing of the leak suppression in the STC drive of embodiment. It is explanatory drawing of the Vgs-Ids characteristic of a drive transistor.

Hereinafter, embodiments of the present invention will be described in the following order.
[1. Configuration of Display Device and Pixel Circuit]
[2. Pixel circuit operation considered in the process leading to the present invention: division threshold correction]
[3. Pixel circuit operation considered in the process leading to the present invention: STC driving]
[4. Pixel Circuit Operation of Embodiment]

[1. Configuration of Display Device and Pixel Circuit]

FIG. 1 shows a configuration of an organic EL display device according to an embodiment.
This organic EL display device includes a pixel circuit 10 that uses an organic EL element as a light emitting element and performs light emission driving by an active matrix method.
As illustrated, the organic EL display device includes a pixel array 20 in which a large number of pixel circuits 10 are arranged in a matrix in the column direction and the row direction (m rows × n columns). Each of the pixel circuits 10 is a light emitting pixel of any one of R (red), G (green), and B (blue), and a color display device is configured by arranging the pixel circuits 10 of each color according to a predetermined rule. .

As a configuration for driving each pixel circuit 10 to emit light, a horizontal selector 11, a drive scanner 12, and a write scanner 13 are provided.
Also, signal lines DTL1, DTL2,... DTL (n), which are selected by the horizontal selector 11 and supply a voltage corresponding to the signal value (gradation value) of the luminance signal as display data to the pixel circuit 10, are on the pixel array. It is arranged in the column direction. The signal lines DTL1, DTL2,... DTL (n) are arranged by the number of columns (n columns) of the pixel circuits 10 arranged in a matrix in the pixel array 20.

  On the pixel array 20, write control lines WSL1, WSL2,... WSL (m) and power supply control lines DSL1, DSL2,. These write control lines WSL and power supply control lines DSL are arranged by the number of rows (m rows) of the pixel circuits 10 arranged in a matrix in the pixel array 20, respectively.

Write control lines WSL (WSL1 to WSL (m)) are driven by the write scanner 13.
The write scanner 13 sequentially supplies scanning pulses WS (WS1, WS2,... WS (m)) to each of the write control lines WSL1 to WSL (m) arranged in rows at a predetermined timing set. Then, the pixel circuit 10 is line-sequentially scanned in units of rows.

The power supply control lines DSL (DSL1 to DSL (m)) are driven by the drive scanner 12. The drive scanner 12 supplies power pulses DS (DS1, DS2,... DS (m)) to the power supply control lines DSL1 to DSL (m) arranged in a row in accordance with the line sequential scanning by the write scanner 13. To do. The power supply pulse DS (DS1, DS2,... DS (m)) is a pulse voltage that switches to a binary value of the drive voltage Vcc and the initial voltage Vini.
The drive scanner 12 and the write scanner 13 set the timing of the scanning pulse WS and the power supply pulse DS based on the clock ck and the start pulse sp.

The horizontal selector 11 supplies a signal line voltage as an input signal to the pixel circuit 10 to the signal lines DTL1, DTL2,... Arranged in the column direction in accordance with the line sequential scanning by the write scanner 13.
In the present embodiment, the horizontal selector 11 supplies a threshold correction reference voltage Vofs, a video signal voltage Vsig, and a leak suppression voltage V1 as signal line voltages to each signal line.

By the way, in the present embodiment, the pixels are driven to emit light by the STC driving method described later in detail. For example, 3 horizontal lines are defined as 1 unit.
As illustrated, in the m horizontal lines, an operation for light emission is performed for each unit as units U1 to U (z) in units of three lines. The pixel circuits in the same unit are simultaneously subjected to threshold correction operation.
As will be described later, in this case, the horizontal selector 11 outputs, as a signal line voltage for each signal line, a threshold correction reference voltage Vofs, a leak suppression voltage V1, and a video signal for the first line in the unit within three horizontal periods. The voltage Vsig, the video signal voltage Vsig for the second line, and the video signal voltage Vsig for the third line are supplied.

  In the display device of this embodiment, an example of a signal selector referred to in the present invention is the horizontal selector 11, an example of a drive control scanner is a drive scanner, and an example of a writing scanner is a write scanner 13. Become.

FIG. 2 shows a configuration example of the pixel circuit 10. The pixel circuits 10 are arranged in a matrix like the pixel circuits 10 in the configuration of FIG.
In FIG. 2, only one pixel circuit 10 arranged at a portion where the signal line DTL intersects with the write control line WSL and the power supply control line DSL is shown for simplification.

  The pixel circuit 10 includes an organic EL element 1 that is a light emitting element, a storage capacitor Cs, a sampling transistor Ts, and an n-channel thin film transistor (TFT) as a driving transistor Td. Note that the capacitance Coled is a parasitic capacitance of the organic EL element 1.

The storage capacitor Cs has one terminal connected to the source of the drive transistor Td and the other terminal connected to the gate of the drive transistor Td.
The light emitting element of the pixel circuit 10 is, for example, the organic EL element 1 having a diode structure, and includes an anode and a cathode. The anode of the organic EL element 1 is connected to the source of the drive transistor Td, and the cathode is connected to a predetermined wiring (cathode potential Vcat).

The sampling transistor Ts has one end of its drain and source connected to the signal line DTL and the other end connected to the gate of the driving transistor Td.
The gate of the sampling transistor Ts is connected to the write control line WSL.
The drain of the drive transistor Td is connected to the power supply control line DSL.

The light emission driving of the organic EL element 1 is basically as follows.
At the timing when the video signal voltage Vsig is applied to the signal line DTL, the sampling transistor Ts is turned on by the scanning pulse WS supplied from the write scanner 13 by the write control line WSL. As a result, the video signal voltage Vsig from the signal line DTL is written to the storage capacitor Cs.

The drive transistor Td causes the current Ids to flow through the organic EL element 1 by supplying current from the power supply control line DSL to which the drive potential Vcc is applied by the drive scanner 12, and causes the organic EL element 1 to emit light.
At this time, the current Ids becomes a value corresponding to the gate-source voltage Vgs of the driving transistor Td (a value corresponding to the voltage held in the holding capacitor Cs), and the organic EL element 1 emits light with luminance corresponding to the current value. To do.
That is, in the case of this pixel circuit 10, by writing the video signal voltage Vsig from the signal line DTL to the storage capacitor Cs, the gate applied voltage of the drive transistor Td is changed, thereby controlling the value of the current flowing through the organic EL element 1. To obtain the gradation of light emission.

Since the drive transistor Td is designed to always operate in the saturation region, the drive transistor Td becomes a constant current source having a value represented by the following expression 1.
Ids = (1/2) · μ · (W / L) · Cox · (Vgs−Vth) ² (Equation 1)
Where Ids is the current flowing between the drain and source of a transistor operating in the saturation region, μ is the mobility, W is the channel width, L is the channel length, Cox is the gate capacitance, and Vth is the threshold voltage of the driving transistor Td. Yes.
As apparent from Equation 1, the drain current Ids is controlled by the gate-source voltage Vgs in the saturation region. Since the gate-source voltage Vgs is kept constant, the drive transistor Td operates as a constant current source, and can emit the organic EL element 1 with constant luminance.

In this way, basically, in each frame period, an operation is performed in which the video signal value (gradation value) Vsig is written in the storage capacitor Cs in the pixel circuit 10, and thereby the driving transistor is selected according to the gradation to be displayed. The gate-source voltage Vgs of Td is determined.
The drive transistor Td functions as a constant current source for the organic EL element 1 by operating in the saturation region, and a current corresponding to the gate-source voltage Vgs is supplied to the organic EL element 1 so that each frame period is The organic EL element 1 emits light with a luminance corresponding to the gradation value of the video signal.

[2. Pixel circuit operation considered in the process leading to the present invention: division threshold correction]

Here, the pixel circuit operation considered in the process leading to the present invention will be described. This is a circuit operation including a threshold correction operation and a mobility correction operation for compensating for uniformity deterioration due to variations in the threshold and mobility of the driving transistor Td of each pixel circuit 10. In particular, the threshold correction operation is an example in which division threshold correction is performed a plurality of times by dividing within one light emission cycle.

In the pixel circuit operation, the threshold value correction operation and the mobility correction operation itself have been performed conventionally. This necessity will be briefly described.
For example, in a pixel circuit using a polysilicon TFT or the like, the threshold voltage Vth of the drive transistor Td and the mobility μ of the semiconductor thin film constituting the channel of the drive transistor Td may change over time. Further, the transistor characteristics of the threshold voltage Vth and the mobility μ are different for each pixel due to variations in the manufacturing process.
If the threshold voltage and mobility of the drive transistor Td differ from pixel to pixel, the current value flowing through the drive transistor Td varies from pixel to pixel. For this reason, even if the same video signal value (video signal voltage Vsig) is given to all the pixel circuits 10, the light emission luminance of the organic EL element 1 varies from pixel to pixel. As a result, the screen uniformity (uniformity) ) Is damaged.
For this reason, the pixel circuit operation is provided with a correction function for fluctuations in the threshold voltage Vth and the mobility μ.

FIG. 3 shows a timing chart of the operation of the pixel circuit 10 in one cycle (one frame period).
FIG. 3 shows the signal line voltage that the horizontal selector 11 applies to the signal line DTL. In the case of this operation example, the horizontal selector 11 supplies the signal line DTL with the pulse voltage as the threshold correction reference voltage Vofs and the video signal voltage Vsig in one horizontal period (1H) as the signal line voltage.
FIG. 3 shows a scan pulse WS applied to the gate of the sampling transistor Ts by the write scanner 13 via the write control line WSL. The n-channel sampling transistor Ts is turned on when the scanning pulse WS is set to the H level, and is turned off when the scanning pulse WS is set to the L level.
FIG. 3 shows a power pulse DS supplied from the drive scanner 12 via the power control line DSL. The drive voltage Vcc or the initial voltage Vini is given as the power supply pulse DS.
FIG. 3 shows changes in the gate voltage and source voltage of the drive transistor Td as the gate voltage Vg and the source voltage Vs.

A time point ts in the timing chart of FIG. 3 is a start timing of one cycle in which the organic EL element 1 as a light emitting element is driven to emit light, for example, one frame period of image display.
First, at time ts, the power supply pulse DS = the initial potential Vini is set, and the scanning pulse WS is at H level, and the sampling transistor Ts is turned on.

By stopping the supply of the drive voltage Vcc by setting the power supply pulse DS = the initial potential Vini, the gate voltage and the source voltage of the drive transistor Td are lowered, and the organic EL element 1 is extinguished and enters a non-light emission period.
In this case, the source potential = Vini, and the signal line voltage is applied to the gate of the drive transistor Td via the sampling transistor Ts. At this time, since the signal line voltage = the threshold correction reference voltage Vofs, the gate potential = Vofs.
Here, the initial potential Vini is set to satisfy Vofs−Vini> Vth. Vth is a threshold voltage of the drive transistor Td.
That is, as a preparation for threshold correction, the gate-source voltage of the drive transistor is sufficiently widened than the threshold voltage Vth.

Subsequently, the first threshold correction (Vth correction) is performed during the period LT1.
In this case, at the timing when the signal line voltage becomes the threshold correction reference voltage Vofs, the write scanner 13 sets the scanning pulse WS to the H level, and at the same time, the drive scanner 12 sets the power supply pulse DS to the driving voltage Vcc.
Then, the source node rises while the gate of the drive transistor Td is fixed to the threshold correction reference voltage Vofs.
This is because a current flows from the power supply control line DSL toward the anode of the organic EL element 1 by setting the power supply pulse DS to the drive voltage Vcc. As long as the anode potential Vel of the organic EL element 1 is Vel ≦ Vcat + Vthel (threshold voltage of the organic EL element 1), the current of the drive transistor Td is used to charge the storage capacitor Cs and the capacitor Coled. “Vel ≦ Vcat + Vthel” means that the leakage current of the organic EL element 1 is considerably smaller than the current flowing through the drive transistor Td.
For this reason, the anode potential Vel (the source potential of the drive transistor Td) increases with time.

This threshold value correction can be said to be an operation in which the gate-source voltage of the drive transistor Td is set to the threshold voltage Vth. Therefore, the source potential of the drive transistor Td only needs to be raised until the gate-source voltage of the drive transistor Td reaches the threshold voltage Vth.
However, the gate node can be fixed to the threshold correction reference voltage Vofs only during the period of the signal line voltage = Vofs. Then, depending on the frame rate or the like, sufficient time for the source potential to rise cannot be taken by the threshold correction operation once until the gate-source voltage reaches the threshold voltage Vth. Therefore, the threshold value correction is performed in a plurality of times.

For this reason, before the signal line voltage = the video signal voltage Vsig, the threshold value correction is suspended during the period LT2. That is, the write scanner 13 once sets the scanning pulse WS to L level and turns off the sampling transistor Ts.
At this time, since both the gate and the source are floating, a current flows between the drain and the source in accordance with the gate-source voltage Vgs and bootstraps. That is, the gate potential and the source potential rise as shown.

Next, in the period LT3, the second threshold correction is performed. That is, when signal line voltage = threshold correction reference voltage Vofs, the write scanner 13 sets the scanning pulse WS to H level again and turns on the sampling transistor Ts. As a result, the gate voltage of the drive transistor Td = the threshold correction reference voltage Vofs, and the source potential is increased.
Further, the threshold value correction operation is paused in the period LT4. Since the gate-source voltage of the driving transistor Td is closer to the threshold voltage Vth in the second threshold correction, the bootstrap amount in the second pause period is smaller than that in the first pause period.
In addition, the third threshold correction is performed in the period LT5, and after the pause of the period LT6, the fourth threshold correction is performed in the period LT7.
Finally, the gate-source voltage of the drive transistor Td becomes the threshold voltage Vth.
At this time, the source potential (the anode potential Vel of the organic EL element 1) = Vofs−Vth ≦ Vcat + Vthel. (Vcat is the cathode potential, Vthel is the threshold voltage of the organic EL element 1)
In the case of FIG. 3, after the fourth threshold correction period LT7, the scanning pulse WS is set to L level, the sampling transistor Ts is turned off, and the threshold correction operation is completed.

  In this example, the threshold correction is performed four times. However, how many times the threshold correction operation is performed can be appropriately determined according to the configuration and operation of the display device. There are also examples of 3 times, 5 times or more.

  Thereafter, after a period LT8, in a period LT9 in which the signal line voltage is the video signal voltage Vsig, the write scanner 13 sets the scanning pulse WS to the H level, and writing of the video signal voltage Vsig and mobility correction are performed. That is, the video signal voltage Vsig is input to the gate of the drive transistor Td.

The gate potential of the drive transistor Td becomes the potential of the video signal voltage Vsig, but current flows because the power supply control line DSL is at the drive voltage Vcc, and the source potential rises with time.
At this time, if the source voltage of the driving transistor Td does not exceed the sum of the threshold voltage Vthel and the cathode voltage Vcat of the organic EL element 1, the current of the driving transistor Td is used to charge the holding capacitor Cs and the capacitor Coled. That is, the condition is that the leakage current of the organic EL element 1 should be much smaller than the current flowing through the drive transistor Td.
At this time, since the threshold value correcting operation of the drive transistor Td is completed, the current flowing through the drive transistor Td reflects the mobility μ.
Specifically, those with high mobility have a large current amount at this time, and the source rises quickly. On the other hand, when the mobility is low, the amount of current is small and the source rises slowly.
As a result, the gate-source voltage Vgs of the drive transistor Td becomes smaller reflecting the mobility, and becomes a voltage that completely corrects the mobility after a predetermined time has elapsed.

  After writing the video signal voltage Vsig and correcting the mobility in this way, the gate-source voltage Vgs is determined, and the bootstrap and light emission states are entered.

As described above, the pixel circuit 10 performs the operation for light emission of the organic EL element 1 including the threshold value correction operation and the mobility correction operation as the light emission drive operation of one cycle in one frame period.
A current corresponding to the signal potential Vsig can be supplied to the organic EL element 1 regardless of variations in the threshold voltage Vth of the drive transistor Td in each pixel circuit 10 and fluctuations in the threshold voltage Vth due to temporal fluctuations by the threshold correction operation. . That is, variations in the threshold voltage Vth due to manufacturing or changes over time can be canceled, and high image quality can be maintained without causing uneven brightness on the screen.
In addition, since the drain current varies depending on the mobility of the driving transistor Td, the image quality deteriorates due to variations in the mobility of the driving transistor Td for each pixel circuit 10, but the mobility correction increases or decreases the mobility of the driving transistor Td. In response to this, the source potential Vs is obtained. As a result, the gate-source voltage Vgs is adjusted so as to absorb the variation in mobility of the drive transistor Td of each pixel circuit 10, so that the deterioration in image quality due to the variation in mobility is also eliminated.

Further, the threshold correction operation is divided and performed a plurality of times as a one-cycle pixel circuit operation because of the demand for higher frequency display devices.
As the frame rate is increased, the operation time of the pixel circuit is relatively shortened, so that it is difficult to secure a continuous threshold correction period (signal line voltage = threshold correction reference voltage Vofs period). . Thus, by performing the threshold correction operation in a time-sharing manner as described above, a necessary period is secured as the threshold correction period, and the gate-source voltage of the drive transistor Td is converged to the threshold voltage Vth.

[3. Pixel circuit operation considered in the process leading to the present invention: STC driving]

However, if the frame rate is further increased, more division threshold corrections are required to secure the threshold correction operation period.
Here, an STC driving method has been developed as a driving method that can ensure the threshold correction time more appropriately.

The operation of the STC driving method will be described.
In this case, as described with reference to FIG. 1, for example, three horizontal lines are set as one unit, and light emission driving including threshold correction operation is performed in units.

FIG. 4 shows signal line voltages, scanning pulses WS, and power supply pulses DS in the case of the STC driving method.
In FIG. 4, for the unit U1, the scan pulse WS1, power pulse DS1 corresponding to the pixels on the first line in FIG. 1, the scan pulse WS2, power pulse DS2 corresponding to the pixels on the second line, and the third A scan pulse WS3 and a power supply pulse DS3 corresponding to the pixels on the line are shown.
Regarding the unit U2, the scan pulse WS4 and power pulse DS4 corresponding to the pixels on the fourth line, which are omitted in FIG. 1, the scan pulse WS5 and power pulse DS5 corresponding to the pixels on the fifth line, and the sixth line are omitted. The scan pulse WS6 and the power supply pulse DS6 corresponding to the pixels are shown.

The signal line voltage applied to the signal line DTL by the horizontal selector 11 includes a threshold voltage correction reference voltage Vofs and pulse voltages as three video signal voltages Vsig # x, Vsig # y, and Vsig # z in three horizontal periods (3H). Become.
The 3H period is a period corresponding to 3 horizontal lines as one unit.
For example, video signal voltages Vsig applied to the pixel circuits 10 of the unit U1 (first to third lines) by one signal line DTL are indicated as Vsig # 1, Vsig # 2, and Vsig # 3. The video signal voltages Vsig applied to the pixel circuits 10 of the unit U2 (fourth to sixth lines) are indicated as Vsig # 4, Vsig # 5, and Vsig # 6.
Here, it is assumed that the video signal voltage Vsig is applied so that the entire screen emits light with the same luminance, and Vsig # 1 = Vsig # 2 = Vsig # 3 = Vsig # 4 = Vsig # 5 = Vsig # 6 ... Vsig # x = Vsig # y = Vsig # z. Of course, during normal video display, each video signal voltage Vsig has a voltage value corresponding to the luminance to be emitted from the corresponding pixel circuit 10.
The horizontal selector 11 applies the threshold correction reference voltage Vofs, the video signal voltages Vsig # 1, Vsig # 2, and Vsig # 3 to the signal line DTL during a certain 3H period (period in which the video signal voltage Vsig of the unit U1 is output). Will be given to.
In the next 3H period, the threshold correction reference voltage Vofs, video signal voltages Vsig # 4, Vsig # 5, and Vsig # 6 are applied to the signal line DTL as a period for outputting the video signal voltage Vsig of the unit U2.

In the case of this STC driving method, the write scanner 13 outputs a scanning pulse WS to each pixel circuit in one unit so that a threshold correction operation is simultaneously performed within one light emission cycle of each pixel circuit. . That is, the scanning pulse WS is output so that the threshold correction reference voltage Vofs is input to each pixel circuit simultaneously.
The driving by the scanning pulse WS and the power supply pulse DS for the pixel circuits 10 in each line is as follows.

For the pixel circuit 10 in the first line, the power supply pulse DS1 is set to the initial potential Vini at time t0, the light emission of the previous frame is completed, and the light emission operation of one cycle of the current frame is started.
For the pixel circuit 10 on the second line, the power supply pulse DS2 is set to the initial potential Vini at time t1, the light emission of the previous frame is completed, and the light emission operation for one cycle of the current frame is started.
For the pixel circuit 10 on the third line, the power supply pulse DS3 is set to the initial potential Vini at time t2, the light emission of the previous frame is completed, and the light emission operation for one cycle of the current frame is started.
Note that the light emission end timing of each pixel of the unit U1 is different from the time points t0, t1, and t2 because the light emission start timings at the time points t16, t18, and t20 described later are shifted. That is, this is because the light emission period lengths of the pixel circuits 10 of the respective lines are made the same so that a visually recognized luminance difference does not occur.

When each pixel of the unit U1 does not emit light at time points t0, t1, and t2, first, threshold correction preparation is simultaneously performed at time points t4 to t5.
That is, during the period of signal line voltage = threshold correction reference voltage Vofs, the scanning pulses WS1, WS2, and WS3 are simultaneously set to the H level.
As a result, the gate voltage Vg of the driving transistor of each pixel circuit 10 in the first to third lines is set to the threshold correction reference voltage Vofs. Further, the source potential = Vini.
Since the initial potential Vini is set so that Vofs−Vini> Vth, the gate-source voltage of the driving transistor is sufficiently widened than the threshold voltage Vth in preparation for threshold correction.

Next, as the time points t11 to t12, the first threshold correction is simultaneously performed in the pixel circuits 10 of the first line to the third line.
That is, during the period of signal line voltage = threshold correction reference voltage Vofs, the scan pulses WS1, WS2, and WS3 are simultaneously set to the H level, and the power supply pulses DS1, DS2, and DS3 are simultaneously set to the drive voltage Vcc.
As a result, in each pixel circuit 10 in the first to third lines, the source node rises while the gate of the drive transistor Td is fixed to the threshold correction reference voltage Vofs. That is, the gate-source voltage Vgs approaches the threshold voltage Vth.

The first threshold correction operation ends when the scanning pulses WS1, WS2, and WS3 are simultaneously set to the L level, and the threshold correction is suspended during the period in which the signal line voltage is the video signal voltage Vsig.
Then, at time points t13 to t14, the second threshold correction is simultaneously performed in the pixel circuits 10 of the first line to the third line.
That is, during the period of signal line voltage = threshold correction reference voltage Vofs, the scan pulses WS1, WS2, and WS3 are simultaneously set to the H level, and the second threshold correction operation is performed.
In this example, the threshold correction operation is performed in two steps, but the gate-source voltage Vgs of the drive transistor Td becomes the threshold voltage Vth by the second threshold correction operation, and the threshold correction operation is completed. .

Subsequently, the video signal voltage Vsig is sequentially written.
First, at time t15 to t16 when the video signal voltage Vsig # 1 is applied as the signal line voltage by the horizontal selector 11, writing is performed to the pixel circuit 10 of the first line. That is, the scanning pulse WS1 is set to the H level from time t15 to t16.
As a result, in each pixel circuit 10 in the first line, the video signal voltage Vsig # 1 is written to the gate of the drive transistor Td, the current flows because the power supply control line DSL is at the drive voltage Vcc, and the source potential is Ascending with time, mobility correction is performed.
In this way, the writing of the video signal voltage Vsig # 1 and the mobility correction are performed, the gate-source voltage Vgs is determined, and the state shifts to the light emitting state after time t16.

In addition, at time t17 to t18 when the video signal voltage Vsig # 2 is applied as the signal line voltage by the horizontal selector 11, the scanning pulse WS2 is set to the H level, and writing is performed on the pixel circuits 10 on the second line. That is, in each pixel circuit 10 on the second line, the video signal voltage Vsig # 2 is written to the gate of the drive transistor Td, and mobility correction is performed. After time t18, the light emission state is entered.
Further, at time t19 to t20 when the video signal voltage Vsig # 3 is applied as the signal line voltage by the horizontal selector 11, the scanning pulse WS3 is set to the H level, and writing is performed to the pixel circuit 10 on the third line. In each pixel circuit 10 on the third line, the video signal voltage Vsig # 3 is written to the gate of the driving transistor Td, mobility correction is performed, and the state shifts to the light emitting state after time t20.

The light emission operation in one cycle of each pixel circuit of the unit U1 is as described above.
In the unit U2, the same operation is performed for the pixel circuits 10 in the fourth line to the sixth line with a 3H period offset from the unit U1.
That is, at time points t6, t7, and t8, the power supply pulses DS4, DS5, and DS6 are set to the initial potential Vini, respectively, and the light emission of the previous frames of the pixel circuits 10 of the fourth to sixth lines is sequentially terminated, One cycle of light emission is started.
At time points t9 to t10, the scan pulses WS4, WS5, and WS6 are simultaneously set to the H level, and threshold correction preparation is simultaneously performed in the pixel circuits 10 of the fourth to sixth lines. As a result, the gate voltage Vg of the drive transistor of each pixel circuit 10 in the fourth to sixth lines is set to the threshold correction reference voltage Vofs. Further, the source potential = Vini. That is, the gate-source voltage of each driving transistor is sufficiently widened than the threshold voltage Vth.

Next, at time points t13 to t14, the scan pulses WS4, WS5, and WS6 are simultaneously set to the H level, and the power supply pulses DS4, DS5, and DS6 are simultaneously set to the drive voltage Vcc. As a result, the first threshold correction is simultaneously performed in the pixel circuits 10 of the fourth to sixth lines.
Further, after the correction suspension period, at time points t21 to t22, the scanning pulses WS4, WS5, and WS6 are simultaneously set to the H level, and the second-time threshold correction is simultaneously performed in the pixel circuits 10 of the fourth to sixth lines.

The video signal voltages Vsig # 4, Vsig # 5, and Vsig # 6 are sequentially written.
First, at time points t23 to t24 where the signal line voltage is equal to the video signal voltage Vsig # 4, the scanning pulse WS4 is set to the H level, and the writing of the video signal voltage Vsig # 4 to the pixel circuit 10 on the fourth line is performed. Mobility correction is performed. After time t24, the light emission state is entered.
At time points t25 to t26 when the signal line voltage = the video signal voltage Vsig # 5, the scanning pulse WS5 is set to the H level, and the video signal voltage Vsig # 5 is written and moved to the pixel circuit 10 on the fifth line. Degree correction is performed. After time t26, the light emission state is entered.
Further, at time points t27 to t28 when the signal line voltage is equal to the video signal voltage Vsig # 6, the scanning pulse WS6 is set to the H level, and the video signal voltage Vsig # 6 is written and moved to the pixel circuit 10 on the sixth line. Degree correction is performed. Then, after time t28, the light emission state is entered.

In the STC driving method, the threshold value correction operation and the like are collectively performed in units as described above.
Performing the threshold correction operation for all three lines means that 3H can be used for one operation in which the signal line voltage becomes the threshold correction reference voltage Vofs / video signal voltage Vsig. That is, it takes a long time for the threshold correction operation, which is an effective driving method for increasing the operation margin even when the frame rate is increased and the pulse transient is increased as the panel size is increased.
FIGS. 5A and 5B show threshold correction times in the case of normal division threshold correction (example in FIG. 3) and STC driving.
When performing the division threshold correction as shown in FIG. 3 as shown in FIG. 5A, one threshold correction operation is limited within a period in which the signal line voltage is the threshold correction reference voltage Vofs within the 1H period. The On the other hand, in the case of the above-described STC driving, as shown in FIG. 5B, the operation in units of 3H periods can increase the period during which the signal line voltage is the threshold correction reference voltage Vofs. In addition, the period of one threshold correction operation can be made longer.

Describe in detail. The time required other than the threshold correction time and the video signal writing time is a transition time (xτsig) of the signal line voltage pulse and a transition time (yτws) of the scanning pulse WS. In the case of the normal operation of FIG. 5A, the total of them is 2 (xτsig + yτws). For 3 lines, 6 (xτsig + yτws).
On the other hand, in the case of the three-line STC driving method, the total transition time is 4 (xτsig + yτws) as shown in FIG. That is, the time margin for threshold correction can be increased by 2 (xτsig + yτws).
As described above, in the case of the X-line STC driving method, the time margin is increased by (X−1) (xτsig + yτws) compared to the normal driving.
For this reason, STC driving can be said to be an effective driving method for increasing the operation margin even when the pulse rate increases as the frame rate increases and the panel size increases.

In this way, the STC driving method is advantageous when considering a high frame rate and a large panel by making the threshold correction operation period longer.
However, in the case of STC driving, there are concerns about the following problems.
Pay attention to the waiting time from the end of the last threshold correction to signal writing. For example, in the case of the unit U1 in FIG. 4, the second threshold correction operation from the time point t13 to t14 is the final threshold value correction, and waiting from the end time point t14 to the writing of the video signal voltages Vsig1, Vsig2, and Vsig3. It's time.

FIG. 6 shows a gate voltage and a source voltage of the drive transistor Td in the pixel circuit 10 in each line by extending the period from the last threshold correction in this unit U1 to signal writing.
Vg1 and Vs1 are the gate voltage and source voltage of the drive transistor Td of the pixel circuit 10 in the first line.
Vg2 and Vs2 are the gate voltage and source voltage of the drive transistor Td of the pixel circuit 10 in the second line.
Vg3 and Vs3 are the gate voltage and source voltage of the drive transistor Td of the pixel circuit 10 in the third line.
The gate-source voltage of the drive transistor Td of the pixel circuit 10 in each line is shown as Vgs1, Vgs2, and Vgs3.

After the final threshold correction is performed at time points t13 to t14, the gate-source voltage Vgs≈Vth is satisfied in the drive transistor Td of each line.
Although the threshold correction is completed and Vgs≈Vth, a minute leak current continues to flow between the drain and source of the drive transistor Td. (Generally, current Ids after threshold correction≈1 pA).

Here, a waiting time WT (waiting term) from the end of threshold correction to video signal writing in the same unit differs for each line.
That is, if the waiting times of the first, second, and third lines in the unit U1 are WT1, WT2, and WT3, respectively, the relationship is WT1 <WT2 <WT3.
The longer the lower line, the longer the waiting time. The increase in the source voltage Vs due to the leakage current of the driving transistor Td is also large, and the gate-source voltage Vgs in the same unit immediately before the video signal voltage Vsig is written is Vgs1>Vgs2> Vgs3. It becomes.
That is, as the lower line has a longer waiting time WT, the rise of the source voltage Vs increases due to the leakage current, and the gate-source voltage Vgs decreases, which causes the gate-source before the video signal voltage Vsig is written. A difference in voltage Vgs occurs.
Then, if the same video signal voltage (Vsig1 = Vsig2 = Vsig3) is written in the unit after that, the shading becomes darker as the lower line of the unit becomes darker as shown in FIG. It is visually recognized and the uniformity deteriorates.

[4. Pixel Circuit Operation of Embodiment]

The pixel circuit operation of the present embodiment is to prevent uniformity deterioration as described above while employing STC driving.
The pixel circuit operation of the embodiment will be described with reference to FIGS. FIG. 8 shows the signal line voltage, the scanning pulses WS (WS1 to WS6), and the power supply pulses DS (DS1 to DS6) for the units U1 and U2 in the same format as in FIG.

  The signal line voltage applied to the signal line DTL by the horizontal selector 11 includes a threshold correction reference voltage Vofs, a leak suppression voltage V1, and three video signal voltages Vsig # x, Vsig # y, and Vsig in three horizontal periods (3H). It becomes a pulse voltage as #z. That is, the horizontal selector 11 differs from the STC drive in FIG. 4 in that the leak suppression voltage V1 is applied as the signal line voltage next to the threshold correction reference voltage Vofs. Leakage suppression voltage V1 <threshold correction reference voltage Vofs.

The driving by the scanning pulse WS and the power supply pulse DS for the pixel circuits 10 in each line is as follows.
For each of the pixel circuits 10 in the first to third lines, the power supply pulses DS1, DS2, and DS3 are set to the initial potential Vini at the time points t0, t1, and t2, respectively, and the emission of the previous frame is completed as in FIG. It is.

If each pixel of the unit U1 does not emit light at time points t0, t1, and t2, first, threshold correction preparation is simultaneously performed at time points t4 to t5 ′.
That is, during the period of signal line voltage = threshold correction reference voltage Vofs, the scanning pulses WS1, WS2, and WS3 are simultaneously set to the H level.
As a result, the gate voltage Vg of the drive transistor of each pixel circuit 10 in the first line to the third line is set to the threshold correction reference voltage Vofs, and the source potential = Vini, so that the gate-source voltage of the drive transistor Td is The threshold voltage Vth is sufficiently widened.
Note that the scanning pulses WS1, WS2, and WS3 are set to the L level at time t5 ′ before the signal line voltage becomes the leakage suppression voltage V1.

Next, as time points t11 to t12 ′, the first threshold correction is simultaneously performed in the pixel circuits 10 of the first to third lines.
That is, during the period of signal line voltage = threshold correction reference voltage Vofs, the scan pulses WS1, WS2, and WS3 are simultaneously set to the H level, and the power supply pulses DS1, DS2, and DS3 are simultaneously set to the drive voltage Vcc.
As a result, in each pixel circuit 10 in the first to third lines, the source node rises while the gate of the drive transistor Td is fixed to the threshold correction reference voltage Vofs. That is, the gate-source voltage Vgs approaches the threshold voltage Vth.

The first threshold value correction operation ends when the scanning pulses WS1, WS2, and WS3 are set to the L level at time t12 ′ before the signal line voltage becomes the leakage suppression voltage V1, and the signal line voltage is reduced to the leakage suppression voltage V1 and the video. The threshold value correction is suspended during the period when the signal voltage is Vsig.
Then, at time points t13 to t14, the second threshold correction is simultaneously performed in the pixel circuits 10 of the first line to the third line. In this example, the second threshold correction is the final threshold correction operation in the division correction.
This last threshold value correction operation is executed while the scanning pulses WS1, WS2, and WS3 are simultaneously set to the H level during the period in which the signal line voltage is the threshold value correction reference voltage Vofs. By this threshold value correcting operation, the gate-source voltage Vgs of the driving transistor Td becomes the threshold voltage Vth, and the threshold value correcting operation is completed.
However, in this case, even when the threshold correction is completed, the scanning pulses WS1, WS2, and WS3 are kept at the H level even when the signal line voltage becomes the leakage suppression voltage V1 as it is. As will be described later with reference to FIG. 9, after the threshold correction operation is completed, the gate voltage Vg of the drive transistor Td of each pixel circuit 10 is set to the leakage suppression voltage V1.

Thereafter, the video signal voltage Vsig is sequentially written.
First, at time t15 to t16 when the video signal voltage Vsig # 1 is applied as the signal line voltage by the horizontal selector 11, the scanning pulse WS1 is set to the H level, and the video signal voltage Vsig # for the pixel circuit 10 in the first line. 1 is written and mobility correction is performed. After time t16, the light emission state is entered.
In addition, at time t17 to t18 when the video signal voltage Vsig # 2 is applied as the signal line voltage by the horizontal selector 11, the scanning pulse WS2 is set to the H level, and the video signal voltage Vsig # for the pixel circuit 10 in the second line. 2 writing and mobility correction are performed. After time t18, the light emission state is entered.
Further, at time t19 to t20 when the video signal voltage Vsig # 3 is applied as the signal line voltage by the horizontal selector 11, the scanning pulse WS3 is set to the H level, and the video signal voltage Vsig # for the pixel circuit 10 in the third line. 3 and mobility correction are performed. After time t20, the light emission state is entered.

In the unit U2, the same operation is performed for the pixel circuits 10 in the fourth line to the sixth line with a 3H period offset from the unit U1.
That is, at time points t6, t7, and t8, the power supply pulses DS4, DS5, and DS6 are set to the initial potential Vini, respectively, and the light emission of the previous frames of the pixel circuits 10 of the fourth to sixth lines is sequentially terminated, One cycle of light emission is started.
At time points t9 to t10 ′, the scanning pulses WS4, WS5, and WS6 are simultaneously set to the H level, and the threshold correction preparation is simultaneously performed in the pixel circuits 10 of the fourth to sixth lines.
Next, at time t13 to t14 ′, the scan pulses WS4, WS5, WS6 are simultaneously set to the H level, and the power supply pulses DS4, DS5, DS6 are simultaneously set to the drive voltage Vcc. As a result, the first threshold correction is simultaneously performed in the pixel circuits 10 of the fourth to sixth lines.
Further, after the correction suspension period, at time points t21 to t22, the scanning pulses WS4, WS5, and WS6 are simultaneously set to the H level, and the second (last) threshold correction is simultaneously performed in the pixel circuits 10 of the fourth to sixth lines. Done. At this time, the scan pulses WS4, WS5, and WS6 are kept at the H level even when the signal line voltage becomes the leakage suppression voltage V1 after the threshold correction is completed. Thus, after the threshold correction operation is completed, the gate voltage Vg of the drive transistor Td of each pixel circuit 10 is set to the leakage suppression voltage V1.
Thereafter, the video signal voltages Vsig # 4, Vsig # 5, and Vsig # 6 are sequentially applied to the pixel circuits 10 of the fourth to sixth lines at time points t23 to t24, time points t25 to t26, and time points t27 to t28. Writing is performed, and each shifts to a light emitting state.

In the STC driving method of FIG. 8, in the threshold correction before the final threshold correction in the division correction (first threshold correction in the example of FIG. 8), the sampling transistor Ts is turned on by the scanning pulse WS with the signal line voltage = Vofs. Then, threshold correction is performed.
With respect to the final threshold correction (second threshold correction in the example of FIG. 8), the signal line voltage = Vofs to V1 is set to the timing at which the sampling transistor Ts is turned on by the scanning pulse WS.
That is, when the threshold correction is completed, the leak suppression voltage V1 is finally written to the gate of the drive transistor Td.

9 shows, in the same manner as in FIG. 6, for each pixel circuit 10 of the unit U1, a scanning pulse WS (WS1 to WS3) during the period from the final threshold correction to the writing of the video signal voltage, and the gate of the driving transistor Td. The voltage Vg (Vg1-Vg3) and the source voltage Vs (Vs1-Vs3) are shown.
As shown in the figure, in the pixel circuits 10 of each line, at the time of final threshold correction, the gate voltages Vg1, Vg2, and Vg3 are respectively set to the threshold correction reference voltage Vofs and threshold correction is performed. As a result, the gate-source voltage Vgs of each drive transistor Td is set to Vgs = Vth. Thereafter, the gate voltages Vg1, Vg2, and Vg3 are set to the leakage suppression voltage V1.

Here, when the gate-source voltage after the final threshold correction in the case of FIG. 6 is X (V) = Vofs−Vth, the gate-source voltage X ′ (V) in this example is the write gain (gate If the source node change ratio relative to the node change is Gin (%),
X ′ = X− (Vofs−V1) × Gin <X
It becomes.
Although the TFT characteristics shown in FIG. 10 are shown, inputting the leakage suppression voltage V1 to the gate voltage Vg of the drive transistor Td corresponds to shifting the operating point from X (V) to X ′ (V).
Thus, the leakage current of the drive transistor Td is suppressed by the amount that the gate-source voltage Vgs is reduced. Actually, there is a slight leakage current, but the leakage suppression voltage V1 can be set to have almost no influence by setting the leakage suppression voltage V1.
Then, as shown in FIG. 9, the fluctuation of the gate-source voltage Vgs during the waiting time until the video signal voltage Vsig is written can be suppressed.

As described in the case of FIG. 6, in the pixel circuits 10 of the first, second, and third lines in the unit U1, the wait times WT1, WT2, and WT3 have a relationship of WT1 <WT2 <WT3. Due to this difference in waiting time, a difference in the amount of increase in the source voltage Vs occurs, and the amount of variation in the gate-source voltage Vgs differs in each pixel circuit.
However, in the case of the present embodiment, as shown in FIG. 9, the leakage current during the waiting time is suppressed by setting the gate voltage Vg of the driving transistor Td = leakage suppression voltage V1. That is, an increase in the source voltage Vs is suppressed, and as a result, a difference in fluctuation amount of the gate-source voltage Vgs of each drive transistor Td is suppressed.
Then, when the video signal voltages Vsig # 1, Vsig # 2, and Vsig # 3 are written at time t15 to t16, time t17 to t18, and time t19 to t20, respectively (Vsig # 1 = Vsig # 2 = Vsig # 3), the current value for each line in the unit becomes equal.
For this reason, it is possible to prevent in-unit shading as shown in FIG. 7, and uniform uniformity is realized.

As described above, according to the present embodiment, in the STC driving method, it is possible to prevent shading in the unit while obtaining an advantage in securing the threshold correction period.
As a result, a display driving method that can appropriately cope with a high frame rate and a large panel can be achieved.

Although the embodiment has been described above, the present invention is not limited to the above example. For example, how many times the division threshold correction is performed in STC driving is determined according to the actual frame rate, panel size, and the like. For example, the threshold value correction may be performed by dividing it into three or more times. Of these, after the final threshold correction, the leakage suppression voltage V1 may be input to the gate of the drive transistor Td.
Further, if the threshold correction can be completed by one threshold correction operation, the division threshold correction is not necessarily required. In this case, since the first threshold correction is the final threshold correction, the leak suppression voltage V1 may be input to the gate immediately after that.
In addition, it is only an example that three lines are used as one unit for STC driving, and STC driving may be performed using four or more lines as one unit.

  DESCRIPTION OF SYMBOLS 1 Organic EL element, 10 pixel circuit, 11 horizontal selector, 12 drive scanner, 13 write scanner, 20 pixel array part, Cs holding capacity, Ts sampling transistor, Td drive transistor

Claims (4)

The driving voltage is applied between the light-emitting element and the drain-source to apply a current corresponding to the gate-source voltage to the light-emitting element, and the signal line voltage is driven to be electrically connected to the light-emitting element. A pixel circuit having a sampling transistor that is input to the gate of a transistor and a storage capacitor that is connected between the gate and source of the drive transistor and that holds the threshold voltage of the drive transistor and the input video signal voltage A pixel array arranged in
When a plurality of horizontal lines are formed as one unit for each pixel circuit of the pixel array, each signal line arranged in a row on the pixel array in a plurality of horizontal periods corresponding to the number of horizontal lines of one unit. A signal selector for supplying a threshold correction reference voltage, a leakage suppression voltage, and a video signal voltage for each of the pixel circuits in the unit as the signal line voltage;
A drive control scanner that applies a power pulse to each power control line arranged in a row on the pixel array and applies a drive voltage to the drive transistor of the pixel circuit;
A scan pulse is applied to each write control line arranged in a row on the pixel array to control the sampling transistor of the pixel circuit, and each pixel is used as the scan pulse for each pixel circuit in one unit. The threshold correction reference voltage is input to each pixel circuit so that the threshold correction operation is performed simultaneously within one light emission cycle of the circuit, and the leak suppression voltage is input to each pixel circuit after the threshold correction operation is completed. A writing scanner that outputs the scan pulse for controlling the sampling transistor so as to sequentially input a video signal voltage for each pixel circuit in the unit;
A display device comprising:   The writing scanner performs a plurality of threshold correction operations in each pixel circuit within a period of one light emission cycle, and sets the leak suppression voltage after the last threshold correction operation among the plurality of threshold correction operations. The display device according to claim 1, wherein the scanning pulse is output so as to be input to each pixel circuit.   The display device according to claim 2, wherein the leakage suppression voltage is a voltage lower than the threshold correction reference voltage. The driving voltage is applied between the light-emitting element and the drain-source to apply a current corresponding to the gate-source voltage to the light-emitting element, and the signal line voltage is driven to be electrically connected to the light-emitting element. A pixel circuit having a sampling transistor that is input to the gate of a transistor and a storage capacitor that is connected between the gate and source of the drive transistor and that holds the threshold voltage of the drive transistor and the input video signal voltage A pixel array arranged in
A signal selector for supplying the signal line voltage to each signal line arranged in a row on the pixel array;
A drive control scanner that applies a power pulse to each power control line arranged in a row on the pixel array and applies a drive voltage to the drive transistor of the pixel circuit;
A write scanner for controlling the sampling transistor of the pixel circuit by applying a scan pulse to each write control line arranged in a row on the pixel array;
As a display driving method for a display device comprising:
When the signal selector has a plurality of horizontal lines as one unit for each pixel circuit of the pixel array, the signal line voltage is applied to each signal line in a plurality of horizontal periods corresponding to the number of horizontal lines of one unit. , Supplying a threshold correction reference voltage, a leakage suppression voltage, and a video signal voltage for each of the pixel circuits in the unit,
The writing scanner is provided for each pixel circuit in one unit.
The threshold correction reference voltage is input to each pixel circuit so that the threshold correction operation is performed simultaneously within one light emission cycle period of each pixel circuit,
After the threshold correction operation is completed, the leak suppression voltage is input to each pixel circuit,
After that, by sequentially inputting the video signal voltage for each pixel circuit in the unit,
A display driving method in which light emission with luminance corresponding to an input video signal voltage is performed in each pixel circuit.