JP2010146402A - Smoke sensor - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a smoke sensor for simplifying and omitting a means for preventing disturbance light from being incident on a light-receiving unit. <P>SOLUTION: A current-voltage converting circuit 2 is provided with: a second feedback circuit 5 which outputs an output voltage Vout according to the magnitude of a low-frequency component at or lower than a predetermined second cut-off frequency; and a correcting transistor Q1 which supplies a correction current Ic2 according to the magnitude of the output of the second feedback circuit 5 through a connection terminal Tin of a conversion unit 3 to a photo-diode PD. The second feedback circuit 5 comprises a second integration circuit 9 which integrates the output voltage Vout of the conversion unit 3; and a sample-and-hold circuit 10 which samples and holds the output of the second integration circuit 9 in a sensing period, during which a pulsed detection signal is input. <P>COPYRIGHT: (C)2010,JPO&INPIT

Description

  The present invention relates to a smoke detector that detects and reports smoke generated during a fire.

  Conventionally, as this kind of smoke detector A, an LED (light emitting unit) 6 that has a detection space in the housing 20 as shown in FIG. 11A and outputs light intermittently toward the detection space. And a photodiode (light receiving unit) PD that is arranged at a position where direct light from the LED 6 is not incident and converts received light into current is known (for example, see Patent Document 1). In this smoke detector A, when smoke flows into the detection space, the light from the LED 6 is diffused and reflected by the smoke in the detection space, so that the amount of light received from the LED 6 at the photodiode PD increases. The amount of current flowing through the diode PD increases.

  The LED 6 and the photodiode PD constitute an optical block 25 together with a light projecting lens 23 disposed in front of the LED 6 and a light receiving lens 24 disposed in front of the photodiode PD. The housing 20 has an opening formed on the lower surface and a body 26 housing the optical block 25 so that light from the LED 6 is emitted toward the opening, and a bottomed cylindrical shape with an upper surface opening. A cover 27 coupled to the body 26 is provided so as to cover the opening. An opening window for taking in smoke is formed on the peripheral wall of the cover 27, and the detection space is formed in the cover 27. Here, in the cover 27, an insect net 28 for preventing insects from entering the detection space, and a labyrinth 21 for preventing disturbance light from entering the detection space are arranged so as to surround the detection space. The labyrinth 21 is complicated to prevent the incidence of various disturbance lights from fluorescent lamps and incandescent lamps, and to prevent the light of the LED 6 from entering the photodiode PD in the absence of smoke in the detection space. A complicated structure with an optical path is adopted.

  In this type of smoke detector A, as shown in FIG. 11B, a current-voltage conversion circuit that converts the current flowing through the photodiode PD into a voltage and outputs it to the circuit block 1 housed in the housing 20. (IV conversion circuit) 2 is provided. Further, the output voltage of the current-voltage conversion circuit 2 is input to the alarm determination circuit 14 which is a determination processing unit through the amplifier circuit 12 and the filter circuit 13, and when the change amount of the output voltage exceeds a predetermined fire determination level, The alarm circuit 15 (buzzer or the like) issues a report. The circuit block 1 includes a power supply circuit 16 that supplies power to each circuit, an interlocking circuit 17 that links other reporting means and the like, and a transistor Tr1 (see FIG. 12) connected in series with the LED 6. An LED drive circuit 18 that periodically emits light is provided.

  The current-voltage conversion circuit 2 used here has a conversion unit 3 formed by connecting a conversion resistor R2 between an inverting input terminal and an output terminal of an operational amplifier OP1, for example, as shown in FIG. When the current I1 flows through the photodiode PD inserted between the terminal and the circuit ground, the output voltage Vout whose voltage value varies according to the variation of the current I1 is output to the output terminal Tout. In the example of FIG. 12, since the reference voltage Vs is applied to the non-inverting input terminal, the output voltage Vout is expressed by Vout = Vs + (I1 × r2) if the resistance value of the conversion resistor R2 is r2. In short, the current-voltage conversion circuit 2 uses the output voltage Vout in a steady state where the photodiode PD does not receive the light from the LED 6 as an operating point, and uses the operating point as a reference according to the fluctuation of the current I1 flowing through the photodiode PD. The output voltage Vout is varied.

  In recent years, since the installation is simple, the demand for the smoke detector A using a battery as a power source is increasing. When the battery is used as the power source of the smoke detector A, it is necessary to drive the smoke detector A intermittently in order to suppress the average power consumption of the smoke detector A and extend the life of the battery. In this case, the power supply to the current-voltage conversion circuit 2 shown in FIG. 13A is also intermittently performed. Therefore, the LED 6 outputs pulsed light while power is supplied to the current-voltage conversion circuit 2 as shown in FIG. Here, when smoke flows into the detection space and the photodiode PD receives light from the LED 6, the change amount ΔV of the output voltage Vout of the current-voltage conversion circuit 2 increases as shown by the solid line in FIG. The fire judgment level in the figure will be reached. On the other hand, if there is no smoke in the detection space, as shown by the broken line in FIG. 13C, the change amount ΔV of the output voltage becomes small and does not reach the fire determination level.

  In the current-voltage conversion circuit 2 as shown in FIG. 12, the dynamic range of the operational amplifier OP1 is defined between the power supply voltage VDD of the operational amplifier OP1 and the ground GND as shown in FIG. The output voltage Vout described above fluctuates within this dynamic range. Therefore, when the current I1 flowing through the photodiode PD exceeds a certain level, the output voltage Vout is saturated.

  For example, in the smoke detector A described above, although the labyrinth 21 is provided, the detection space cannot be completely blocked from the outside, so that a slight disturbance light may enter the photodiode PD. Normally, disturbance light has a small temporal variation, and when the photodiode PD receives the disturbance light, a current (hereinafter referred to as “low frequency component”) having a small temporal variation flows through the photodiode PD. When the low frequency component included in the current I1 flowing through the photodiode PD exceeds a certain level, the output voltage Vout may be saturated.

  That is, if the current I1 flowing through the photodiode PD does not contain a low frequency component, the operating point of the output voltage Vout becomes the reference voltage Vs as shown in FIG. The voltage Vout also fluctuates following this fluctuation. On the other hand, if the current I1 contains a low frequency component, the operating point of the output voltage Vout increases as shown in FIG. When the current I1 increases, the output voltage Vout may be saturated on the way. In particular, when the low frequency component is large and the operating point of the output voltage Vout rises to near the power supply voltage VDD as shown in FIG. 14C, the output voltage Vout is saturated regardless of the fluctuation of the current I1. Therefore, the output voltage Vout does not follow the increase in the current I1.

  For example, when the power supply voltage VDD of the operational amplifier OP1 is 5V, if the resistance value r2 of the conversion resistor R2 is 1 MΩ and the reference voltage Vs is 1V, the current I1 flowing through the photodiode PD is 4 μA and the voltage across the conversion resistor R2 The drop is 4V, and as a result, the output voltage Vout of the current-voltage conversion circuit 2 becomes 5V and is saturated. In this state, even if the photodiode PD receives the light from the LED 6 and the pulsed current I1 flows to the photodiode PD, the output voltage Vout of the current-voltage conversion circuit 2 is saturated, so that it fluctuates further. There is a possibility that the change amount ΔV of the output voltage Vout may be reported without reaching the fire determination level.

However, in the above-described smoke detector A, the labyrinth 21 prevents disturbance light from entering the detection space. Therefore, generally, the current I1 in which a low-frequency component that flows as the output voltage Vout becomes saturated flows through the photodiode PD Is not included.
Japanese Patent No. 2783945 (page 1-2)

  By the way, in the above-described smoke detector A, the structure of the labyrinth 21 that prevents the incidence of ambient light into the detection space is complicated, and the cost for manufacturing the labyrinth 21 hinders the cost reduction of the entire smoke detector A. Therefore, it is desired to reduce the cost of the smoke detector A by simplifying the structure of the labyrinth 21 as much as possible or omitting the labyrinth 21 itself. However, if the labyrinth 21 is simplified or omitted, the disturbance light received by the photodiode PD becomes strong, and the low frequency component included in the current I1 flowing through the photodiode PD becomes large and the output voltage Vout is saturated. There is. In particular, when the battery is used as the power source of the smoke detector A as described above, the output voltage Vout is likely to be saturated because the power supply voltage of the operational amplifier OP1 is low and the dynamic range of the operational amplifier OP1 is relatively narrow.

  The present invention has been made in view of the above reasons, and an object of the present invention is to provide a smoke detector that can simplify or omit means for preventing disturbance light from entering the light receiving unit.

  According to the first aspect of the present invention, a light emitting unit that outputs pulsed light during a predetermined sensing period toward the detection space, and direct light from the light emitting unit is not incident and diffusely reflected by smoke flowing into the detection space. The light receiving unit is arranged at a position where light from the light emitting unit is incident, and a current corresponding to the received light intensity is supplied to the light receiving unit via a connection terminal connected to the light receiving unit. A current-voltage conversion circuit having a conversion unit that outputs an output voltage whose voltage value varies according to the output terminal, and a determination processing unit that determines the presence or absence of smoke in the detection space based on the output voltage, The current-voltage conversion circuit extracts a low-frequency component below the cutoff frequency lower than the frequency of the pulse-shaped detection signal generated when the light-receiving unit receives light from the light-emitting unit from the output voltage, and the low-frequency component Correction power of the size corresponding to It characterized by having a low-frequency correction means supplies the light receiving portion through the connection terminals of the conversion unit.

  According to this configuration, when a low-frequency component is included in the current flowing through the light receiving unit, feedback is applied between the output terminal and the connection terminal to suppress saturation of the output voltage due to the low-frequency component. it can. That is, the low frequency correction means supplies a correction current having a magnitude corresponding to the low frequency component to the light receiving unit via the connection terminal of the conversion unit, so that the low frequency is converted from the current supplied from the conversion unit to the light receiving unit. The component is subtracted, and the influence of the low frequency component on the output voltage is suppressed. Therefore, even when the disturbance light received by the light receiving unit is strong and the low frequency component included in the current flowing through the light receiving unit is relatively large, the influence of the low frequency component on the output voltage generated at the output terminal of the conversion unit is suppressed. be able to. As a result, it is possible to simplify or omit the means for preventing disturbance light from entering the light receiving unit.

  According to a second aspect of the present invention, in the first aspect of the invention, the low frequency correcting means outputs a voltage corresponding to a low frequency component equal to or lower than a first cutoff frequency lower than the frequency of the detection signal in the output voltage. A first feedback circuit; and a correction resistor that is inserted between the output of the first feedback circuit and the connection terminal to pass the correction current having a magnitude corresponding to the output of the first feedback circuit. It is characterized by.

  According to this configuration, since the low frequency component equal to or lower than the first cutoff frequency is fed back to the connection terminal through the correction resistor, the low frequency component is subtracted from the current supplied from the conversion unit to the light receiving unit to obtain an output voltage. The influence of the low frequency component of is suppressed. Therefore, saturation of the output voltage can be suppressed with a relatively simple configuration.

  According to a third aspect of the present invention, in the first or second aspect of the present invention, the low frequency correction means outputs a low frequency component equal to or lower than a second cutoff frequency lower than the frequency of the detection signal in the output voltage. The control terminal is connected to the output of the second feedback circuit and the second feedback circuit inserted between the predetermined potential point and the connection terminal, so that the size of the second feedback circuit corresponds to the output of the second feedback circuit. And a correction transistor for supplying the correction current.

  According to this configuration, since the low frequency component equal to or lower than the second cutoff frequency is fed back to the connection terminal through the correction transistor, the low frequency component is subtracted from the current supplied from the conversion unit to the light receiving unit, to the output voltage. The influence of the low frequency component of is suppressed. Here, since the correction transistor can flow a larger current than a resistor or the like, it can cope with a relatively large low-frequency component.

  According to a fourth aspect of the present invention, in the second aspect of the invention, the low-frequency correction unit outputs a second low-frequency component having a frequency equal to or lower than a second cutoff frequency lower than the frequency of the detection signal. The control current is inserted between the circuit, a predetermined potential point, and the connection terminal, and the control terminal is connected to the output of the second feedback circuit, so that the correction current having a magnitude corresponding to the output of the second feedback circuit is The second feedback circuit is lower than the first cutoff frequency during the sensing period and higher than the first cutoff frequency during the periods other than the sensing period. It has the frequency switching means which switches a frequency, It is characterized by the above-mentioned.

  According to this configuration, since the low frequency component equal to or lower than the second cutoff frequency is fed back to the connection terminal through the correction transistor, the low frequency component is subtracted from the current supplied from the conversion unit to the light receiving unit, to the output voltage. The influence of the low frequency component of is suppressed. Here, since the correction transistor can flow a larger current than a resistor or the like, it can cope with a relatively large low-frequency component. In addition, since the second feedback circuit has frequency switching means for switching the second cut-off frequency, in the period other than the sensing period, a relatively wide range of low frequency components are fed back, but detection is performed in the sensing period. It can be avoided that the signal is fed back. Also during the sensing period, any low frequency component below the first cut-off frequency can be fed back through the correction resistor.

  According to a fifth aspect of the present invention, in the fourth aspect of the present invention, the second feedback circuit includes an integrating circuit that outputs an integrated value component of the output voltage, and the frequency switching means includes the output of the integrating circuit and the correction. A sample-and-hold circuit having a first switch inserted between the control terminal of the transistor for operation and operating the sample-and-hold circuit by turning off the first switch during the sensing period. The output voltage of the circuit is applied to the control terminal of the correcting transistor.

  According to this configuration, during the sensing period, the first switch is turned off to cut off the output of the integration circuit and the control terminal of the correction transistor, so that the steady state such as flicker noise generated in the integration circuit Noise can be prevented from affecting the input, and the SN ratio is improved.

  According to a sixth aspect of the invention, in the fifth aspect of the invention, a second switch is connected between the connection terminal and the output terminal of the conversion unit, and the second switch is the first switch. It is characterized by being turned on when the switch is on.

  According to this configuration, when the second switch is turned on, the gain between the connection terminal and the output terminal of the conversion unit is reduced, and the oscillation of the system due to the first switch being turned on can be suppressed. .

  According to a seventh aspect of the invention, in the fifth aspect of the invention, the first switch has an off-resistance value set smaller than a resistance value between a control terminal of the correcting transistor and the predetermined potential point. It is characterized by.

  According to this configuration, even during the sensing period in which the first switch is turned off, a minute current can flow through the off resistance of the first switch, and thus occurs between the control terminal of the correcting transistor and the predetermined potential point. It is possible to prevent the potential at the control terminal of the correcting transistor from being lowered due to the leakage current. Therefore, fluctuations in the output voltage due to a decrease in the potential of the control terminal of the correction transistor can be suppressed.

  According to an eighth aspect of the present invention, in the fourth aspect of the present invention, the second feedback circuit includes an integration circuit that outputs an integrated value component of the output voltage, and the frequency switching means is a control terminal of the correction transistor. And a capacitor connected between the predetermined potential point and a low-pass filter circuit having a resistor and a parallel circuit of a third switch connected between the output of the integrating circuit and the control terminal of the correcting transistor. In the sensing period, the low-pass filter circuit is operated by turning off the third switch.

  According to this configuration, even during the sensing period in which the third switch is turned off, a current can flow through the resistor. Therefore, the leakage current generated between the control terminal of the correction transistor and the predetermined potential point causes the correction transistor. It is possible to prevent the potential of the control terminal from being lowered. Therefore, fluctuations in the output voltage due to a decrease in the potential of the control terminal of the correction transistor can be suppressed. In addition, since the second cutoff frequency in the sensing period can be set with high accuracy, the second cutoff frequency can be set high within a range in which the detection signal is not fed back to the connection terminal. A wide range of low frequency components can be fed back to the connection terminals.

  The invention according to claim 9 is the invention according to claim 4, wherein the second feedback circuit includes an integration circuit having a time constant determined by a first resistor and a capacitor, and the frequency switching means includes the first A series circuit of a second resistor and a fourth switch connected in parallel with the resistor is provided, and the fourth switch is turned off during the sensing period.

  According to this configuration, it is possible to reduce the size and power consumption of the circuit as compared with the case where the sample hold circuit is provided. In addition, since the second cutoff frequency in the sensing period can be set with high accuracy, the second cutoff frequency can be set high within a range in which the detection signal is not fed back to the connection terminal. A wide range of low frequency components can be fed back to the connection terminals.

  According to a tenth aspect of the present invention, in the invention according to any one of the fourth to ninth aspects, the first feedback circuit outputs a voltage having the same phase as the current supplied from the conversion unit to the light receiving unit. The second feedback circuit includes an active filter that outputs a voltage having a phase opposite to that of the current supplied from the conversion unit to the light receiving unit.

  According to this configuration, since the first and second feedback circuits are realized by the active filter, it is possible to have a high gain with respect to the low frequency component, and to reliably suppress the fluctuation of the output voltage due to the low frequency component. can do.

  According to an eleventh aspect of the present invention, in the invention according to any one of the third to tenth aspects, a plurality of the correction transistors are provided, and the selection transistors are inserted between the respective correction transistors and the connection terminals. And a switch control circuit that controls on / off of the selection switch in accordance with the output of the second feedback circuit so that the number of selection switches that are turned on increases as the output of the second feedback circuit increases. It is characterized by that.

  According to this configuration, the number of correction transistors used for feedback increases as the correction current supplied from the low-frequency correction unit to the light receiving unit via the connection terminal increases. The ratio (W / L) between the channel width (W) and the channel length (L) in each correction transistor can be suppressed to be small, and stationary noise per correction transistor can be suppressed to be small.

  The invention of claim 12 is the operation mode of the invention of claim 10, wherein the first feedback circuit and the second feedback circuit share an operational amplifier, and the operational amplifier uses the operational amplifier for the first feedback circuit. And a mode switching means for switching between operation modes in which the operational amplifier is used in the second feedback circuit.

  According to this configuration, since the first feedback circuit and the second feedback circuit share the operational amplifier, the circuit can be reduced in size as compared with the case where each feedback circuit is provided with the operational amplifier. it can.

  The invention of claim 13 is characterized in that, in the invention of claim 10, the power supply voltage of the second feedback circuit is set higher than the power supply voltages of the other circuits.

  According to this configuration, the upper limit value of the output of the second feedback circuit is higher than when the power supply voltage of the second feedback circuit is the same as the power supply voltage of the other circuits. The upper limit of the magnitude of the correction current that can be fed back to the connection terminal can be increased.

  In the present invention, even if a low-frequency component is included in the current flowing through the light receiving unit, it is possible to suppress the saturation of the output voltage due to the low-frequency component by applying feedback between the output terminal and the connection terminal. There is an advantage that means for preventing incidence of disturbance light to the light receiving section can be simplified or omitted.

(Embodiment 1)
The smoke detector A of the present embodiment has a detection space in the housing 20 as in the conventional configuration shown in FIG. 12, and a light emitting unit that intermittently outputs pulsed light toward the detection space; The light receiving unit is disposed at a position where direct light from the light emitting unit is not incident, and converts the received light into current, and the circuit block 1 that detects smoke in the detection space based on the current flowing through the light receiving unit. In the smoke detector A, when smoke flows into the detection space, the amount of light received from the light emitting unit at the light receiving unit increases due to diffuse reflection of the light from the light emitting unit with the smoke in the detection space, The amount of current flowing through the light receiving portion increases. The smoke detector A exemplified here uses a battery as a power source, and is intermittently driven in order to reduce the average power consumption and extend the life of the battery.

  The circuit block 1 of the present embodiment is based on a current-voltage conversion circuit that converts the current flowing through the light receiving unit into an output voltage whose voltage value varies according to the variation of the current and outputs the output voltage, and the output voltage of the current-voltage conversion circuit And a determination processing unit (notification determination circuit 14 in FIG. 11B) for determining the presence or absence of smoke in the detection space.

  As shown in FIG. 2, the current-voltage conversion circuit 2 outputs a current I1 flowing out through the connection terminal Tin (hereinafter referred to as an output current) I1 to an output voltage Vout whose voltage value varies according to the variation of the output current I1. The conversion unit 3 that converts the signal to the output terminal Tout and outputs the output voltage from the output terminal Tout as a low-frequency correction unit according to the magnitude of a low-frequency component that is equal to or lower than a predetermined first cutoff frequency fc1 in the output voltage Vout output from the conversion unit 3 A first feedback circuit 4 that outputs a voltage, and a correction resistor R1 inserted between the output of the first feedback circuit 4 and the connection terminal Tin of the conversion unit 3. Further, in the present embodiment, the second feedback circuit 5 that outputs a voltage corresponding to the magnitude of the low frequency component below the predetermined second cutoff frequency fc2 in the output voltage Vout, the predetermined potential point Vcc, and the conversion unit. The correction transistor Q1 inserted between the three connection terminals Tin is provided as a low-frequency correction means.

  As shown in FIG. 1, the conversion unit 3 has a configuration in which a conversion resistor R2 is connected between the inverting input terminal and the output terminal of the operational amplifier OP1, and the reference voltage Vs is applied to the non-inverting input terminal of the operational amplifier OP1. Have A photodiode PD (see FIG. 2) as a light receiving unit is connected to the connection terminal Tin of the conversion unit 3, and an output current I1 of the conversion unit 3 is supplied to the photodiode PD through the connection terminal Tin. Here, the conversion unit 3 of the present embodiment has a capacitor C1 connected in parallel to the conversion resistor R2 and also functions as a low-pass filter, and passes only the output current I1 having a predetermined cutoff frequency fc0 or less. Circuit constants of the conversion resistor R2 and the capacitor C1 are set. This cut-off frequency fc0 is represented by fc0 = 1 / (2π × r2 × c1) using the resistance value r2 of the conversion resistor R2 and the constant c1 of the capacitor C1, and at least the photodiode PD is an LED 6 (light emitting portion). It is set so as to pass a pulsed output current (hereinafter referred to as a detection signal) I1 generated when receiving light from (see FIG. 2).

  Therefore, the current-voltage conversion circuit 2 uses the output voltage Vout (here, the reference voltage Vs) when the output current I1 from the conversion unit 3 to the photodiode PD is zero as an operating point in accordance with the fluctuation of the output current I1. The output voltage Vout is varied based on the operating point.

  The first feedback circuit 4 integrates the inverting amplifier circuit 7 that inverts and amplifies the output voltage Vout of the conversion unit 3 and the output voltage Vout that is inverted and amplified by the inverting amplifier circuit 7 and corresponds to an integrated value component of the output voltage Vout. And a first integration circuit 8 that outputs an integration voltage Vdc.

  The first integrating circuit 8 connects the inverting input terminal of the operational amplifier OP2 to the output of the inverting amplifier circuit 7 via the resistor R3, and connects the capacitor C2 between the inverting input terminal and the output terminal of the operational amplifier OP2. Configured as a low-pass filter having a time constant determined by the resistor R3 and the capacitor C2. The integration circuit 8 has a time constant set so as to have a first cut-off frequency fc1 that blocks at least the detection signal generated when the photodiode PD receives light from the LED 6 (that is, lower than the frequency of the detection signal). The

  The inverting amplifier circuit 7 is for making the output of the integrating circuit 8 in phase with the output voltage Vout of the conversion unit 3, and is connected to the output terminal Tout of the conversion unit 3 via the resistor R4 to invert the operational amplifier OP3. An input terminal is connected, and a resistor R5 is connected between the inverting input terminal and the output terminal of the operational amplifier OP3. A reference voltage Vs is applied to the non-inverting input terminals of both operational amplifiers OP2 and OP3.

  Thus, when the detection signal and the low frequency component generated when the photodiode PD receives the light from the LED 6 are included in the output current I1 of the converter 3, the signal is output from the first integrating circuit 8. The integrated voltage Vdc is a voltage corresponding to the low frequency component. At this time, an output voltage Vout having the same phase as the output current I1 appears at the output terminal Tout of the converter 3, and the phase of the output voltage Vout is inverted once by the inverting amplifier circuit 7 and the integrating circuit 8, respectively. An integrated voltage Vdc in phase with the output current I1 appears at the output of the circuit 8. Here, since the reference voltage Vs is applied to the connection terminal Tin of the conversion unit 3, a potential difference obtained by subtracting the reference voltage Vs from the integrated voltage Vdc is generated between both ends of the correction resistor R1. A current Ic1 corresponding to the magnitude (hereinafter referred to as a correction current) Ic1 flows through the correction resistor R1.

  Thereby, when a low-frequency component having a frequency equal to or lower than the first cut-off frequency fc1 is included in a current (hereinafter referred to as a supply current) I0 flowing through the photodiode PD, this low-frequency component is used as the correction current Ic1. The correction current Ic1 flows in the photodiode PD in addition to the output current I1 of the conversion unit 3. Therefore, if the supply current I0 flowing through the photodiode PD is constant, the correction current Ic1 is subtracted from the output current I1 supplied from the converter 3 to the photodiode PD, and the low frequency component is removed from the output voltage Vout.

  If a resistor having a small resistance value is used as the correction resistor R1, the thermal noise of the correction resistor R1 itself increases and the input conversion noise of the current-voltage conversion circuit 2 also increases. Since there is a problem that the S / N ratio, which is the ratio with the signal component (supply current I0) of the diode PD, is reduced, the resistance value of the correction resistor R1 is set to be somewhat large.

  By the way, in the smoke detector A of the present embodiment, the second feedback circuit 5 includes a second integration circuit 9 that integrates the output voltage Vout of the conversion unit 3, and an output of the second integration circuit 9 by sample-holding. And a sample and hold circuit 10 for performing the above operation.

  The second integrating circuit 9 is configured by connecting the inverting input terminal of the operational amplifier OP4 to the output terminal Tout via the resistor R6, and connecting the capacitor C3 between the inverting input terminal and the output terminal of the operational amplifier OP4. And functions as a low-pass filter having a time constant determined by the resistor R6 and the capacitor C3. The integration circuit 9 has a time constant set to have a second cutoff frequency fc2 (that is, fc1 <fc2) higher than the first cutoff frequency fc1 of the first integration circuit 8 described above. The reference voltage Vs is applied to the non-inverting input terminal of the operational amplifier OP4.

  The correction transistor Q1 has a control terminal connected to the output of the second integration circuit 9, and allows a current corresponding to the output of the second integration circuit 9 to flow from the predetermined potential point Vcc of the converter 3 to the connection terminal Tin. In this case, it is composed of a P-channel MOSFET. The correcting transistor Q1 has a drain connected to the connection terminal Tin of the conversion unit 3 and a source connected to the predetermined potential point Vcc, and a gate connected to the output of the integrating circuit 9 via the sample hold circuit 10 (the output of the operational amplifier OP4). Terminal).

  The sample and hold circuit 10 is connected between the normally closed first switch SW1 inserted between the output of the integrating circuit 9 and the gate of the correcting transistor Q1, and between the gate of the correcting transistor Q1 and the circuit ground. By turning off the first switch SW1 at a predetermined timing, the output of the integrating circuit 9 at the predetermined timing is maintained as the output voltage of the capacitor C4.

  With the above-described configuration, the integration circuit 9 integrates the output voltage Vout of the conversion unit 3, so that a low frequency component having a frequency equal to or lower than the second cutoff frequency fc in the output voltage Vout of the conversion unit 3 appears in the output of the integration circuit 9. It will be. At this time, the output voltage Vout having the same phase as the output current I1 appears at the output terminal Tout of the converter 3, and the phase of the output voltage Vout is inverted by the integrating circuit 9, so that the output of the integrating circuit 9 is the output current I1. And low-frequency components with opposite phase appear. Here, since the output of the integration circuit 9 is applied to the gate of the correction transistor Q1 via the sample hold circuit 10, when the switch SW1 of the sample hold circuit 10 is on, the drain-source region of the correction transistor Q1. In this case, a current (hereinafter referred to as a correction current) Ic2 corresponding to the magnitude of the output of the integrating circuit 9 (low frequency component of the output voltage Vout) flows.

  Thus, when the supply current I0 flowing through the photodiode PD includes a low frequency component having a frequency equal to or lower than the second cutoff frequency fc2, this low frequency component is fed back to the connection terminal Tin of the conversion unit 3 as the correction current Ic2. Thus, the correction current Ic2 flows in the photodiode PD in addition to the output current I1 of the conversion unit 3. Therefore, if the supply current I0 flowing through the photodiode PD is constant, the correction current Ic2 is subtracted from the output current I1 supplied from the converter 3 to the photodiode PD, and the low frequency component is removed from the output voltage Vout. As a result, the gain of the low frequency component can be lowered as a whole of the current-voltage conversion circuit 2.

  Here, when the switch SW1 of the sample hold circuit 10 is turned off, the output of the integrating circuit 9 and the gate of the correcting transistor Q1 are cut off, but the output of the integrating circuit 9 is maintained as the voltage across the capacitor C4. Therefore, the correction current Ic2 corresponding to the magnitude of the output of the integration circuit 9 immediately before the switch SW1 is turned off can continue to flow between the drain and source of the correction transistor Q1. In other words, when the sample hold circuit 10 is activated by turning off the switch SW1 of the sample hold circuit 10, the upper limit value of the frequency of the correction current Ic2 that can flow between the drain and source of the correction transistor Q1 (second cutoff) Although the frequency fc2) is lowered, the DC component can be removed from the output voltage Vout by continuing feedback through the correcting transistor Q1.

  In the present embodiment, the timing at which the switch SW1 of the sample hold circuit 10 is turned off is a period during which the LED 6 of the smoke detector A outputs pulsed light and detects the presence or absence of smoke flowing into the detection space (hereinafter referred to as sensing). (Referred to as “period”). That is, the smoke detector A of the present embodiment is for converting a detection signal generated when the photodiode PD receives light from the LED 6 during the sensing period into a voltage and outputting it as an output voltage Vout. Therefore, the switch SW1 is turned off during the sensing period so that the detection signal during the sensing period is not fed back through the correction transistor Q1.

  More specifically, the second cutoff frequency fc2 of the second integration circuit 9 is set closer to the frequency of the detection signal than the first cutoff frequency fc1 of the first integration circuit 8. When the switch SW1 is on, the detection signal is fed back through the correction transistor Q1, and the gain of the detection signal may be reduced as a whole of the current-voltage conversion circuit 2. Therefore, in this embodiment, the switch SW1 is turned off and the sample hold circuit 10 is operated during the sensing period, so that the detection signal is prevented from being fed back through the correction transistor Q1, and the current-voltage conversion circuit 2 as a whole. A high gain of the detection signal is ensured.

  Here, when the smoke detector A is intermittently driven as described above, the power supply to the current-voltage conversion circuit 2 is also intermittently performed and the power supply to the current-voltage conversion circuit 2 is performed. The sensing period is set in the inside. The switch SW1 of the sample-and-hold circuit 10 is turned off only during the sensing period, the current voltage from the start of power supply to the current-voltage conversion circuit 2 until the sensing period starts, and after the sensing period ends. The switch SW1 is turned on until the power supply to the conversion circuit 2 is stopped.

  Thus, during the sensing period in which the switch SW1 is turned off, the output of the second feedback circuit 5 is fixed to a value immediately before the switch SW1 is turned off, so that there is no fluctuation in the DC component included in the supply current I0. Feedback can be continuously applied by the correction transistor Q1, but for the low frequency component with fluctuation included in the supply current I0, the low frequency component is a low frequency component equal to or lower than the second cutoff frequency fc2. However, feedback cannot be applied by the correction transistor Q1.

  However, even during the sensing period, the low-frequency component below the first cut-off frequency fc1 can be fed back by the correction resistor R1 by taking it out as the output of the first feedback circuit 4.

  According to the smoke detector A having the above-described configuration, in the period other than the sensing period, the low-frequency component having the second cutoff frequency fc2 or less in the supply current I0 flowing through the photodiode PD is fed back through the correction transistor Q1. Since the output voltage Vout is removed, the operating point of the output voltage Vout settles on the reference voltage Vs even if the supply current I0 includes a low frequency component. In the sensing period, the low-frequency component of the supply current I0 that is equal to or lower than the first cutoff frequency fc1 is fed back through the correction resistor R1 and removed from the output voltage Vout. Even if the frequency component is included, the operating point of the output voltage Vout settles to the reference voltage Vs. At this time, the switch SW1 of the sample hold circuit 10 is turned off, and the output of the second feedback circuit 5 is held at a value immediately before the sensing period, so that the detection signal is not fed back through the correction transistor Q1 and is detected. An output voltage Vout corresponding to the signal can be output.

  That is, when the correction resistor R1 and the correction transistor Q1 are used as means for feeding back and removing the low frequency component of the supply current I0 from the output voltage Vout, the low frequency component is fed back only by the correction resistor R1. In comparison, it is possible to cope with feedback of a larger current component. In addition, by setting the second cut-off frequency fc2 higher, it is possible to remove a relatively wide range of low-frequency components from the output voltage Vout during a period other than the sensing period, while switching the switch SW1 of the sample hold circuit 10 on and off. In the sensing period, it is possible to prevent the detection signal to be detected from being attenuated.

  In addition, since the second cutoff frequency fc2 of the second feedback circuit 5 is set higher than the first cutoff frequency fc1 of the first feedback circuit 4, when power supply to the current-voltage conversion circuit 2 starts The output of the second feedback circuit 5 responds before the first feedback circuit 4. Therefore, most of the low frequency components below the second cut-off frequency fc2 can be fed back through the correction transistor Q1 without adding means for shutting off the first feedback circuit 4, and as a result, the current-voltage conversion circuit 2 can be miniaturized.

  In addition, by using the sample hold circuit 10 as frequency switching means for reducing the second cutoff frequency fc2 of the second feedback circuit 5 during the sensing period, the output of the integrating circuit 9 and the correcting transistor Q1 Therefore, noise generated by the integrating circuit 9 (flicker noise or the like) does not affect the supply current I0, and there is an advantage that the SN ratio can be improved.

Note that the P-channel MOSFET used as the correction transistor Q1 in the present embodiment has a smaller hole mobility than the N-channel MOSFET, so that the N-channel MOSFET is used as the correction transistor Q1. The noise component from the correction transistor Q1 is reduced. In particular, it is known that flicker noise generated when electrons are captured and emitted from dangling bonds at the Si / SiO ₂ interface is reduced to about １ ／ in the P channel compared to the N channel. Therefore, using a P-channel MOSFET as the correction transistor Q1 is useful for improving the SN ratio.

  A specific example of the current-voltage conversion circuit 2 having the above configuration will be described. Even if the photodiode PD receives light from a fluorescent lamp that is lit with a commercial power source (60 Hz AC power source) using a copper iron ballast. The second cutoff frequency fc2 of the second feedback circuit 5 is set higher than at least 120 Hz so that the output voltage Vout of the current-voltage conversion circuit 2 does not fluctuate due to the flickering of the fluorescent lamp light. . Furthermore, by setting the first cut-off frequency fc1 of the first feedback circuit 4 higher than 120 Hz, even in the sensing period when the switch SW1 is turned off, the low frequency of 120 Hz or less affected by the light of the fluorescent lamp The component is fed back through the correction resistor R1 and removed from the output voltage Vout.

  By the way, in FIG. 1, the 2nd switch SW2 connected in parallel with the conversion resistance R2 of the conversion part 3 is provided. The switch SW2 is a normally closed switch that is turned off at the same timing as the first switch SW1, and has a function described below.

  That is, if only the first switch SW1 is provided, the cutoff frequency fc2 of the second feedback circuit 5 is shifted to the high frequency side when the first switch SW1 is turned on. In the frequency characteristics of the gain of the entire current-voltage conversion circuit 2 shown in (2), when the first switch SW1 is turned on, the gain on the low frequency side is crushed as shown by the solid line, and the cutoff frequency fc0 of the conversion unit 3 A gain peak occurs between the second feedback circuit 5 and the second cutoff frequency fc2, and the system is likely to oscillate. That is, since the output voltage Vout is in a state of being easily oscillated, if the first switch SW1 is turned off when the output voltage Vout is low as shown by a broken line in FIG. 4C, the output voltage Vout is consequently obtained. There is a problem that the rise of is delayed.

  On the other hand, in the present embodiment in which the second switch SW2 connected in parallel with the conversion resistor R2 is provided, the second switch SW2 is turned on together with the first switch SW1 from when the power is turned on to when the sensing period starts. Thus, as shown in FIG. 3B, while the first switch SW1 is on, both ends of the conversion resistor R2 are connected, the gain of the conversion unit 3 is crushed, and the above-described gain peak is eliminated. be able to. As a result, it is possible to suppress the oscillation of the system due to the first switch SW1 being turned on.

  Furthermore, in this embodiment, since the integrating circuits 8 and 9 of the first and second feedback circuits 4 and 5 are not passive circuits but active circuits having operational amplifiers OP2 and OP4, low frequency The component can have a high gain, and feedback can be applied up to the open gain of the operational amplifiers OP2 and OP4. That is, in the configuration using the passive filter, when the second feedback circuit 5 is activated, a voltage drop (the amount of drop varies depending on the gain) occurs in the output voltage Vout, and then the sample hold circuit 10 is activated. The first feedback circuit 4 operates and the output voltage Vout similarly varies, and as a result, the variation appears in the final output. For this reason, erroneous detection of the detection signal may occur during the fluctuation. In order to suppress the fluctuation, it is conceivable that the sample hold circuit 10 is not operated until just before the timing at which the detection signal is generated. In this case, the current consumption of the entire circuit increases. On the other hand, since the active filter is used in the present embodiment, the fluctuation of the output voltage Vout due to the low frequency component can be suppressed and the saturation of the output voltage Vout can be surely avoided.

  Here, it is desirable that the power supply voltage of the second feedback circuit 5 is higher than the power supply voltage of circuits other than the feedback circuit 5 in the current-voltage conversion circuit 2. As a result, the absolute value of the output voltage of the second feedback circuit 5 (that is, the gate voltage of the correction transistor Q1) can be increased, and therefore a relatively large correction current Ic2 can be supplied to the correction transistor Q1. It becomes possible. As a result, even when a low-frequency component having a relatively large amplitude is included in the supply current I0, the low-frequency component can be removed from the output voltage Vout, and the magnitude of the low-frequency component that can suppress the influence on the output voltage Vout. There is an advantage that the upper limit of the thickness is further increased.

  Even during the sensing period in which the first switch SW1 is turned off and the sample hold circuit 10 is operating, correction is performed due to the influence of leakage current generated between the gate of the correcting transistor Q1 and the predetermined potential point Vcc. In some cases, the gate voltage of the transistor Q1 gradually decreases with time. At this time, since the current flowing between the drain and source of the correction transistor Q1 also gradually decreases, the output voltage Vout may vary accordingly. As a countermeasure, it is conceivable to use an element (for example, an analog switch) whose off-resistance is smaller than the resistance value between the gate and the source of the correction transistor Q1 for the first switch SW1. As a result, even during a sensing period in which the switch SW1 is off, a small current flowing through the off-resistance of the switch SW1 can suppress a decrease in the gate voltage due to the leakage current, and suppress fluctuations in the output voltage Vout. be able to.

  As described above, the smoke detector A according to the present embodiment is capable of converting even when the supply current I0 including a large low-frequency component flows to the photodiode PD due to strong disturbance light incident on the photodiode PD. The influence of the low frequency component on the output voltage Vout generated at the output terminal Tout of the unit 3 can be suppressed. Therefore, the labyrinth 21 can be simplified, and the smoke detector A can be made thinner as shown in FIG. The smoke detector A in FIG. 5 uses the front of the housing 20 (below when the housing 20 is attached to the ceiling) as a detection space, and the light from the LED 6 diffused and reflected by the smoke of the photodiode PD flowing into the detection space. Smoke is detected by receiving light.

(Embodiment 2)
The smoke detector A of this embodiment is different from the smoke detector A of Embodiment 1 in that a plurality of correction transistors Q1 are provided as shown in FIG.

  That is, in this embodiment, a plurality of correction transistors Q1 are connected in parallel between the connection terminal Tin and the predetermined potential point Vcc, and the output of the second feedback circuit 5 is connected to the gate of each correction transistor Q1, respectively. It is connected. Here, selection switches SW11, SW12,... Are inserted between the drains of the correction transistors Q1 and the connection terminals Tin, and the selection switches SW11, SW12,. The control is performed by the switch control circuit 11.

  The switch control circuit 11 monitors the output of the second feedback circuit 5 applied to the gate of the correcting transistor Q1, and the selection switches SW11, SW12,... That are turned on as the absolute value of the output of the feedback circuit 5 increases. ... The selection switches SW11, SW12,... Are turned on / off according to the magnitude of the output of the feedback circuit 5 so that the number of. Therefore, as the correction current Ic2 supplied to the photodiode PD via the connection terminal Tin increases, the number of correction transistors Q1 connected in parallel between the connection terminal Tin and the predetermined potential point Vcc increases, and current feedback is performed. The number of correction transistors Q1 used increases.

  In short, it is necessary to increase the ratio (W / L) of the channel width (W) to the channel length (L) in order to increase the applicable current value in the correction transistor Q1 that feeds back the correction current Ic2. However, if W / L is increased, the thermal noise of the correction transistor Q1 increases even if the amount of current to be fed back is the same. In contrast, in the present embodiment, a plurality of correction transistors Q1 are fed back when a large current is fed back as the correction current Ic2 while suppressing W / L of each correction transistor Q1 to be small and thermal noise to be small. By connecting these in parallel, there is an advantage that a relatively large current can be handled.

  Other configurations and functions are the same as those of the first embodiment.

(Embodiment 3)
The smoke detector A of the present embodiment is provided with a low-pass filter circuit 10 ′ instead of the sample hold circuit 10 as frequency switching means for switching the second cutoff frequency fc2 of the second feedback circuit 5 as shown in FIG. This is different from the smoke detector A of the first embodiment.

  The low-pass filter circuit 10 ′ includes a resistor R7 inserted between the output of the second integrating circuit 9 and the gate of the correction transistor Q1, and a capacitor connected between the gate of the correction transistor Q1 and the circuit ground. C5 and a normally closed third switch SW3 connected in parallel to the resistor R7. This low-pass filter circuit 10 'passes a low-frequency component having a frequency equal to or lower than a predetermined cutoff frequency determined by the resistor R7 and the capacitor C5.

  With the above configuration, when the third switch SW3 is on, the output of the integrating circuit 9 is directly applied to the correcting transistor Q1, while when the third switch SW3 is off, the output of the integrating circuit 9 is low-pass. It is applied to the correction transistor Q1 through the filter circuit 10 ′. Therefore, the second cut-off frequency fc2 of the second feedback circuit 5 is lowered by turning off the third switch SW3.

  In the present embodiment, the timing when the switch SW3 of the low-pass filter circuit 10 ′ is turned off is a period (sensing period) in which the LED 6 of the smoke detector A outputs pulsed light and detects the presence or absence of smoke flowing into the detection space. ). That is, the smoke detector A of the present embodiment is for converting a detection signal generated when the photodiode PD receives light from the LED 6 during the sensing period into a voltage and outputting it as an output voltage Vout. Therefore, the switch SW3 is turned off during the sensing period so that the detection signal during the sensing period is not fed back through the correction transistor Q1.

  Other configurations and functions are the same as those of the first embodiment.

(Embodiment 4)
As shown in FIG. 8, the smoke detector A of the present embodiment uses a second integration circuit 9 instead of the sample-and-hold circuit 10 as frequency switching means for switching the second cutoff frequency fc2 of the second feedback circuit 5. The difference from the smoke detector A of the first embodiment is that a series circuit of the second resistor R8 and the fourth switch SW4 is provided.

  A series circuit of the resistor R8 and the normally closed fourth switch SW4 is connected in parallel with the first resistor R6 of the second integrating circuit 9. Thus, when the fourth switch SW4 is on, the second cutoff frequency fc2 of the integrating circuit 9 is determined by the time constant determined by the resistor R6, the resistor R8, and the capacitor C3, while the fourth switch SW4 is In the off state, the second cutoff frequency fc2 of the integrating circuit 9 is determined by a time constant determined by the resistor R6 and the capacitor C3. Therefore, the second cut-off frequency fc2 of the second feedback circuit 5 is lowered when the fourth switch SW4 is turned off.

  In the present embodiment, the timing at which the switch SW4 of the second integration circuit 9 is turned off is a period (sensing) in which the LED 6 of the smoke detector A outputs pulsed light and detects the presence or absence of smoke flowing into the detection space. (Period). That is, the smoke detector A of the present embodiment is for converting a detection signal generated when the photodiode PD receives light from the LED 6 during the sensing period into a voltage and outputting it as an output voltage Vout. Therefore, the switch SW4 is turned off during the sensing period so that the detection signal during the sensing period is not fed back through the correction transistor Q1.

  Other configurations and functions are the same as those of the first embodiment.

(Embodiment 5)
As shown in FIG. 9, the smoke detector A of the present embodiment has the first feedback circuit 4 and the second feedback circuit 5 that are also used as the operational amplifier OP2. Different from A.

  That is, in the present embodiment, the operational amplifier OP2 of the first feedback circuit 4 is also used as the second feedback circuit 5, and the operation mode for operating the first feedback circuit 4 and the second feedback circuit 5 are used. Are provided with a plurality of switches (mode switching means) SW5 to SW10. More specifically, a switch SW5 is inserted between the output terminal of the operational amplifier OP2 and the correction resistor R1, a switch SW6 is inserted between the output terminal Tout and the resistor R3, and is inverted with respect to the output terminal Tout. A switch SW7 is inserted between the input (resistor R4) of the amplifier circuit 7, and a switch SW8 is inserted between the output of the inverting amplifier circuit 7 and the resistor R3. Further, a series circuit of a resistor R6 ′ and a switch SW9 is connected in parallel with the resistor R3 connected to the inverting input terminal of the operational amplifier OP2, and between the inverting input terminal and the output terminal of the operational amplifier OP2. Is connected to a capacitor C3, and a series circuit of a capacitor C2 'and a switch SW10 is connected in parallel with the capacitor C3.

  Here, the switches SW6 and SW9 operate the second feedback circuit 5 by being turned on simultaneously with the first switch SW1 as shown in FIG. 10, and at this time, the other switches SW5, SW7, SW8 and SW10 are turned off. In this state, the output terminal Tout is connected to the inverting input terminal of the operational amplifier OP2 via the parallel circuit of the resistor R3 and the resistor R6 ′, and the output terminal of the operational amplifier OP2 is connected to the gate of the correction transistor Q1. The capacitor C3 is connected between the inverting input terminal and the output terminal of the operational amplifier OP2.

  On the other hand, the switches SW5, SW7, SW8, and SW10 operate the first feedback circuit 4 by being simultaneously turned on as shown in FIG. 10, and at this time, the other switches SW1, SW6, and SW9 are turned off. To do. In this state, the output terminal Tout is connected to the inverting input terminal of the operational amplifier OP2 via the inverting amplifier circuit 7 and the resistor R3, and the output terminal of the operational amplifier OP2 is connected to the correction resistor R1, and the operational amplifier OP2 A parallel circuit of a capacitor C3 and a capacitor C2 ′ is connected between the inverting input terminal and the output terminal.

  In short, in any state, the inverting amplifier circuit OP2 constitutes an integrating circuit, but the cut-off frequency is determined by the parallel circuit of the resistor R3 and the resistor R6 ′ and the capacitor C3 when the switches SW1, SW6, SW9 are on. When the second cut-off frequency fc2 is set and the switches SW5, SW7, SW8, and SW10 are on, the first cut-off frequency fc1 is set by the parallel circuit of the capacitor C3 and the capacitor C2 ′ and the resistor R3.

  According to the configuration of the present embodiment described above, since the operational amplifier OP2 is shared by the first feedback circuit 4 and the second feedback circuit 5, an operational amplifier is individually provided for each of the feedback circuits 4 and 5. Compared with the case of providing, it is possible to achieve downsizing and low power consumption.

  Other configurations and functions are the same as those of the first embodiment.

  By the way, in each said embodiment, although photodiode PD was illustrated as a light-receiving part, it is not restricted to this example, For example, elements, such as CdS and a thermistor, can also be used for a light-receiving part. That is, since the smoke detector A of the present invention uses the current-voltage conversion circuit 2 as a current supply source for supplying a current to the light receiving unit, not only an element that generates its own photovoltaic power, such as a photodiode PD. It is also possible to cope with a light receiving unit made of a passive element such as CdS or thermistor that does not generate photovoltaic power itself.

It is a schematic circuit diagram which shows the structure of Embodiment 1 of this invention. It is a block diagram which shows a structure same as the above. It is a characteristic view which shows the gain of the current voltage converter circuit same as the above. It is a timing chart which shows operation | movement same as the above. It is a perspective view which shows a smoke detector same as the above. It is a schematic circuit diagram which shows the structure of Embodiment 2 of this invention. It is a schematic circuit diagram which shows the structure of Embodiment 3 of this invention. It is a schematic circuit diagram which shows the structure of Embodiment 4 of this invention. It is a schematic circuit diagram which shows the structure of Embodiment 5 of this invention. It is a timing chart which shows operation | movement same as the above. A conventional smoke detector is shown, (a) is a schematic block diagram, (b) is a block of a circuit block. It is a schematic circuit diagram which shows a current-voltage conversion circuit same as the above. It is a timing chart which shows operation | movement same as the above. It is explanatory drawing which shows an output voltage same as the above.

Explanation of symbols

2 Current-voltage conversion circuit 3 Conversion unit 4 First feedback circuit 5 Second feedback circuit 6 LED (light emitting unit)
8 First integration circuit 9 Second integration circuit 10 Sample hold circuit 10 'Low-pass filter circuit 11 Switch control circuit A Smoke detector C5 Capacitor I0 Supply current I1 Output current Ic1, Ic2 Correction current OP2 Operational amplifier PD Photodiode (light reception) Part)
Q1 correcting transistor R1 correcting resistor R6 first resistor R7 resistor R8 second resistor SW1 first switch SW2 second switch SW3 third switch SW4 fourth switch SW5 to SW10 switch (mode switching means)
SW11, SW12 selection switch Tin connection terminal Tout output terminal Vout output voltage

Claims (13)

  A light emitting unit that outputs pulsed light during a predetermined sensing period toward the detection space, and light from the light emitting unit that is diffusely reflected by smoke flowing into the detection space is incident without direct light from the light emitting unit entering The current value is supplied to the light receiving part through the connection part connected to the light receiving part that is arranged at the position where the current corresponding to the light receiving intensity flows, and the voltage value changes according to the fluctuation of the current Current voltage conversion circuit having a conversion unit that outputs the output voltage from the output terminal, and a determination processing unit that determines the presence or absence of smoke in the detection space based on the output voltage, the current voltage conversion circuit, From the output voltage, extract the low frequency component below the cut-off frequency lower than the frequency of the pulsed detection signal generated when the light receiving unit receives light from the light emitting unit, and correct the magnitude according to the low frequency component The connection end of the current converter Smoke detector, characterized in that it comprises a low-frequency correction means supplies the light receiving portion through the.   The low-frequency correction means outputs a voltage corresponding to a low-frequency component equal to or lower than a first cutoff frequency lower than the frequency of the detection signal in the output voltage, and an output of the first feedback circuit The smoke detector according to claim 1, further comprising: a correction resistor that is inserted between the connection terminal and the connection terminal and allows the correction current to flow in a magnitude corresponding to the output of the first feedback circuit.   The low frequency correction means includes a second feedback circuit that outputs a low frequency component equal to or lower than a second cutoff frequency lower than the frequency of the detection signal in the output voltage, and a predetermined potential point and the connection terminal. And a control transistor connected to the output of the second feedback circuit and having a correction transistor for passing the correction current having a magnitude corresponding to the output of the second feedback circuit. The smoke detector according to claim 1 or 2.   The low frequency correction means includes a second feedback circuit that outputs a low frequency component equal to or lower than a second cutoff frequency lower than the frequency of the detection signal in the output voltage, and a predetermined potential point and the connection terminal. A control transistor connected to the output of the second feedback circuit that is inserted so that the correction current flows through the correction current having a magnitude corresponding to the output of the second feedback circuit, and the second feedback circuit. Comprises frequency switching means for switching the second cutoff frequency so that it is lower than the first cutoff frequency during the sensing period and higher than the first cutoff frequency during periods other than the sensing period. Item 3. The smoke detector according to item 2.   The second feedback circuit has an integration circuit that outputs an integrated value component of the output voltage, and the frequency switching means is a first inserted between the output of the integration circuit and the control terminal of the correction transistor. In the sensing period, the sample hold circuit is activated by turning off the first switch, and the held output voltage of the integrating circuit is applied to the control terminal of the correction transistor. The smoke detector according to claim 4.   A second switch is connected between the connection terminal and the output terminal of the conversion unit, and the second switch is turned on when the first switch is on. Item 6. The smoke detector according to item 5.   6. The smoke detection device according to claim 5, wherein the first switch has an off-resistance value set smaller than a resistance value between a control terminal of the correcting transistor and the predetermined potential point. vessel.   The second feedback circuit includes an integration circuit that outputs an integral value component of the output voltage, and the frequency switching unit includes a capacitor connected between a control terminal of the correction transistor and the predetermined potential point. And a low-pass filter circuit having a resistor and a parallel circuit of a third switch connected between the output of the integrating circuit and the control terminal of the correcting transistor, and the third switch is turned off during the sensing period. 5. The smoke detector according to claim 4, wherein the low-pass filter circuit is activated.   The second feedback circuit includes an integrating circuit having a time constant determined by a first resistor and a capacitor, and the frequency switching means includes a second resistor and a fourth resistor connected in parallel with the first resistor. 5. The smoke detector according to claim 4, further comprising a series circuit of switches, wherein the fourth switch is turned off during the sensing period.   The first feedback circuit includes an active filter that outputs a voltage having the same phase as the current supplied from the conversion unit to the light receiving unit, and the second feedback circuit is supplied from the conversion unit to the light receiving unit. The smoke detector according to any one of claims 4 to 9, further comprising an active filter that outputs a voltage having a phase opposite to that of the applied current.   A plurality of the correction transistors are provided, a selection switch inserted between each correction transistor and the connection terminal, and a selection switch that is turned on as the output of the second feedback circuit increases. The smoke control device according to any one of claims 3 to 10, further comprising: a switch control circuit that performs on / off control of a selection switch in accordance with an output of the second feedback circuit so that the number thereof increases. sensor.   The first feedback circuit and the second feedback circuit share an operational amplifier, an operation mode using the operational amplifier for the first feedback circuit, and an operation mode using the operational amplifier for the second feedback circuit; The smoke detector according to claim 10, further comprising mode switching means for switching between. 11. The smoke detector according to claim 10, wherein the power supply voltage of the second feedback circuit is set higher than the power supply voltages of other circuits.

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