JP2005159587A - Even harmonics mixer - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To reduce cross modulation distortion without increasing power consumption significantly while ensuring a conversion gain in an even harmonics mixer or a two frequency mixer. <P>SOLUTION: An even harmonics mixer or a two frequency mixer ensuring a large conversion gain while having a small cross modulation distortion for the input signal is realized without increasing power consumption significantly by employing a current signal as an input signal so that the mixer operates linearly for the input signal and modulating a local oscillation signal by performing multiplication of the input signal while imparting nonlinearity of an even function. <P>COPYRIGHT: (C)2005,JPO&NCIPI

Description

  The present invention relates to an even harmonic mixer that mixes a signal having a frequency twice that of a local oscillation signal with respect to an input signal, and a two-frequency mixer that simultaneously mixes a local oscillation signal with two frequencies to an input signal. It is.

  In a receiver that receives a high-frequency signal, the direct conversion method has attracted attention from the viewpoint of miniaturization of the device. However, when a high-frequency signal is converted into a baseband signal, the local oscillator signal wraps around the high-frequency signal input. This causes a phenomenon called self-mixing, which causes the reception performance of the receiver to deteriorate. Self-mixing is caused by the fact that the frequency of the output signal of the local oscillator is the same as the reception frequency.

  As a method for avoiding this self-mixing problem, it has been proposed to use an even harmonic mixer that shifts the frequency of the input signal by twice the frequency of the signal of the local oscillator. In an even harmonic mixer, an odd symmetric nonlinear operation is performed on a sum or difference signal of an input signal and an output signal of a local oscillator, and is a part of a signal generated by a third-order term included in the nonlinear operation. A signal component whose frequency is shifted by twice the frequency of the output signal of the local oscillator with respect to the input signal is extracted. Therefore, self-mixing does not occur in an ideal state.

  However, since the even harmonic mixer uses a third-order distortion term, there is a problem that cross modulation distortion becomes large. In general, if the increase in power consumption of a mixer is allowed, cross modulation distortion can be suppressed. However, a receiver is often required to have low power consumption, and even in a mixer, low power consumption is a necessary condition. It has become. In addition, there is a problem that the level of the output signal of the local oscillator has to be considerably increased by using the third-order distortion term as compared with the case where the conventional second-order distortion term is used.

FIG. 20 is an example of an even harmonic mixer that has already been proposed. The input signals are complementary (IN1 and IN2), and are mixed by two differential amplifiers so that the nonlinearity becomes an odd function with respect to the local oscillation signal LO1. The local oscillation signal LO1 has a sufficient signal level so that the two differential amplifiers exhibit nonlinear characteristics. Even-order nonlinear terms in the differential amplifier cancel each other by using two differential amplifiers. Therefore, ideally, even-order intermodulation distortion is canceled out by the two differential amplifiers, but in reality, even-order intermodulation distortion remains due to a mismatch in the characteristics of the two differential amplifiers. End up. Since the two differential amplifiers need to operate so as to generate third-order distortion, the magnitude of the second-order distortion term inevitably increases. Therefore, a slight cancellation residual of the second-order distortion term is greatly involved in cross modulation. In order to solve this problem, a method for reducing the cross modulation distortion by finely adjusting the operating points of the two differential amplifiers has been proposed. However, the manufacturing cost is greatly increased.
Japanese Patent Laid-Open No. 2003-32048 Tanimoto, “Research and Development Trend of Mixer for Direct Conversion Receiver”, IEICE Transactions C, Vol. J84-C, No. 5, pp. 337-348, 2001

  The problem to be solved is to suppress cross modulation distortion while keeping power consumption low in a mixer with small self-mixing such as an even harmonic mixer.

  The present invention realizes an even harmonic mixer by causing a local oscillation signal to act on an input signal in a multiplying manner so that an even-order nonlinear term is generated at that time. Alternatively, by injecting a local oscillation signal having two types of frequencies at that time, a two-frequency mixer that mixes a signal having a difference between the two types of local oscillation signals or a sum frequency with the input signal is realized. Specifically:

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input as a complementary current input in which a DC component is superimposed from the first input terminal and the second input terminal, and the output signal is The first output terminal and the second output terminal output a differential current output in which a direct current component is superimposed, and the local oscillation signal includes a first local oscillation signal and an inverted signal of the first local oscillation signal. A second local oscillation signal, a third local oscillation signal whose phase is delayed by 90 degrees from the first local oscillation signal, and a fourth local oscillation signal which is an inverted signal of the third local oscillation signal. , First to eighth field effect transistors (FETs) or bipolar transistors, the source of the first FET, the source of the second FET, the source of the third FET, and the source of the fourth FET are the first Connect to input terminal The source of the fifth FET, the source of the sixth FET, the source of the seventh FET, and the source of the eighth FET are connected to the second input terminal, and the first local oscillation signal is the first FET. The second local oscillation signal is supplied to the gate of the second FET and the gate of the seventh FET in an alternating manner, and the third local oscillation signal is The fourth FET is supplied to the gate of the fourth FET and the gate of the fifth FET in an alternating manner, and the fourth local oscillation signal is supplied to the gate of the third FET and the gate of the sixth FET in an alternating manner. The drain of the FET, the drain of the second FET, the drain of the fifth FET, and the drain of the sixth FET are connected to the first output terminal, and the drain of the third FET, the drain of the fourth FET, and the seventh drain. FET drain and 8th F The drain of the ET is connected to the second output terminal, and outputs a signal including a signal having a frequency that is added to or subtracted from the input signal by twice the frequency of the local oscillation signal.

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input as a complementary current input in which a DC component is superimposed from a first input terminal and a second input terminal, and the output signal Is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is a first local oscillation signal and an inversion of the first local oscillation signal. A second local oscillation signal that is a signal, a third local oscillation signal whose phase is delayed by 90 degrees from the first local oscillation signal, and a fourth local oscillation signal that is an inverted signal of the third local oscillation signal And having first to third and fifth to seventh FETs or bipolar transistors, the source of the first FET, the source of the second FET, and the source of the third FET are connected to the first input terminal. , The fifth FET source And the source of the sixth FET and the source of the seventh FET are connected to the second input terminal, the first local oscillation signal is supplied to the gate of the first FET in an alternating manner, and the second local oscillation is generated. The signal is supplied to the gate of the second FET in an alternating manner, the third local oscillation signal is supplied to the gate of the fifth FET in an alternating manner, and the fourth local oscillation signal is supplied to the gate of the sixth FET. The signal is not supplied to the gate of the third FET and the gate of the seventh FET in an alternating manner, and the drain of the first FET, the drain of the second FET, and the drain of the fifth FET. And the drain of the sixth FET are connected to the first output terminal, the drain of the third FET and the drain of the seventh FET are connected to the second output terminal, and the local oscillation signal with respect to the input signal Add or subtract only twice the frequency of A signal including a signal having a different frequency is output.

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input as a complementary current input in which a DC component is superimposed from a first input terminal and a second input terminal, and the output signal Is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is a first local oscillation signal and an inversion of the first local oscillation signal. A second local oscillation signal as a signal, having first to third and fifth to seventh FETs or bipolar transistors, the source of the first FET, the source of the second FET, and the third FET The source is connected to the first input terminal, the source of the fifth FET, the source of the sixth FET, and the source of the seventh FET are connected to the second input terminal, and the first local oscillation signal is the first local oscillation signal. FET gate The second local oscillation signal is supplied to the gates of the second FET and the sixth FET in an AC manner, and supplied to the gates of the third FET and the seventh FET. No signal is supplied to the gate of the FET of AC, and the drain of the first FET, the drain of the second FET, and the drain of the seventh FET are connected to the first output terminal, and the third FET , The drain of the fifth FET and the drain of the sixth FET are connected to the second output terminal, and a frequency obtained by adding or subtracting the input signal by twice the frequency of the local oscillation signal. The signal including the signal is output.

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input as a complementary current input in which a DC component is superimposed from a first input terminal and a second input terminal, and the output signal Is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is a first local oscillation signal and an inversion of the first local oscillation signal. It consists of a second local oscillation signal that is a signal and has first, third, sixth, and seventh FETs or bipolar transistors, and the first and sixth FETs have different characteristics from the third and seventh FETs. The source of the first FET and the source of the third FET are connected to the first input terminal, the source of the sixth FET and the source of the seventh FET are connected to the second input terminal, First station The oscillation signal is supplied to the gate of the first FET in an alternating manner, the second local oscillation signal is supplied to the gate of the sixth FET in an alternating manner, and is supplied to the gates of the third FET and the seventh FET. Is not supplied with an AC signal, the drain of the first FET and the drain of the seventh FET are connected to the first output terminal, and the drain of the third FET and the drain of the sixth FET are the second. And a signal including a signal having a frequency obtained by adding or subtracting a frequency twice the frequency of the local oscillation signal to the input signal.

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input as a complementary current input in which a DC component is superimposed from a first input terminal and a second input terminal, and the output signal Is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is composed of the first local oscillation signal, and the first, third and third The first and fifth FETs have different characteristics from the third and seventh FETs, and the source of the first FET and the source of the third FET are the first and second FETs. 1 is connected to the input terminal of the first FET, the source of the fifth FET and the source of the seventh FET are connected to the second input terminal, and the first local oscillation signal is the gate of the first FET and the fifth FET. Game And the third FET gate and the seventh FET gate are not supplied with an AC signal, and the drain of the first FET and the drain of the seventh FET are the first output. And the drain of the third FET and the drain of the fifth FET are connected to the second output terminal, and are added to or subtracted from the input signal by twice the frequency of the local oscillation signal. A signal including a signal of a different frequency is output.

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input as a current input on which a DC component is superimposed from a first input terminal, and the output signal is input to a first output terminal and a second output signal. Output as a differential current output in which a DC component is superimposed, and the local oscillation signal is a first local oscillation signal and a second local oscillation signal which is an inverted signal of the first local oscillation signal And a third local oscillation signal whose phase is delayed by 90 degrees from the first local oscillation signal, and a fourth local oscillation signal which is an inverted signal of the third local oscillation signal. Or it has a bipolar transistor, the source of the first FET, the source of the second FET, the source of the third FET and the source of the fourth FET are connected to the first input terminal, and the first local oscillation signal is The gate of the first FET The second local oscillation signal is supplied to the gate of the second FET in an AC manner, the third local oscillation signal is supplied to the gate of the third FET in an AC manner, and the fourth local oscillation signal is supplied. The oscillation signal is supplied to the gate of the fourth FET in an alternating manner, the drain of the first FET and the drain of the second FET are connected to the first output terminal, and the drain of the third FET and the fourth FET. Is connected to a second output terminal so as to output a signal including a signal having a frequency that is added to or subtracted from the input signal by a frequency twice that of the local oscillation signal.

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input from a first input terminal as a current input on which a DC component is superimposed, and the output signal is input to a first output terminal and a second output signal. Output as a differential current output with a DC component superimposed thereon, the local oscillation signal being a first local oscillation signal and a second local oscillation signal being an inverted signal of the first local oscillation signal And having first to third FETs or bipolar transistors, the source of the first FET, the source of the second FET, and the source of the third FET are connected to the first input terminal, and the first local The oscillation signal is supplied to the gate of the first FET in an AC manner, the second local oscillation signal is supplied to the gate of the second FET in an AC manner, and a signal is supplied to the gate of the third FET in an AC manner. Not supplied, the first The drain of the ET and the drain of the second FET are connected to the first output terminal, the drain of the third FET is connected to the second output terminal, and the frequency of the local oscillation signal is 2 with respect to the input signal. A signal including a signal having a frequency added or subtracted by a double frequency is output.

  In an even harmonic mixer having an input signal and a local oscillation signal as inputs, the input signal is input from a first input terminal as a current input on which a DC component is superimposed, and the output signal is input to a first output terminal and a second output signal. Output from the output terminal as a differential current output in which a direct current component is superimposed, the local oscillation signal is composed of a first local oscillation signal, and includes first and third FETs or bipolar transistors, The FET and the third FET have different characteristics, the source of the first FET and the source of the third FET are connected to the first input terminal, and the first local oscillation signal is connected to the gate of the first FET in an AC manner. And no signal is supplied to the gate of the third FET in an alternating manner, the drain of the first FET is connected to the first output terminal, and the drain of the third FET is connected to the second output terminal. Connected to So as to output a signal including a signal including a frequency twice by addition or frequency of the signal obtained by subtracting the frequency of the local oscillation signal to fill force signal.

  In a two-frequency mixer in which an input signal, a local oscillation signal of a first local oscillator, and a local oscillation signal of a second local oscillator are input, the input signal has a DC component from the first input terminal and the second input terminal. The output signal is input as a superimposed complementary current input, and the output signal is output as a differential current output with a DC component superimposed from the first output terminal and the second output terminal. The local oscillation signal includes a first local oscillation signal and a second local oscillation signal that is an inverted signal of the first local oscillation signal, and the local oscillation signal of the second local oscillator includes a fifth local oscillation signal, It consists of a sixth local oscillation signal that is an inverted signal of the fifth local oscillation signal, has first to eighth FETs or bipolar transistors, and includes a first FET source, a second FET source, and a third FET. FET saw And the source of the fourth FET are connected to the first input terminal, and the source of the fifth FET, the source of the sixth FET, the source of the seventh FET, and the source of the eighth FET are the second input terminal. The first local oscillation signal is supplied to the gate of the first FET and the gate of the eighth FET in an alternating manner, and the second local oscillation signal is supplied to the gate of the third FET and the gate of the sixth FET. The fifth local oscillation signal is supplied to the gate of the fourth FET and the gate of the fifth FET, and the sixth local oscillation signal is supplied to the gate of the second FET and the second FET. And the drain of the first FET, the drain of the second FET, the drain of the fifth FET, and the drain of the sixth FET are connected to the first output terminal, and the third FET FET drain and fourth FET The drain, the drain of the seventh FET, and the drain of the eighth FET are connected to the second output terminal, and the frequency of the local oscillation signal of the first local oscillator and the local frequency of the second local oscillator with respect to the input signal. A signal including a signal having a frequency added or subtracted by the sum or difference of the frequencies of the oscillation signals is output.

  In a two-frequency mixer in which an input signal, a local oscillation signal of a first local oscillator, and a local oscillation signal of a second local oscillator are input, the input signal has a DC component from the first input terminal and the second input terminal. The output signal is input as a superimposed complementary current input, and the output signal is output as a differential current output with a DC component superimposed from the first output terminal and the second output terminal. The local oscillation signal includes a first local oscillation signal and a second local oscillation signal that is an inverted signal of the first local oscillation signal, and the local oscillation signal of the second local oscillator includes a fifth local oscillation signal, It comprises a sixth local oscillation signal that is an inverted signal of the fifth local oscillation signal, and has first to third and fifth to seventh FETs or bipolar transistors, and the source of the first FET and the second FET Source of The source of the third FET is connected to the first input terminal, the source of the fifth FET, the source of the sixth FET, and the source of the seventh FET are connected to the second input terminal, and the first local oscillation The signal is supplied to the gate of the first FET in an alternating manner, the second local oscillation signal is supplied to the gate of the sixth FET in an alternating manner, and the fifth local oscillation signal is supplied to the gate of the fifth FET in an alternating manner. The sixth local oscillation signal is supplied to the gate of the second FET in an alternating manner, and no signal is supplied to the gate of the third FET and the gate of the seventh FET in an alternating manner, The drain of the first FET, the drain of the second FET, the drain of the fifth FET, and the drain of the sixth FET are connected to the first output terminal, and the drains of the third FET and the seventh FET. Is connected to the second output terminal and is connected to the input signal. So as to output a signal including a first local oscillator frequency and the frequency of the signal in which only the added or subtracted frequency of the sum or difference of the frequencies of the local oscillation signal of the second local oscillator of the local oscillation signal Te.

  In a two-frequency mixer in which an input signal, a local oscillation signal of a first local oscillator, and a local oscillation signal of a second local oscillator are input, the input signal has a DC component from the first input terminal and the second input terminal. The output signal is input as a superimposed complementary current input, and the output signal is output as a differential current output with a DC component superimposed from the first output terminal and the second output terminal. The local oscillation signal is composed of a first local oscillation signal, the local oscillation signal of the second local oscillator is composed of a fifth local oscillation signal, and has first to third and fifth to seventh FETs or bipolar transistors. The source of the first FET, the source of the second FET, and the source of the third FET are connected to the first input terminal, the source of the fifth FET, the source of the sixth FET, and the source of the seventh FET. Source Connected to the second input terminal, the first local oscillation signal is supplied to the gate of the first FET and the gate of the sixth FET in an alternating manner, and the fifth local oscillation signal is supplied to the gate of the fifth FET and AC is supplied to the gate of the second FET, no signal is supplied to the gate of the third FET and the gate of the seventh FET, and the drain of the first FET and the gate of the second FET are not supplied. The drain of the third FET and the drain of the seventh FET are connected to the first output terminal, the drain of the third FET, the drain of the fifth FET, and the drain of the sixth FET are connected to the second output terminal. A signal including a signal having a frequency obtained by adding or subtracting the frequency of the local oscillation signal of the first local oscillator and the frequency of the local oscillation signal of the second local oscillator by the sum or difference of the signal to the signal is output. To do.

  In a two-frequency mixer that receives an input signal, a local oscillation signal of a first local oscillator, and a local oscillation signal of a second local oscillator, the input signal is a current input in which a DC component is superimposed from a first input terminal. The output signal is output as a differential current output in which a direct current component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal of the first local oscillator is the first local oscillation signal. Signal and a second local oscillation signal which is an inverted signal of the first local oscillation signal. The local oscillation signal of the second local oscillator is a fifth local oscillation signal and an inverted signal of the fifth local oscillation signal. Having a first to a fourth FET or a bipolar transistor, a source of the first FET, a source of the second FET, a source of the third FET, and a source of the fourth FET. Source is first The first local oscillation signal is supplied to the gate of the first FET in an AC manner, the second local oscillation signal is supplied to the gate of the fourth FET in an AC manner, The local oscillation signal is supplied to the gate of the third FET in an alternating manner, and the sixth local oscillation signal is supplied to the gate of the second FET in an alternating manner, so that the drain of the first FET and the drain of the second FET are supplied. Is connected to the first output terminal, the drain of the third FET and the drain of the fourth FET are connected to the second output terminal, and the frequency of the local oscillation signal of the first local oscillator with respect to the input signal And a signal including a signal having a frequency added or subtracted by the sum or difference frequency of the local oscillation signals of the second local oscillator.

  In a two-frequency mixer that receives an input signal, a local oscillation signal of a first local oscillator, and a local oscillation signal of a second local oscillator, the input signal is a current input in which a DC component is superimposed from a first input terminal. The output signal is output as a differential current output with a DC component superimposed from the first output terminal and the second output terminal, and the local oscillation signal of the first local oscillator is the first local oscillation signal. The local oscillation signal of the second local oscillator comprises the fifth local oscillation signal and has first to third FETs or bipolar transistors, the source of the first FET and the source of the second FET, and The source of the third FET is connected to the first input terminal, the first local oscillation signal is supplied in an alternating manner to the gate of the first FET, and the fifth local oscillation signal is supplied to the gate of the second FET. The signal is supplied to the gate of the third FET in an alternating manner, the drain of the first FET and the drain of the second FET are connected to the first output terminal, and the third FET The drain of the FET is connected to the second output terminal, and is added to the input signal by the sum or difference frequency of the frequency of the local oscillation signal of the first local oscillator and the frequency of the local oscillation signal of the second local oscillator. A signal including a signal having a frequency that is increased or decreased is output.

  In the even harmonic mixer or the two-frequency mixer, the input signal is a high frequency signal or an intermediate frequency signal, and the output signal is a baseband signal.

  In the even harmonic mixer or the two-frequency mixer, the input signal is a baseband signal, and the output signal is a high-frequency signal or an intermediate-frequency signal.

  In the even harmonic mixer and the two-frequency mixer according to the present invention, the local oscillation signal is caused to act on the input signal in a multiplicative manner, so that the input signal is linearly operated, and the nonlinear operation is intentionally performed. Therefore, the cross modulation distortion can be easily suppressed without increasing the power consumption.

  Also, by using the same even harmonic mixer and two-frequency mixer as an up-converter in the transmitter, the spurious can be reduced because the cross modulation distortion is small. Can be shared.

  As for the input signal, a complementary signal on which direct current is superimposed is created using a differential amplifier and used. A field effect transistor or a bipolar transistor is used as the amplifying element. The differential output signal on which the direct current is superimposed is converted into a differential voltage signal by a resistive load and output.

  FIG. 1 is a circuit diagram showing an even harmonic mixer according to a first embodiment of the present invention, which receives a high frequency signal. Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q4. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 to Q4. A signal having a phase of 0 degrees of the local oscillator is supplied to the gate of the field effect transistor Q1, a signal having a phase of 180 degrees of the local oscillator is supplied to the gate of the field effect transistor Q2, and a local oscillator is supplied to the gate of the field effect transistor Q3. The signal having a phase of 270 degrees is supplied, and the signal of the local oscillator having a phase of 90 degrees is supplied to the gate of the field effect transistor Q4. The signal from the local oscillator is assumed to have a signal level that causes the nonlinear effect of the field effect transistors Q1 to Q4. Then, since the source potentials of the field effect transistors Q1 to Q4 are all the same, the sum of the drain currents of the field effect transistors Q1 and Q2 and the sum of the drain currents of the field effect transistors Q3 and Q4 are respectively connected to the terminal P1. It becomes a signal modulated by the even harmonic of the local oscillation signal with respect to the flowing current. When the signal from the local oscillator is considerably large, the path of the current flowing through the terminal P1 changes in the order of the field effect transistors Q1, Q4, Q2, Q3 by a quarter of the signal frequency from the local oscillator. Will go. Similarly, the sum of the drain currents of field effect transistors Q5 and Q6 and the sum of the drain currents of field effect transistors Q7 and Q8 are signals modulated by the even harmonics of the local oscillation signal with respect to the current flowing through terminal P2, respectively. It becomes. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant.

Here the angular frequency of the input signal omega _i, when the amplitude of the current flowing through the terminal P1, P2 a, the DC component is b, the current I _P1 flowing through the terminal P1, the current I _P2 flowing through the terminal P2 as follows Become.

I _P1 = a * sin (ω _i t) + b

I _P2 = -a * sin (ω _i t) + b

Further, the total drain current I _{12 of} the field effect transistors Q1 and Q2, the total drain current I _{34 of} the field effect transistors Q3 and Q4, the total drain current I _{56 of} the field effect transistors Q5 and Q6, and the field effect transistors Q7 and Q8. The drain current total I ₇₈ is as follows when the angular frequency of the local oscillation signal is ω _o .

I ₁₂ = {a * sin (ω _i t) + b} * {0.5-c * cos (2ω _o t)}

I ₃₄ = {a * sin (ω _i t) + b} * {0.5 + c * cos (2ω _o t)}

I ₅₆ = {-a * sin (ω _i t) + b} * {0.5 + c * cos (2ω _o t)}

I ₇₈ = {-a * sin (ω _i t) + b} * {0.5-c * cos (2ω _o t)}

However, c is an appropriate constant. Therefore, the current I _P3 passing through the terminal P3 and the current I _P4 passing through the terminal _P4 are

I _P3 = -2 * a * c * sin (ω _i t) * cos (2ω _o t) + b
= -a * c * {sin (ω _i t + 2ω _o t) + sin (ω _i t-2ω _o t)} + b

I _P4 = 2 * a * c * sin (ω _i t) * cos (2ω _o t) + b
= a * c * {sin (ω _i t + 2ω _o t) + sin (ω _i t-2ω _o t)} + b

Therefore, the output signal is modulated at a frequency twice that of the local oscillation signal with respect to the input signal, and becomes a mixed signal.

  The power consumption of this even harmonic mixer is the same as that of the Gilbert mixer. Although the number of transistors used is four more than that of the Gilbert mixer, the intermodulation distortion characteristic is determined by the differential amplifier formed by the field effect transistors Q9 and Q10, so that the power consumption does not increase. Also, the noise figure related to the white noise is almost determined by the differential amplifier constituted by the field effect transistors Q9 and Q10, so that it is almost the same as that of the Gilbert mixer.

  The motivation for using even harmonic mixers is to prevent self-mixing. That is, in order to prevent a direct current component from being superimposed on the output due to the local oscillation signal being turned to the high frequency input, the local oscillation frequency is reduced to half of the high frequency signal frequency so that a phenomenon such as self-mixing does not occur. A possible cause of self-mixing in a normal even harmonic mixer is due to the second harmonic of the local oscillation signal. However, the even harmonic mixer shown in FIG. 1 may be caused by the second harmonic included in the drain currents of the field effect transistors Q1 to Q8. However, the second harmonic is canceled out and hardly included in the current flowing through the terminals P3 and P4. In the even harmonic mixer shown in FIG. 1, the self-mixing due to the second harmonic of the local oscillation signal wrapping around the high frequency input and the second harmonic contained in the drain currents of the field effect transistors Q1 to Q8 is not caused. In addition, the physical layout of the circuit can be canceled, and the self-mixing due to the second harmonic contained in the drain currents of the field effect transistors Q1 to Q8 is caused by the drains of the field effect transistors Q1 to Q8. Can be reduced by shortening the wiring from the terminal to the terminal P3 or P4. Regarding the potential fluctuation of the terminals P1 and P2, in an ideal state, the frequency component is four times that of the local oscillation signal, and the frequency component twice that of the local oscillation signal is canceled out. In order to reduce the influence of this residual cancellation, although not shown in FIG. 1, a gate-grounded buffer or a base-grounded buffer is provided between the terminal P1 and the drain of the field effect transistor Q9 and between the terminal P2 and the drain of the field effect transistor Q10. You may put a buffer.

  As described above, the cross modulation distortion characteristic is almost determined by the signal distortion generated by the differential amplifier formed by the field effect transistors Q9 and Q10. Field effect transistors Q1 to Q8 only control the ratio of the distribution of current passing through terminals P1 and P2 to terminals P3 and P4, and therefore have little to do with distortion to the input signal. This is the same as the Gilbert mixer. In FIG. 1, no resistance is included in the sources of field effect transistors Q9 and Q10. However, resistances may be provided in the sources of field effect transistors Q9 and Q10. Intermodulation distortion can be reduced in exchange for a decrease in gain or a deterioration in noise figure.

  In the circuit shown in FIG. 1, it is assumed that the input signals are input complementarily to IN1 and IN2. The input signal may be supplied only to IN1, and the input signal may not be supplied to the gate of the field effect transistor Q10.

  In the circuit shown in FIG. 1, the output signals OUT1 and OUT2 are taken out using the load resistors R1 and R2 with respect to the current passing through the terminals P3 and P4. Alternatively, an inductive load may be used. Furthermore, you may take out an alternating current signal output using a transformer coupling.

  In FIG. 1, since it is assumed that the even harmonic mixer is applied to the down converter, the capacitors C1 and C2 are inserted. However, the even harmonic mixer may be used for the up converter. Particularly in such a case, the capacitors C1 and C2 may be omitted, and signals from IN1 and IN2 may be directly input to the gates of the field effect transistors Q9 and Q10.

  FIG. 2 shows an example of a chip layout when the even harmonic mixer according to the first embodiment of the present invention is formed as a monolithic IC. It is a top view. A cross-sectional view is shown in FIG. Only the portions corresponding to the field effect transistors Q1 to Q10 in the circuit shown in FIG. 1 are shown, and other components and wirings are omitted. In the figure, G1 to G10 indicate the gate regions of the field effect transistors Q1 to Q10, respectively. Similarly, D1 to D10 are drain regions, and S1 to S10 are source regions. Field effect transistors Q9 and Q10 are each divided into four. The substrate of each field effect transistor is P-type, and the surface of the drain region and the source region is N-type. In the figure, S9 + S10 is a region where the source of the field effect transistor Q9 serves as the source of the field effect transistor Q10. D9 + S1 + S5 is a region where the source region of the field effect transistor Q1 and the source region of the field effect transistor Q5 are combined, and a region that also serves as part of the drain of the field effect transistor Q9. The region that combines the source region of the effect transistor Q4 and the source region of the field effect transistor Q8 and also serves as a part of the drain of the field effect transistor Q9, D10 + S2 + S6 is the source region of the field effect transistor Q2 and the field effect D10 + S3 + S7 is a region combining the source region of the transistor Q6 and also serving as a part of the drain of the field effect transistor Q10. The region where the source region of the field effect transistor Q3 and the source region of the field effect transistor Q7 are combined. With field effect Part of the drain of the transistor Q10 is also an area which is also. D1 + D2 + D5 + D6 is a region where the drain regions of the field effect transistors Q1, Q2, Q5 and Q6 are combined, and D3 + D4 + D7 + D8 is a region where the drain regions of the field effect transistors Q3, Q4, Q7 and Q8 are combined. is there. The region “D9 + S1 + D5” and the region “D9 + S4 + S8” are electrically connected to each other, and the region “D10 + S2 + S6” and the region “D10 + S3 + S7” are electrically connected to each other.

  Thus, one advantage of having both the drain region of one field effect transistor and the source region of another field effect transistor is that the chip area can be reduced. One advantage of reducing the chip area is that the cost can be reduced. Another advantage is that the second harmonic radiation and induction of the local oscillation signal can be suppressed and self-mixing can be suppressed. It is done.

  In the circuit shown in FIG. 1, the second harmonic component of the local oscillation signal is largely contained in the current flowing through the wiring from the drain of the field effect transistors Q1 to Q8 to the terminal P3 or the terminal P4. In the chip layout shown in FIG. 2, the field effect transistor Q1 and the field effect transistor Q5 are arranged adjacent to each other to cancel the induction and radiation of the second harmonic component of the local oscillation signal included in each drain current, Care is taken to suppress self-mixing.

  In the even harmonic mixer of the circuit shown in FIG. 1, self-mixing does not occur when the circuit is perfectly symmetric and signal induction and radiation are also completely symmetric. However, when an even harmonic mixer is built on an IC, the circuit is not perfectly symmetric due to the fact that the mask used for IC manufacturing shifts and the characteristics of individual field effect transistors are not uniform. . As a countermeasure, a plurality of layouts shown in FIG. 2 may be prepared, and corresponding portions of the plurality of layouts may be electrically connected to each other so as to cancel the influence of the mask alignment error.

  FIG. 4 is a circuit diagram showing an even harmonic mixer according to a second embodiment of the present invention, which inputs a high frequency signal. The basic operation is the same as that of the first embodiment of the even harmonic mixer according to the present invention. In contrast, in the second embodiment of the even harmonic mixer in the present invention, the complementary input signal IN1 and IN2 are used for the complementary input signal current. That is, the current flowing through the terminals P1 and P2 is created using the inductive load by the inductors L1 and L2.

  The advantage of using the inductive load by the inductors L1 and L2 is that the number of transistors stacked in the mixer circuit can be reduced, so that the power supply voltage can be lowered, which is particularly advantageous for application to a portable type device. That is. In order to ensure the same characteristics as those of the first embodiment of the even harmonic mixer according to the present invention, it is necessary to provide an amplifier having a high impedance output in the previous stage. Also, a disadvantage of this method is that it is necessary to mount the inductors L1 and L2, and the chip area increases when an IC is formed.

  FIG. 5 is a circuit diagram showing an even harmonic mixer according to a third embodiment of the present invention, which inputs a high frequency signal. The basic operation is the same as that of the first embodiment of the even harmonic mixer according to the present invention, except that a field effect transistor is used in the even harmonic mixer according to the first embodiment of the present invention. In contrast, the even harmonic mixer according to the third embodiment of the present invention uses a bipolar transistor. Whether to use a field effect transistor or a bipolar transistor is selected depending on conditions such as compatibility with other circuits mounted in the same chip and power consumption.

  In the even harmonic mixer according to the third embodiment of the present invention, bipolar transistors are employed for all transistors. However, only bipolar transistors B9 and B10 constituting a differential amplifier are replaced with field effect transistors. The bipolar transistors B1 to B8 may be left as they are, or only the bipolar transistors B9 and B10 may be left as they are, and the bipolar transistors B1 to B8 may be replaced with field effect transistors.

  FIG. 6 is a circuit diagram showing an even harmonic mixer according to a fourth embodiment of the present invention, which receives a high frequency signal. Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q3. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 and Q2. A signal having a phase of 0 degrees of the local oscillator is supplied to the gate of the field effect transistor Q1, and a signal having a phase of 180 degrees of the local oscillator is supplied to the gate of the field effect transistor Q2. The signal from the local oscillator is assumed to have a high signal level that causes the field effect transistors Q1 and Q2 to perform a nonlinear operation. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 becomes a signal modulated by the even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. This is a phenomenon that occurs when the field effect transistor Q3 is connected as shown in FIG. 6, and the field effect transistors Q1 and Q2 alone cannot effectively modulate. Since the drain current of the field effect transistor Q3 is obtained by subtracting the sum of the drain currents of the field effect transistors Q1 and Q2 from the current flowing through the terminal P1, similarly, the even-order harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. The signal is modulated by the wave. Similarly, the sum of the drain currents of field effect transistors Q5 and Q6 and the drain current of field effect transistor Q7 are signals modulated by the even harmonics of the local oscillation signal with respect to the current flowing through terminal P2, respectively. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant. The drain currents of the field effect transistors Q1, Q2, Q5, and Q6 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3 and Q7 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 contain a lot of signals modulated by the second harmonic of the local oscillation signal with respect to the input signal.

  The advantage of the even harmonic mixer according to the fourth embodiment of the present invention over the even harmonic mixer according to the first embodiment of the present invention is that two transistors are used. However, the conversion gain as an even harmonic mixer is reduced accordingly. Further, since the second harmonic component of the local oscillation signal is included in the fluctuation component of the potentials at the terminals P1 and P2, caution is required for suppressing self-mixing.

  In the even harmonic mixer according to the fourth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the even harmonic mixer according to the fourth embodiment of the present invention, a differential amplifier is used to create a complementary current signal with a superimposed DC current. However, the differential amplifier need not be used. As in the even harmonic mixer according to the second embodiment of the present invention, by applying an inductive load to each of a pair of input signals to be differential signals after cutting a DC component with a capacitor, A complementary current signal superimposed with direct current may be created.

  In the even harmonic mixer according to the fourth embodiment of the present invention, it is assumed that the input signal is a high-frequency signal, but the input signal may be a baseband signal and the output signal may be a high-frequency signal. At that time, if necessary, the capacitors C1 and C2 are removed, and the input signal is directly input to the gates of the field effect transistors Q9 and Q10.

  FIG. 7 is a circuit diagram showing an even harmonic mixer according to a fifth embodiment of the present invention, which receives a high frequency signal. Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q3. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 and Q2. A signal having a phase of 0 degrees of the local oscillator is supplied to the gate of the field effect transistor Q1, and a signal having a phase of 180 degrees of the local oscillator is supplied to the gate of the field effect transistor Q2. The signal from the local oscillator is assumed to have a high signal level that causes the field effect transistors Q1 and Q2 to perform a nonlinear operation. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 becomes a signal modulated by the even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. This is a phenomenon that occurs when the field effect transistor Q3 is connected as shown in FIG. 7, and the field effect transistors Q1 and Q2 alone cannot effectively modulate. Since the drain current of the field effect transistor Q3 is obtained by subtracting the sum of the drain currents of the field effect transistors Q1 and Q2 from the current flowing through the terminal P1, similarly, the even-order harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. The signal is modulated by the wave. Similarly, the sum of the drain currents of field effect transistors Q5 and Q6 and the drain current of field effect transistor Q7 are signals modulated by the even harmonics of the local oscillation signal with respect to the current flowing through terminal P2, respectively. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant. The drain currents of the field effect transistors Q1, Q2, and Q7 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3, Q5, and Q6 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 contain a lot of signals modulated by the second harmonic of the local oscillation signal with respect to the input signal.

  The advantage of the even harmonic mixer according to the fifth embodiment of the present invention over the even harmonic mixer according to the first embodiment of the present invention is that two transistors are used. However, the conversion gain as an even harmonic mixer is reduced accordingly. The advantage of the even harmonic mixer according to the fifth embodiment of the present invention over the even harmonic mixer according to the fourth embodiment of the present invention is that the local oscillation signal may be two phases. However, when demodulating each of the I-phase and Q-phase components of the input signal, it is necessary to supply two even harmonic mixers with signals that are 45 degrees out of phase with each other. In the fourth embodiment, the symmetry of the local oscillator is improved.

  In the even harmonic mixer according to the fifth embodiment of the present invention, the second harmonic component of the local oscillation signal is included in the fluctuation component of the potential at the terminals P1 and P2, so that self-mixing is suppressed. Therefore, it is necessary to be careful.

  In the even harmonic mixer according to the fifth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the even harmonic mixer according to the fifth embodiment of the present invention, a differential amplifier is used to create a complementary current signal with a superimposed DC current. However, the differential amplifier need not be used. As in the even harmonic mixer according to the second embodiment of the present invention, by applying an inductive load to each of a pair of input signals to be differential signals after cutting a DC component with a capacitor, A complementary current signal superimposed with a direct current may be created.

  In the even harmonic mixer according to the fifth embodiment of the present invention, it is assumed that the input signal is a high frequency signal, but the input signal may be a baseband signal and the output signal may be a high frequency signal. At that time, if necessary, the capacitors C1 and C2 are removed, and the input signal is directly input to the gates of the field effect transistors Q9 and Q10.

  FIG. 8 is a circuit diagram showing an even harmonic mixer according to a sixth embodiment of the present invention, which receives a high frequency signal. Field effect transistors Q1 and Q6 have different characteristics from field effect transistors Q3 and Q7, such as different channel widths and different threshold voltages. Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current passing through terminal P1 is distributed by field effect transistors Q1 and Q3. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 and Q3. A signal having a phase of 0 degrees of the local oscillator is supplied to the gate of the field effect transistor Q1, and no AC signal is supplied to the gate of the field effect transistor Q3. The signal from the local oscillator is assumed to have a high signal level that causes the field effect transistor Q1 to perform a nonlinear operation. Then, the drain current of the field effect transistor Q1 becomes a signal modulated by a signal including even-order harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. This is because the characteristics of the field effect transistors Q1 and Q3 are different, so that the influence of even-order nonlinear terms appears. When the characteristics of the field effect transistors Q1 and Q3 are uniform, the even-order harmonics are present. The signal component modulated by the above cannot be extracted effectively. Since the drain current of the field effect transistor Q3 is obtained by subtracting the drain current of the field effect transistor Q1 from the current flowing through the terminal P1, similarly, a signal including even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. The signal is modulated by. Similarly, the drain current of the field effect transistor Q6 and the drain current of the field effect transistor Q7 are signals modulated by signals including even-order harmonics of the local oscillation signal with respect to the current flowing through the terminal P2. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant. The drain currents of the field effect transistors Q1 and Q7 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3 and Q6 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 contain a lot of signals modulated by the second harmonic of the local oscillation signal with respect to the input signal.

  The advantage of the even harmonic mixer according to the sixth embodiment of the present invention over the even harmonic mixer according to the fifth embodiment of the present invention is that two transistors are used. However, the conversion gain as an even harmonic mixer is reduced accordingly.

  In the even harmonic mixer according to the sixth embodiment of the present invention, the fundamental wave component and the second harmonic component of the local oscillation signal are often included in the fluctuation components of the potentials at the terminals P1 and P2. In this embodiment, since the conversion gain with respect to the fundamental frequency of the local oscillator is also high, care is required to suppress self-mixing.

  In the even harmonic mixer according to the sixth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the even harmonic mixer according to the sixth embodiment of the present invention, a differential amplifier is used to create a complementary current signal with a superimposed DC current. However, the differential amplifier need not be used. As in the even harmonic mixer according to the second embodiment of the present invention, by applying an inductive load to each of a pair of input signals to be differential signals after cutting a DC component with a capacitor, A complementary current signal superimposed with a direct current may be generated.

  In the even harmonic mixer according to the sixth embodiment of the present invention, it is assumed that the input signal is a high frequency signal, but the input signal may be a baseband signal and the output signal may be a high frequency signal. At that time, if necessary, the capacitors C1 and C2 are removed, and the input signal is directly input to the gates of the field effect transistors Q9 and Q10.

  FIG. 9 is a circuit diagram showing an even harmonic mixer according to a seventh embodiment of the present invention, which receives a high frequency signal. Field effect transistors Q1 and Q5 have different characteristics from field effect transistors Q3 and Q7, such as different channel widths and different threshold voltages. Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current passing through terminal P1 is distributed by field effect transistors Q1 and Q3. The distribution ratio is determined by the gate voltage of the field effect transistor Q1. A signal having a phase of 0 degrees of the local oscillator is supplied to the gate of the field effect transistor Q1, and no AC signal is supplied to the gate of the field effect transistor Q3. The signal from the local oscillator is assumed to have a high signal level that causes the field effect transistor Q1 to perform a nonlinear operation. Then, the drain current of the field effect transistor Q1 becomes a signal modulated by a signal including even-order harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. This is because the characteristics of the field effect transistors Q1 and Q3 are different, so that the influence of even-order nonlinear terms appears. When the characteristics of the field effect transistors Q1 and Q3 are uniform, even-order harmonics The signal component modulated by is less included. Since the drain current of the field effect transistor Q3 is obtained by subtracting the drain current of the field effect transistor Q1 from the current flowing through the terminal P1, similarly, a signal including even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. The signal is modulated by. Similarly, the drain current of field effect transistor Q5 and the drain current of field effect transistor Q7 are signals modulated by signals including even-order harmonics of the local oscillation signal with respect to the current flowing through terminal P2. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant. The drain currents of the field effect transistors Q1 and Q7 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3 and Q5 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 contain a lot of signals modulated by the second harmonic of the local oscillation signal with respect to the input signal.

  In the even harmonic mixer according to the seventh embodiment of the present invention, the fundamental wave component and the second harmonic component of the local oscillation signal are often included in the fluctuation components of the potentials at the terminals P1 and P2. In this embodiment, since the conversion gain with respect to the fundamental frequency of the local oscillator is also high, care is required to suppress self-mixing.

  The advantage of the even harmonic mixer according to the seventh embodiment of the present invention over the even harmonic mixer according to the sixth embodiment of the present invention is that the local oscillation signal needs only one phase. However, since the local oscillation signal is one phase, care must be taken when suppressing the local oscillation signal from entering the high frequency amplifier circuit.

  In the even harmonic mixer according to the seventh embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the even harmonic mixer according to the seventh embodiment of the present invention, a differential amplifier is used to create a complementary current signal superimposed with a direct current. However, the differential amplifier need not be used. As in the even harmonic mixer according to the second embodiment of the present invention, by applying an inductive load to each of a pair of input signals to be differential signals after cutting a DC component with a capacitor, A complementary current signal superimposed with a direct current may be generated.

  In the even harmonic mixer according to the seventh embodiment of the present invention, it is assumed that the input signal is a high frequency signal, but the input signal may be a baseband signal and the output signal may be a high frequency signal. At that time, if necessary, the capacitors C1 and C2 are removed, and the input signal is directly input to the gates of the field effect transistors Q9 and Q10.

  FIG. 10 is a circuit diagram showing an even harmonic mixer according to an eighth embodiment of the present invention, which receives a high frequency signal. An input signal is input to IN1, and is converted into a current signal on which a direct current is superimposed by an amplifier including a field effect transistor Q9, and passes through a terminal P1. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q4. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 to Q4. A signal having a phase of 0 degrees of the local oscillator is supplied to the gate of the field effect transistor Q1, a signal having a phase of 180 degrees of the local oscillator is supplied to the gate of the field effect transistor Q2, and a local oscillator is supplied to the gate of the field effect transistor Q3. A signal having a phase of 270 degrees is supplied to the gate of the field effect transistor Q4. The signal from the local oscillator is assumed to have a signal level that causes the nonlinear effect of the field effect transistors Q1 to Q4. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 becomes a signal modulated by the even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. When the signal from the local oscillator is considerably large, the path of the current flowing through the terminal P1 changes in the order of the field effect transistors Q1, Q3, Q2, Q4 by a quarter of the signal frequency from the local oscillator. Will go. Similarly, the sum of the drain currents of the field effect transistors Q3 and Q4 is a signal modulated by the even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant. The drain currents of the field effect transistors Q1 and Q2 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3 and Q4 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 contain a lot of signals modulated by the second harmonic of the local oscillation signal with respect to the input signal.

  The advantage of the even harmonic mixer according to the eighth embodiment of the present invention over the even harmonic mixer according to the first embodiment of the present invention is that the number of transistors used is small. However, since it does not operate complementary to the input signal, there is a concern that the cross modulation distortion will increase accordingly.

  In the even harmonic mixer according to the eighth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the even harmonic mixer according to the eighth embodiment of the present invention, an amplifier is used to create an input current signal superimposed with a direct current. However, the amplifier need not be used. As in the even harmonic mixer according to the embodiment, an input current signal on which a direct current is superimposed may be created by applying an inductive load to the input signal after cutting a direct current component with a capacitor.

  FIG. 11 is a circuit diagram showing an even harmonic mixer according to a ninth embodiment of the present invention, which receives a high frequency signal. An input signal is input to IN1, and is converted into a current signal on which a direct current is superimposed by an amplifier including a field effect transistor Q9, and passes through a terminal P1. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q3. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 and Q2. A signal having a phase of 0 degrees of the local oscillator is supplied to the gate of the field effect transistor Q1, and a signal having a phase of 180 degrees of the local oscillator is supplied to the gate of the field effect transistor Q2. A local oscillator signal is not input to the gate of the field effect transistor Q3. The signal from the local oscillator is assumed to have a high signal level that causes the field effect transistors Q1 and Q2 to perform a nonlinear operation. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 becomes a signal modulated by the even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. This is a phenomenon that occurs when the field effect transistor Q3 is connected as shown in FIG. 11, and the field effect transistors Q1 and Q2 alone cannot effectively modulate. Since the drain current of the field effect transistor Q3 is obtained by subtracting the sum of the drain currents of the field effect transistors Q1 and Q2 from the current flowing through the terminal P1, similarly, the even-order harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. The signal is modulated by the wave. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant. The drain currents of the field effect transistors Q1 and Q2 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain current of the field effect transistor Q3 is supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 contain a lot of signals modulated by the second harmonic of the local oscillation signal with respect to the input signal.

  The advantages of the even harmonic mixer according to the ninth embodiment of the present invention over the even harmonic mixer according to the eighth embodiment of the present invention are that the number of transistors used is further reduced and the local oscillation signal is used. Only two phases are needed. However, since a large amount of the second harmonic component of the local oscillation signal is included in the fluctuation component of the potential at the terminal P1, care must be taken to suppress self-mixing. In the even harmonic mixer according to the ninth embodiment of the present invention, since it does not operate complementary to the input signal, there is a concern that the cross modulation distortion increases correspondingly.

  In the even harmonic mixer according to the ninth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the even harmonic mixer according to the ninth embodiment of the present invention, an amplifier is used to create a DC superimposed input current signal. However, the amplifier need not be used. As in the even harmonic mixer according to the embodiment, an input current signal on which a direct current is superimposed may be created by applying an inductive load to the input signal after cutting a direct current component with a capacitor.

  FIG. 12 is a circuit diagram showing an even harmonic mixer according to the tenth embodiment of the present invention, which receives a high frequency signal. The field effect transistors Q1 and Q3 have different characteristics such as different channel widths and different threshold voltages. An input signal is input to IN1, and is converted into a current signal on which a direct current is superimposed by an amplifier including a field effect transistor Q9, and passes through a terminal P1. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 and Q3. The distribution ratio is determined by the gate voltage of the field effect transistor Q1. A local oscillator signal is supplied to the gate of the field effect transistor Q1. A local oscillator signal is not input to the gate of the field effect transistor Q3. The signal from the local oscillator is assumed to have a high signal level that causes the field effect transistors Q1 and Q2 to perform a nonlinear operation. Then, the drain current of the field effect transistor Q1 becomes a signal modulated by a signal including even-order harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. This is because the characteristics of the field effect transistors Q1 and Q3 are different, so that the influence of even-order nonlinear terms appears. When the characteristics of the field effect transistors Q1 and Q3 are uniform, the even-order harmonics are present. The signal component modulated by is less included. Since the drain current of the field effect transistor Q3 is obtained by subtracting the drain current of the field effect transistor Q1 from the current flowing through the terminal P1, similarly, a signal including even harmonics of the local oscillation signal with respect to the current flowing through the terminal P1. The signal is modulated by. In this case, of the even-order harmonics, the second-order harmonics having a lower order are dominant. The drain current of the field effect transistor Q1 is supplied to the load resistor R1, and a signal is output to the output OUT1. The drain current of the field effect transistor Q3 is supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 contain a lot of signals modulated by the second harmonic of the local oscillation signal with respect to the input signal.

  The advantages of the even harmonic mixer according to the tenth embodiment of the present invention over the even harmonic mixer according to the ninth embodiment of the present invention are that the number of transistors used is smaller and the local oscillation signal is Only one phase is needed. However, in order to ensure the gain as an even harmonic mixer, care should be taken such as setting the ratio of the channel widths of the field effect transistors Q1 and Q3 appropriately and appropriately setting the level of the signal LO1 from the local oscillator. is necessary.

  In the even harmonic mixer according to the tenth embodiment of the present invention, since it does not operate complementary to the input signal, there is a concern that the cross modulation distortion will increase accordingly. Moreover, since the second harmonic component of the local oscillation signal is often included in the fluctuation component of the potential at the terminal P1, care must be taken to suppress self-mixing.

  In the even harmonic mixer according to the tenth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the even harmonic mixer according to the tenth embodiment of the present invention, an amplifier is used to create a DC superimposed input current signal. However, it is not necessary to use an amplifier. As in the even harmonic mixer according to the embodiment, an input current signal on which a direct current is superimposed may be created by applying an inductive load to the input signal after cutting a direct current component with a capacitor.

  FIG. 13 is an explanatory view showing a usage pattern of the even harmonic mixer according to the eleventh embodiment of the present invention as a down converter. This is a down-converter that takes a high-frequency signal or an intermediate-frequency signal as an input and extracts a two-phase signal of an I-phase component and a Q-phase component of the baseband signal. In the figure, even harmonic mixers MX1 and MX2 are the even harmonic mixers of the first embodiment or the third to tenth embodiments of the present invention. In the down-converter of the even harmonic mixer according to the eleventh embodiment of the present invention, since the input signal is directly distributed to the two mixers, the even harmonic mixers MX1 and MX2 are voltage inputs with respect to the input signal. There is a need. The even harmonic mixer according to the second embodiment of the present invention is a current input for the input signal. Therefore, when used in the down converter according to the eleventh embodiment of the present invention, the even harmonic mixer is used. It is necessary to take measures such as providing a buffer in the input portion of the input signal of the mixer or using a distributor for inputting a high frequency signal to the two mixers. In FIG. 13, the even harmonic mixers MX1 and MX2 have complementary input signals and four-phase local oscillation signal inputs, whereas the inputs are complementary depending on the type of even harmonic mixers used. It is assumed that the input of the local oscillation signal is two-phase or one-phase, but there is no wiring if there is no corresponding input. The local oscillator OSC1 outputs a signal having a frequency that is half the frequency to be received, and outputs an eight-phase signal that is 45 degrees out of phase. Since the local oscillation signal supplied to the even harmonic mixer MX2 is 45 degrees out of phase with respect to the local oscillation signal supplied to the even harmonic mixer MX1, the even harmonic mixers MX1 and MX2 are in baseband. Two orthogonal components of the signal can be detected.

  FIG. 14 is an explanatory view showing a usage form as an up-converter of an even harmonic mixer according to a twelfth embodiment of the present invention. This is an up-converter that receives a two-phase baseband signal of an I-phase component and a Q-phase component and extracts a high-frequency signal or an intermediate-frequency signal. In the figure, even harmonic mixers MX1 and MX2 are even harmonic mixers according to any one of the first to seventh embodiments of the present invention. Since the even harmonic mixers MX1 and MX2 obtain an output signal by supplying a current signal to a resistance load, the signals are added by connecting the outputs of the even harmonic mixers MX1 and MX2 to each other. . In FIG. 14, even harmonic mixers MX1 and MX2 have a four-phase local oscillation signal input, whereas depending on the type of even harmonic mixer to be used, the local oscillation signal input has two phases. It is assumed that there is no wiring if there is no corresponding input. The local oscillator OSC1 outputs a signal having a frequency that is half the center frequency of the output signal, and outputs an 8-phase signal having a phase shift of 45 degrees. Since the local oscillation signal supplied to the even harmonic mixer MX2 is 45 degrees out of phase with the local oscillation signal supplied to the even harmonic mixer MX1, the even harmonic mixers MX1 and MX2 have two phases. Can be modulated as two-phase components orthogonal to each other.

  FIG. 15 is a circuit diagram of a two-frequency mixer according to a thirteenth embodiment of the present invention. Two types of local oscillation signals with different frequencies are mixed with the input signal, and a signal containing a signal whose frequency is shifted by the sum or difference of the two local oscillation frequencies with respect to the frequency of the input signal is output. It is.

  Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q4. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 to Q4. A signal having a phase of 0 degrees of the first local oscillator is supplied to the gate of the field effect transistor Q1, and a signal having a phase of 180 degrees of the first local oscillator is supplied to the gate of the field effect transistor Q2. A signal of 180 degrees phase of the second local oscillator is supplied to the gate of the second local oscillator, and a signal of phase 0 degree of the second local oscillator is supplied to the gate of the field effect transistor Q4. The signals from the first and second local oscillators are assumed to have a high signal level that causes the field effect transistors Q1 to Q4 to perform a nonlinear operation. Then, since the source potentials of the field effect transistors Q1 to Q4 are all the same, the sum of the drain currents of the field effect transistors Q1 and Q2 and the sum of the drain currents of the field effect transistors Q3 and Q4 are respectively connected to the terminal P1. A signal modulated by a signal including the frequency component of the sum and difference of the frequency of the first local oscillator and the frequency of the second local oscillator with respect to the flowing current. Similarly, the sum of the drain currents of field effect transistors Q5 and Q6 and the sum of the drain currents of field effect transistors Q7 and Q8 are respectively the frequency of the first local oscillator and the second local oscillator with respect to the current flowing through terminal P2. The signal is modulated by a signal including frequency components of the sum and difference of the frequencies. In this case, a second-order nonlinear term having a lower order is dominant in the nonlinear operation.

Here the angular frequency of the input signal omega _i, when the amplitude of the current flowing through the terminal P1, P2 a, the DC component is b, the current I _P1 flowing through the terminal P1, the current I _P2 flowing through the terminal P2 as follows Become.

I _P1 = a * sin (ω _i t) + b

I _P2 = -a * sin (ω _i t) + b

Further, the total drain current I _{12 of} the field effect transistors Q1 and Q2, the total drain current I _{34 of} the field effect transistors Q3 and Q4, the total drain current I _{56 of} the field effect transistors Q5 and Q6, and the field effect transistors Q7 and Q8. The drain current sum I ₇₈ is as follows, assuming that the angular frequency of the first local oscillation signal is ω ₁ and the angular frequency of the second local oscillation signal is ω ₂ .

However, c and d are appropriate constants. Therefore, current I _P3 passing through the terminal P3, the current I _P4 passing through the terminal P4, respectively as follows.

  Since these include terms of the three products of the input signal and the signal of two local oscillation frequencies, the output signal is also modulated by the frequency of the sum or difference of the two local oscillation signal frequencies with respect to the input signal. It becomes a signal including the received signal.

  The power consumption of this two-frequency mixer is the same as that of the Gilbert mixer. Although the number of transistors used is four more than that of the Gilbert mixer, the intermodulation distortion characteristic is determined by the differential amplifier formed by the field effect transistors Q9 and Q10, so that the power consumption does not increase. Also, the noise figure related to the white noise is almost determined by the differential amplifier constituted by the field effect transistors Q9 and Q10, so that it is almost the same as that of the Gilbert mixer.

  One motivation for using a two-frequency mixer is to prevent self-mixing. In other words, in order to prevent the DC component from being superimposed on the output due to the local oscillation signal traveling to the high frequency input, the sum or difference of the two local oscillation frequencies is used as the reception signal frequency so that a phenomenon such as self-mixing does not occur. ing.

  Another advantage of the two-frequency mixer is that the relative value of the variable range of the local oscillation frequency can be reduced when the variable width of the reception frequency must be increased. For example, consider a receiver that covers a frequency band from 470 MHz to 770 MHz. In order to realize this receiver by a direct conversion method using an even harmonic mixer, the variable width of the oscillation frequency of the local oscillator needs to be 1: 1.64 in relative ratio. In order to realize such a large variable range, a large restriction is imposed on the oscillator circuit to be used. However, if a two-frequency mixer is used, for example, the first local oscillator can be realized by changing the oscillation frequency from 3.6 GHz to 3.9 GHz and the second local oscillation frequency from 3.13 GHz. The variable range of the oscillation frequency of the oscillator can be reduced to a relative ratio of 1: 1.09 or less. However, in this example, since the interference wave is received by the mutual interference between the fourth harmonic of the first local oscillator and the fifth harmonic of the second local oscillator, the influence is sufficiently reduced. It is necessary to set the level of the local oscillation signal.

  As described above, the cross modulation distortion characteristic is almost determined by the signal distortion generated by the differential amplifier formed by the field effect transistors Q9 and Q10. Field effect transistors Q1 to Q8 only control the ratio of the distribution of current passing through terminals P1 and P2 to terminals P3 and P4, and therefore have little to do with distortion to the input signal. This is the same as the Gilbert mixer. In FIG. 15, the source of field effect transistors Q9 and Q10 has no resistance, but a resistance may be provided at the source of field effect transistors Q9 and Q10. Intermodulation distortion can be reduced in exchange for a decrease in gain and a decrease in noise figure.

  In the circuit shown in FIG. 15, it is assumed that the input signals are complementarily input to IN1 and IN2, but the deviation from the quiescent state of the current flowing through the terminals P1 and P2 only needs to be complementary. The input signal may be supplied only to IN1, and the input signal may not be supplied to the gate of the field effect transistor Q10.

  In the circuit shown in FIG. 15, the output signals OUT1 and OUT2 are taken out using the load resistors R1 and R2 with respect to the current passing through the terminals P3 and P4. Alternatively, an inductive load may be used. Furthermore, you may take out an alternating current signal output using a transformer coupling.

  In FIG. 15, since it is assumed that the even harmonic mixer is applied to the down converter, the capacitors C1 and C2 are inserted. However, the even harmonic mixer may be used for the up converter. Particularly in such a case, the capacitors C1 and C2 may be omitted, and signals from IN1 and IN2 may be directly input to the gates of the field effect transistors Q9 and Q10.

  In the dual frequency mixer according to the thirteenth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the two-frequency mixer according to the thirteenth embodiment of the present invention, the differential amplifier is used to create the complementary current signal superimposed with the direct current. However, the differential amplifier need not be used. As with the even harmonic mixer according to the second embodiment of the present invention, a direct current component is cut by a capacitor and then an inductive load is applied to each of a pair of input signals to be a differential signal, thereby producing a direct current. Complementary current signals superimposed on each other may be created.

  FIG. 16 is a circuit diagram showing a two-frequency mixer according to a fourteenth embodiment of the present invention, which receives a high frequency signal. Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q3. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 and Q2. A signal of phase 0 degree of the first local oscillator is supplied to the gate of the field effect transistor Q1, and a signal of phase 180 degree of the second local oscillator is supplied to the gate of the field effect transistor Q2. The signals from the first and second local oscillators are assumed to have a large signal level that causes the field effect transistors Q1 and Q2 to perform a nonlinear operation. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 includes the frequency component of the sum and difference of the frequency of the signal of the first local oscillator and the frequency of the second local oscillator with respect to the current flowing through the terminal P1. The signal is modulated by the signal. Since the drain current of the field effect transistor Q3 is obtained by subtracting the sum of the drain currents of the field effect transistors Q1 and Q2 from the current flowing through the terminal P1, the signal of the first local oscillator is similarly applied to the current flowing through the terminal P1. And a frequency modulated by a signal including the frequency component of the sum and difference of the frequency of the second local oscillator. Similarly, the sum of the drain currents of field effect transistors Q5 and Q6 and the drain current of field effect transistor Q7 are respectively the frequency of the first local oscillator signal and the frequency of the second local oscillator with respect to the current flowing through terminal P2. The signal is modulated by a signal including frequency components of the sum and difference. The drain currents of the field effect transistors Q1, Q2, Q5, and Q6 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3 and Q7 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 were modulated by a signal including the frequency component of the sum and difference of the frequency of the first local oscillator signal and the frequency of the second local oscillator with respect to the input signal. It contains a lot of signals.

  The advantage of the two-frequency mixer of the fourteenth embodiment of the present invention over the two-frequency mixer of the thirteenth embodiment of the present invention is that the number of transistors used is two smaller. However, the conversion gain as a two-frequency mixer is lowered accordingly.

  In the two-frequency mixer according to the fourteenth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the two-frequency mixer according to the fourteenth embodiment of the present invention, a differential amplifier is used to create a complementary current signal superimposed with a direct current. However, the differential amplifier need not be used. As with the even harmonic mixer according to the second embodiment of the present invention, a direct current component is cut by a capacitor and then an inductive load is applied to each of a pair of input signals to be a differential signal, thereby producing a direct current. Complementary current signals superimposed on each other may be created.

  In the two-frequency mixer according to the fourteenth embodiment of the present invention, it is assumed that the input signal is a high-frequency signal, but the input signal may be a baseband signal and the output signal may be a high-frequency signal. At that time, if necessary, the capacitors C1 and C2 are removed, and the input signal is directly input to the gates of the field effect transistors Q9 and Q10.

  FIG. 17 is a circuit diagram showing a two-frequency mixer according to a fifteenth embodiment of the present invention, in which a high frequency signal is input. Complementary input signals are input to IN1 and IN2, converted into complementary current signals superimposed with direct current by a differential amplifier composed of field effect transistors Q9 and Q10, and pass through terminals P1 and P2. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q3. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 and Q2. A signal of phase 0 degree of the first local oscillator is supplied to the gate of the field effect transistor Q1, and a signal of phase 0 degree of the second local oscillator is supplied to the gate of the field effect transistor Q2. The signals from the first and second local oscillators are assumed to have a large signal level that causes the field effect transistors Q1 and Q2 to perform a nonlinear operation. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 includes the frequency component of the sum and difference of the frequency of the signal of the first local oscillator and the frequency of the second local oscillator with respect to the current flowing through the terminal P1. The signal is modulated by the signal. Since the drain current of the field effect transistor Q3 is obtained by subtracting the sum of the drain currents of the field effect transistors Q1 and Q2 from the current flowing through the terminal P1, the signal of the first local oscillator is similarly applied to the current flowing through the terminal P1. And a frequency modulated by a signal including the frequency component of the sum and difference of the frequency of the second local oscillator. Similarly, the sum of the drain currents of field effect transistors Q5 and Q6 and the drain current of field effect transistor Q7 are respectively the frequency of the first local oscillator signal and the frequency of the second local oscillator with respect to the current flowing through terminal P2. The signal is modulated by a signal including frequency components of the sum and difference. The drain currents of the field effect transistors Q1, Q2, Q5, and Q6 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3 and Q7 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 were modulated by a signal including the frequency component of the sum and difference of the frequency of the first local oscillator signal and the frequency of the second local oscillator with respect to the input signal. It contains a lot of signals.

  The difference between the two-frequency mixer according to the fourteenth embodiment of the present invention and the two-frequency mixer according to the fifteenth embodiment of the present invention is the difference between the first and second local portions in the fourteenth embodiment of the present invention. Although a two-phase signal is required as an oscillator signal, in the fifteenth embodiment of the present invention, only a one-phase signal is required. Which two-frequency mixer is superior depends on the circuit of the local oscillator to be used.

  In the two-frequency mixer according to the fifteenth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the two-frequency mixer according to the fifteenth embodiment of the present invention, a differential amplifier is used to create a complementary current signal superimposed with a direct current. However, the differential amplifier need not be used. As with the even harmonic mixer according to the second embodiment of the present invention, a direct current component is cut by a capacitor and then an inductive load is applied to each of a pair of input signals to be a differential signal, thereby producing a direct current. Complementary current signals superimposed on each other may be created.

  In the two-frequency mixer according to the fifteenth embodiment of the present invention, it is assumed that the input signal is a high-frequency signal, but the input signal may be a baseband signal and the output signal may be a high-frequency signal. At that time, if necessary, the capacitors C1 and C2 are removed, and the input signal is directly input to the gates of the field effect transistors Q9 and Q10.

  FIG. 18 is a circuit diagram showing a two-frequency mixer according to the sixteenth embodiment of the present invention, which receives a high frequency signal. An input signal is input to IN1, and is converted into a current signal on which a direct current is superimposed by an amplifier including a field effect transistor Q9, and passes through a terminal P1. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q4. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 to Q4. A signal having a phase of 0 degrees of the first local oscillator is supplied to the gate of the field effect transistor Q1, and a signal having a phase of 180 degrees of the second local oscillator is supplied to the gate of the field effect transistor Q2. A signal of phase 0 degree of the second local oscillator is supplied to the gate of the first local oscillator, and a signal of phase 180 degree of the first local oscillator is supplied to the gate of the field effect transistor Q4. The signals from the first and second local oscillators are assumed to have a high signal level that causes the field effect transistors Q1 to Q4 to perform a nonlinear operation. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 includes the frequency component of the sum and difference of the frequency of the signal of the first local oscillator and the frequency of the second local oscillator with respect to the current flowing through the terminal P1. The signal is modulated by the signal. The sum of the drain currents of the field effect transistors Q3 and Q4 is obtained by subtracting the sum of the drain currents of the field effect transistors Q1 and Q2 from the current flowing through the terminal P1. The signal is modulated by a signal including the frequency component of the sum and difference of the frequency of the signal of the local oscillator and the frequency of the second local oscillator. The drain currents of the field effect transistors Q1 and Q2 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistors Q3 and Q4 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 were modulated by a signal including the frequency component of the sum and difference of the frequency of the first local oscillator signal and the frequency of the second local oscillator with respect to the input signal. It contains a lot of signals.

  The dual frequency mixer according to the sixteenth embodiment of the present invention has a feature that the circuit is simple because the input signal is not a complementary signal. Since it is not, there are points to be noted that the input signal is easy to pick up other signals, and that the cross modulation distortion increases accordingly.

  In the two-frequency mixer according to the sixteenth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the two-frequency mixer according to the sixteenth embodiment of the present invention, an amplifier is used to generate a DC superimposed current signal. However, the amplifier need not be used. As with an even harmonic mixer, the current signal on which the direct current is superimposed may be created by applying an inductive load to the input signal after cutting the direct current component with a capacitor.

  FIG. 19 is a circuit diagram showing a two-frequency mixer according to a seventeenth embodiment of the present invention, which receives a high frequency signal. An input signal is input to IN1, and is converted into a current signal on which a direct current is superimposed by an amplifier including a field effect transistor Q9, and passes through a terminal P1. The current that has passed through the terminal P1 is distributed by the field effect transistors Q1 to Q3. The distribution ratio is determined by the gate voltages of the field effect transistors Q1 and Q2. A signal of phase 0 degree of the first local oscillator is supplied to the gate of the field effect transistor Q1, a signal of phase 0 degree of the second local oscillator is supplied to the gate of the field effect transistor Q2, and the field effect transistor Q3 No AC signal is supplied to the gate. The signals from the first and second local oscillators are assumed to have a high signal level that causes the field effect transistors Q1 to Q4 to perform a nonlinear operation. Then, the sum of the drain currents of the field effect transistors Q1 and Q2 includes the frequency component of the sum and difference of the frequency of the signal of the first local oscillator and the frequency of the second local oscillator with respect to the current flowing through the terminal P1. The signal is modulated by the signal. Since the drain current of the field effect transistor Q3 is obtained by subtracting the sum of the drain currents of the field effect transistors Q1 and Q2 from the current flowing through the terminal P1, the signal of the first local oscillator is similarly applied to the current flowing through the terminal P1. And a frequency modulated by a signal including the frequency component of the sum and difference of the frequency of the second local oscillator. The drain currents of the field effect transistors Q1 and Q2 are summed and supplied to the load resistor R1, and a signal is output to the output OUT1. The drain currents of the field effect transistor Q3 are summed and supplied to the load resistor R2, and a signal is output to the output OUT2. As a result, the differential signals of the outputs OUT1 and OUT2 were modulated by a signal including the frequency component of the sum and difference of the frequency of the first local oscillator signal and the frequency of the second local oscillator with respect to the input signal. It contains a lot of signals.

  The advantages of the two-frequency mixer according to the seventeenth embodiment of the present invention over the two-frequency mixer according to the sixteenth embodiment of the present invention are that the number of transistors used is small and the first and second local oscillators are used. The signal of one phase is sufficient. However, the conversion gain as a two-frequency mixer is lowered accordingly.

  In the two-frequency mixer according to the seventeenth embodiment of the present invention, field effect transistors are used for all transistors, but bipolar transistors may be used. Further, a field effect transistor and a bipolar transistor may be mixed.

  In the two-frequency mixer according to the seventeenth embodiment of the present invention, an amplifier is used to generate a DC superimposed current signal. However, it is not necessary to use an amplifier. As with an even harmonic mixer, the current signal on which the direct current is superimposed may be created by applying an inductive load to the input signal after cutting the direct current component with a capacitor.

  FIG. 20 is an explanatory diagram showing a usage form of a two-frequency mixer according to an eighteenth embodiment of the present invention as a down converter. This is a down-converter that takes a high-frequency signal or an intermediate-frequency signal as an input and extracts a two-phase signal of an I-phase component and a Q-phase component of the baseband signal. In the figure, the two-frequency mixers MX3 and MX4 are the two-frequency mixers according to any one of the thirteenth to seventeenth embodiments of the present invention. In FIG. 20, the two-frequency mixers MX3 and MX4 have complementary input signals and two-phase inputs from two local oscillators, respectively, whereas the inputs are complementary depending on the type of the two-frequency mixer used. It is assumed that the local oscillation signal input is one phase, but there is no wiring if there is no corresponding input. The local oscillators OSC1 and OSC2 are such that the sum or difference of their output frequencies becomes the frequency of the received signal. The local oscillator OSC1 outputs a four-phase signal having a phase difference of 90 degrees, and a two-frequency mixer MX4 supplies a signal whose phase is shifted by 90 degrees with respect to a signal supplied to the two-frequency mixer MX3. . As for the output of the local oscillator OSC2, the same signal is supplied to the two-frequency mixers MX3 and MX4. Then, demodulated signals having components orthogonal to each other can be obtained from the two-frequency mixers MX3 and MX4. When using a two-frequency mixer, unlike when using an even harmonic mixer, when demodulating quadrature signals of I-phase and Q-phase, the phase is shifted by 90 degrees from either of the two local oscillators. It is not necessary to prepare a set of signals whose phases are shifted by 45 degrees.

  In FIG. 20, the local oscillator OSC1 outputs a four-phase signal. However, when the local oscillation signal input of the two-frequency mixers MX3 and MX4 is one phase, it can be a two-phase output. At that time, the local oscillator OSC2 can be one-phase output.

  FIG. 21 is an explanatory diagram showing a usage form of the two-frequency mixer according to the nineteenth embodiment of the present invention as an up-converter. This is an up-converter that receives a two-phase baseband signal of an I-phase component and a Q-phase component and extracts a high-frequency signal or an intermediate-frequency signal. In the figure, the two-frequency mixers MX3 and MX4 are the two-frequency mixers according to any of the thirteenth to fifteenth embodiments of the present invention. Since the two-frequency mixers MX3 and MX4 obtain an output signal by supplying a current signal to the resistance load, the signals are added by connecting the outputs of the two-frequency mixers MX3 and MX4 to each other. In FIG. 21, the two-frequency mixers MX3 and MX4 have two-phase inputs from two local oscillators, respectively, but depending on the type of the two-frequency mixer used, the local oscillation signal input is one-phase. Although there are wirings that do not have corresponding inputs, there are no wirings. The local oscillators OSC1 and OSC2 are such that the sum or difference of their output frequencies becomes the frequency of the received signal. The local oscillator OSC1 outputs a four-phase signal having a phase difference of 90 degrees, and a two-frequency mixer MX4 supplies a signal whose phase is shifted by 90 degrees with respect to a signal supplied to the two-frequency mixer MX3. . As for the output of the local oscillator OSC2, the same signal is supplied to the two-frequency mixers MX3 and MX4. Then, the two-phase baseband signals can be modulated as two-phase components that are orthogonal to each other. When using a two-frequency mixer, unlike when using an even harmonic mixer, when modulating I-phase and Q-phase quadrature signals, the phase of each of the two local oscillators is shifted by 90 degrees. It is not necessary to prepare a set of signals whose phases are shifted by 45 degrees.

  The even harmonic mixer and the two-frequency mixer of the present invention can be used as a mixer in a direct conversion type receiver. Since these have the characteristic that the cross modulation distortion is small, they greatly contribute to the improvement of the performance of the direct conversion type receiver.

  Further, in a transmission / reception apparatus using the same or close transmission / reception frequencies, when the direct conversion method using the even harmonic mixer or the two-frequency mixer of the present invention is used for reception, the even harmonic of the present invention is used for transmission. By using a single conversion method using a mixer or a two-frequency mixer, a local oscillator can be shared in transmission and reception, and the size of the transmitter and receiver can be reduced. Further, since the intermodulation distortion of the mixer is small, suppression of spurious transmission signals can be expected.

The even harmonic mixer which is 1st Example of this invention. 2 is an example of a chip layout in an even harmonic mixer according to the first embodiment of the present invention. Sectional drawing in the example of the chip layout in the even harmonic mixer which is 1st Example of this invention. The even harmonic mixer which is 2nd Example of this invention. The even harmonic mixer which is the 3rd Example of this invention. The even harmonic mixer which is the 4th example of the present invention. The even harmonic mixer which is the 5th Example of this invention. The even harmonic mixer which is the 6th Example of this invention. The even harmonic mixer which is the 7th Example of this invention. The even harmonic mixer which is the 8th Example of this invention. The even harmonic mixer which is the 9th Example of this invention. The even harmonic mixer which is the 10th Example of this invention. Explanatory drawing which showed the usage form as a down converter of the even harmonic mixer which is the 11th Example of this invention. Explanatory drawing which showed the usage type as an up converter of the even harmonic mixer which is the 12th Example of this invention. A two-frequency mixer according to a thirteenth embodiment of the present invention. A two-frequency mixer according to a fourteenth embodiment of the present invention. A two-frequency mixer according to a fifteenth embodiment of the present invention. A two-frequency mixer according to a sixteenth embodiment of the present invention. A two-frequency mixer according to a seventeenth embodiment of the present invention. Explanatory drawing which showed the usage type as a down converter of the 2 frequency mixer which is the 18th Example of this invention. Explanatory drawing which showed the usage type as an up-converter of the 2 frequency mixer which is the 19th Example of this invention. An example of a conventional even harmonic mixer.

Explanation of symbols

IN1 ... Input signal IN2 ... Input signal with opposite phase to IN1 OUT1 ... Output signal OUT2 ... Output signal with differential signal with OUT1 LO1 ... First Output signal of the local oscillator LO2 ... Signal that is 180 degrees out of phase with LO1 in the output signal of the first local oscillator LO3 ... Signal that is 90 degrees out of phase with LO1 in the output signal of the first local oscillator Signal LO4: Signal output from the first local oscillator that is 270 degrees out of phase with LO1 LO5: Output signal from the second local oscillator LO6: Output signal from the second local oscillator LO1 Signals that are 180 degrees out of phase P1 to P4 ... Signal terminals MX1, MX2 ... Even harmonic mixer MX3, MX4 ... Two-frequency mixer OSC1, OSC2 ... Local oscillator DESCRIPTION OF SYMBOLS 1-Q10 ... Field effect transistor G1-G10 ... Gate region of field effect transistor Q1-Q10 D1-D10 ... Drain region of field effect transistor Q1-Q10 S1-S10 ... Field effect transistor Q1- Q10 source region B1 to B10: Bipolar transistors R1, R2, R5: Resistors C1, C2: Capacitors L1, L2: Inductors VB1, VB2: Bias voltage

Claims (15)

  In the signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is superimposed with a DC component from the first input terminal and the second input terminal. The output signal is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is the first A local oscillation signal, a second local oscillation signal that is an inverted signal of the first local oscillation signal, a third local oscillation signal whose phase is delayed by 90 degrees from the first local oscillation signal, and a third local A fourth local oscillation signal which is an inverted signal of the oscillation signal, and has a first terminal, a second terminal, and a third terminal, and a current flowing between the third terminal and the second terminal is the first A first that is a function of the voltage between the terminal and the second terminal The second amplifier terminal, the second terminal of the second amplifier element, the second terminal of the third amplifier element, and the second terminal of the fourth amplifier element. Are connected to the first input terminal, the second terminal of the fifth amplifying element, the second terminal of the sixth amplifying element, the second terminal of the seventh amplifying element, and the eighth amplifying element. And the first local oscillation signal is supplied to the first terminal of the first amplifying element and the first terminal of the eighth amplifying element in an alternating current manner, The second local oscillation signal is supplied to the first terminal of the second amplifying element and the first terminal of the seventh amplifying element in an alternating manner, and the third local oscillation signal is supplied to the first terminal of the fourth amplifying element. And the first terminal of the fifth amplifying element are supplied in an alternating manner, and the fourth local oscillation signal is supplied to the first terminal of the third amplifying element and the first terminal of the sixth amplifying element. Are supplied in an alternating current to the first terminal, the third terminal of the first amplifying element, the third terminal of the second amplifying element, the third terminal of the fifth amplifying element, and the third terminal of the sixth amplifying element. Are connected to the first output terminal, the third terminal of the third amplifying element, the third terminal of the fourth amplifying element, the third terminal of the seventh amplifying element, and the eighth amplifying element. The third terminal is connected to the second output terminal, and outputs a signal including a signal having a frequency obtained by adding or subtracting twice the frequency of the local oscillation signal to the input signal. Even harmonic mixer.   In the signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is superimposed with a DC component from the first input terminal and the second input terminal. The output signal is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is the first A local oscillation signal, a second local oscillation signal that is an inverted signal of the first local oscillation signal, a third local oscillation signal whose phase is delayed by 90 degrees from the first local oscillation signal, and a third local A fourth local oscillation signal which is an inverted signal of the oscillation signal, and has a first terminal, a second terminal, and a third terminal, and a current flowing between the third terminal and the second terminal is the first A first that is a function of the voltage between the terminal and the second terminal The third and fifth to seventh amplifying elements have a second terminal of the first amplifying element, a second terminal of the second amplifying element, and a second terminal of the third amplifying element. The second terminal of the fifth amplifying element, the second terminal of the sixth amplifying element, and the second terminal of the seventh amplifying element are connected to the second input terminal, One local oscillation signal is supplied to the first terminal of the first amplifying element in an alternating manner, and the second local oscillation signal is supplied to the first terminal of the second amplifying element in an alternating manner, The local oscillation signal is supplied to the first terminal of the fifth amplifying element in an AC manner, the fourth local oscillation signal is supplied to the first terminal of the sixth amplifying device in an AC manner, and the third amplifying element is supplied. No signal is supplied to the first terminal and the first terminal of the seventh amplifying element in an alternating manner, and the third terminal of the first amplifying element and the third terminal of the second amplifying element are not supplied. The terminal, the third terminal of the fifth amplifying element, and the third terminal of the sixth amplifying element are connected to the first output terminal, and the third terminal of the third amplifying element and the seventh terminal of the seventh amplifying element are connected. The third terminal is connected to the second output terminal, and outputs a signal including a signal having a frequency that is added to or subtracted from the input signal by twice the frequency of the local oscillation signal. Even harmonic mixer.   In the signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is superimposed with a DC component from the first input terminal and the second input terminal. The output signal is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is the first And a second local oscillation signal that is an inverted signal of the first local oscillation signal, and has a first terminal, a second terminal, a third terminal, and a third terminal and a second terminal. Current flowing between the terminals has first to third and fifth to seventh amplification elements which are a function of the voltage between the first terminal and the second terminal, and the second of the first amplification elements The terminal, the second terminal of the second amplifying element and the third amplifying element. The second terminal of the fifth amplifying element, the second terminal of the sixth amplifying element, and the second terminal of the seventh amplifying element are the second input. The first local oscillation signal is supplied to the first terminal of the first amplifying element and the first terminal of the fifth amplifying element in an alternating manner, and the second local oscillation signal is The first terminal of the amplifying element and the first terminal of the sixth amplifying element are supplied in an alternating manner, and the first terminal of the third amplifying element and the first terminal of the seventh amplifying element are connected in an alternating manner. No signal is supplied to the third amplifying element, the third terminal of the first amplifying element, the third terminal of the second amplifying element, and the third terminal of the seventh amplifying element are connected to the first output terminal, The third terminal of the third amplifying element, the third terminal of the fifth amplifying element, and the third terminal of the sixth amplifying element are connected to a second output terminal, and the input signal Even harmonic mixer and outputs a signal including a frequency twice by addition or frequency of the signal obtained by subtracting the frequency of the local oscillation signal for.   In the signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is superimposed with a DC component from the first input terminal and the second input terminal. The output signal is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is the first And a second local oscillation signal that is an inverted signal of the first local oscillation signal, and has a first terminal, a second terminal, a third terminal, and a third terminal and a second terminal. The current flowing between the terminals has first, third, sixth and seventh amplifying elements that are a function of the voltage between the first terminal and the second terminal, and the first and sixth amplifying elements are Different characteristics from the third and seventh amplifying elements And the second terminal of the first amplifying element and the second terminal of the third amplifying element are connected to the first input terminal, and the second terminal of the sixth amplifying element and the seventh amplifying element are connected. The second terminal is connected to the second input terminal, the first local oscillation signal is supplied to the first terminal of the first amplifying element in an alternating manner, and the second local oscillation signal is supplied to the sixth amplifying element. To the first terminal of the third amplifying element, and no signal is supplied to the first terminal of the third amplifying element and the first terminal of the seventh amplifying element in an alternating manner, so that the first amplifying element And the third terminal of the seventh amplifying element are connected to the first output terminal, and the third terminal of the third amplifying element and the third terminal of the sixth amplifying element are the second terminal. Is connected to the output terminal, and outputs a signal including a signal having a frequency that is added to or subtracted from the input signal by twice the frequency of the local oscillation signal Even harmonic mixer according to claim Rukoto.   In the signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is superimposed with a DC component from the first input terminal and the second input terminal. The output signal is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal is the first The local oscillation signal of the first terminal, the second terminal, and the third terminal, and the current flowing between the third terminal and the second terminal flows between the first terminal and the second terminal. First, third, fifth and seventh amplification elements which are functions of voltage, the first and fifth amplification elements having different characteristics from the third and seventh amplification elements, The second terminal of the amplifying element and the second terminal of the third amplifying element The terminal is connected to the first input terminal, the second terminal of the fifth amplifying element and the second terminal of the seventh amplifying element are connected to the second input terminal, and the first local oscillation signal is AC is supplied to the first terminal of the first amplifying element and the first terminal of the fifth amplifying element, and the first terminal of the third amplifying element and the first terminal of the seventh amplifying element are No signal is supplied in alternating current, the third terminal of the first amplifying element and the third terminal of the seventh amplifying element are connected to the first output terminal, and the third terminal of the third amplifying element is connected. The terminal and the third terminal of the fifth amplifying element are connected to the second output terminal, and include a signal having a frequency that is added to or subtracted from the input signal by a frequency that is twice the frequency of the local oscillation signal. An even harmonic mixer that outputs a signal.   In signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is input as a current input with a DC component superimposed from a first input terminal. The output signal is output as a differential current output in which a direct current component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal includes the first local oscillation signal, the first local oscillation signal, A second local oscillation signal which is an inverted signal of the local oscillation signal, a third local oscillation signal whose phase is delayed by 90 degrees from the first local oscillation signal, and a fourth signal which is an inverted signal of the third local oscillation signal The local oscillation signal of the first terminal, the second terminal, and the third terminal, and the current flowing between the third terminal and the second terminal flows between the first terminal and the second terminal. Having first to fourth amplifying elements which are functions of voltage, The second terminal of the second amplifying element, the second terminal of the second amplifying element, the second terminal of the third amplifying element, and the second terminal of the fourth amplifying element are connected to the first input terminal. The first local oscillation signal is supplied to the first terminal of the first amplifying element in an AC manner, the second local oscillation signal is supplied to the first terminal of the second amplifying device in an AC manner, and The third local oscillation signal is supplied to the first terminal of the third amplifying element in an alternating manner, and the fourth local oscillation signal is supplied to the first terminal of the fourth amplifying element in an alternating manner. The third terminal of the amplifying element and the third terminal of the second amplifying element are connected to the first output terminal, and the third terminal of the third amplifying element and the third terminal of the fourth amplifying element are A signal connected to a second output terminal and including a signal having a frequency added to or subtracted from the input signal by a frequency twice the frequency of the local oscillation signal; An even harmonic mixer characterized by output.   In signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is input as a current input with a DC component superimposed from a first input terminal. The output signal is output as a differential current output in which a direct current component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal includes the first local oscillation signal, the first local oscillation signal, A second local oscillation signal which is an inverted signal of the local oscillation signal, which has a first terminal, a second terminal, and a third terminal, and a current flowing between the third terminal and the second terminal is the first. Having a first to third amplifying element that is a function of the voltage between the first terminal and the second terminal, the second terminal of the first amplifying element, the second terminal of the second amplifying element, and the third A second terminal of the amplifying element is connected to the first input terminal, and the first station The oscillation signal is supplied to the first terminal of the first amplifying element in an alternating manner, the second local oscillation signal is supplied to the first terminal of the second amplifying element in an alternating manner, and No signal is supplied to the first terminal in an alternating manner, the third terminal of the first amplifying element and the third terminal of the second amplifying element are connected to the first output terminal, and the third terminal The third terminal of the amplifying element is connected to the second output terminal, and outputs a signal including a signal having a frequency obtained by adding or subtracting twice the frequency of the local oscillation signal to the input signal. An even harmonic mixer.   In signal conversion means for inputting an input signal and a local oscillation signal and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is input as a current input with a DC component superimposed from a first input terminal. The output signal is output as a differential current output in which a DC component is superimposed from the first output terminal and the second output terminal, and the local oscillation signal includes the first local oscillation signal, First and second terminals, a second terminal and a third terminal, and a current flowing between the third terminal and the second terminal is a function of a voltage between the first terminal and the second terminal. The first amplifying element has a characteristic different from that of the third amplifying element, and the second terminal of the first amplifying element and the second terminal of the third amplifying element are the first amplifying elements. The first local oscillation signal is connected to the input terminal of the first amplification element AC is supplied to the first terminal, no signal is supplied to the first terminal of the third amplifying element in an AC manner, and the third terminal of the first amplifying element is connected to the first output terminal. The third terminal of the third amplifying element is connected to the second output terminal, and a signal having a frequency that is added to or subtracted from the input signal by a frequency that is twice the frequency of the local oscillation signal. An even harmonic mixer that outputs a signal including a signal including the signal.   In the signal converting means for inputting the input signal, the local oscillation signal of the first local oscillator and the local oscillation signal of the second local oscillator, and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is The first input terminal and the second input terminal are input as complementary current inputs superimposed with a direct current component, and the output signal is a difference in which the direct current component is superimposed from the first output terminal and the second output terminal. The local oscillation signal of the first local oscillator is output as a dynamic current output, and includes a first local oscillation signal and a second local oscillation signal that is an inverted signal of the first local oscillation signal, The local oscillation signal of the local oscillator is composed of a fifth local oscillation signal and a sixth local oscillation signal that is an inverted signal of the fifth local oscillation signal. The first terminal, the second terminal, and the third terminal are connected to each other. Holding third terminal and second terminal Has a first to eighth amplifying elements that are a function of the voltage between the first terminal and the second terminal, and the second terminals of the first amplifying elements and the second amplifying elements of the second amplifying elements The second terminal, the second terminal of the third amplifying element, and the second terminal of the fourth amplifying element are connected to the first input terminal, and the second terminal and the sixth amplifying element of the fifth amplifying element are connected. The second terminal of the element, the second terminal of the seventh amplifying element, and the second terminal of the eighth amplifying element are connected to the second input terminal, and the first local oscillation signal is the first amplifying element. And the second local oscillation signal are supplied to the first terminal of the third amplifying element and the first terminal of the sixth amplifying element. And the fifth local oscillation signal is supplied to the first terminal of the fourth amplifying element and the first terminal of the fifth amplifying element in an AC manner, The partial oscillation signal is supplied to the first terminal of the second amplifying element and the first terminal of the seventh amplifying element in an alternating manner, and the third terminal of the first amplifying element and the third terminal of the second amplifying element are supplied. , The third terminal of the fifth amplifying element and the third terminal of the sixth amplifying element are connected to the first output terminal, and the third terminal and the fourth amplifying element of the third amplifying element. A third terminal of the first amplifying element, a third terminal of the seventh amplifying element, and a third terminal of the eighth amplifying element are connected to a second output terminal, and a local part of the first local oscillator is connected to the input signal. A two-frequency mixer that outputs a signal including a signal having a frequency that is added or subtracted by the sum or difference of the frequency of the oscillation signal and the frequency of the local oscillation signal of the second local oscillator.   In the signal converting means for inputting the input signal, the local oscillation signal of the first local oscillator and the local oscillation signal of the second local oscillator, and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is The first input terminal and the second input terminal are input as complementary current inputs superimposed with a direct current component, and the output signal is a difference in which the direct current component is superimposed from the first output terminal and the second output terminal. The local oscillation signal of the first local oscillator is output as a dynamic current output, and includes a first local oscillation signal and a second local oscillation signal that is an inverted signal of the first local oscillation signal, The local oscillation signal of the local oscillator is composed of a fifth local oscillation signal and a sixth local oscillation signal that is an inverted signal of the fifth local oscillation signal. The first terminal, the second terminal, and the third terminal are connected to each other. Holding third terminal and second terminal Having first to third and fifth to seventh amplifying elements, the current flowing through the first terminal being a function of the voltage between the first terminal and the second terminal, and the second terminal of the first amplifying element and the second terminal The second terminal of the second amplifying element and the second terminal of the third amplifying element are connected to the first input terminal, and the second terminal of the fifth amplifying element and the second terminal of the sixth amplifying element And the second terminal of the seventh amplifying element is connected to the second input terminal, the first local oscillation signal is supplied to the first terminal of the first amplifying element in an alternating manner, and the second local The oscillation signal is supplied to the first terminal of the sixth amplifying element in an alternating manner, and the fifth local oscillation signal is supplied to the first terminal of the fifth amplifying element in an alternating manner, and the sixth local oscillation signal is supplied. Is supplied to the first terminal of the second amplifying element in an alternating manner, and the first terminal of the third amplifying element and the first terminal of the seventh amplifying element are exchanged in an alternating manner. The third terminal of the first amplifying element, the third terminal of the second amplifying element, the third terminal of the fifth amplifying element, and the third terminal of the sixth amplifying element are not supplied. The third terminal of the third amplifying element and the third terminal of the seventh amplifying element are connected to the second output terminal, and the first local oscillator of the first local oscillator is connected to the input signal. A two-frequency mixer that outputs a signal including a signal having a frequency added or subtracted by a sum or difference frequency of the frequency of the local oscillation signal and the frequency of the local oscillation signal of the second local oscillator.   In the signal converting means for inputting the input signal, the local oscillation signal of the first local oscillator and the local oscillation signal of the second local oscillator, and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is The first input terminal and the second input terminal are input as complementary current inputs superimposed with a direct current component, and the output signal is a difference in which the direct current component is superimposed from the first output terminal and the second output terminal. Output as a dynamic current output, the local oscillation signal of the first local oscillator is composed of the first local oscillation signal, the local oscillation signal of the second local oscillator is composed of the fifth local oscillation signal, A first to a third terminal having a terminal, a second terminal, and a third terminal, the current flowing between the third terminal and the second terminal being a function of the voltage between the first terminal and the second terminal; And fifth to seventh amplifying elements, The second terminal of the amplifying element, the second terminal of the second amplifying element, and the second terminal of the third amplifying element are connected to the first input terminal, and the second terminal of the fifth amplifying element; The second terminal of the sixth amplifying element and the second terminal of the seventh amplifying element are connected to the second input terminal, and the first local oscillation signal is transmitted from the first terminal of the first amplifying element and the second terminal. The fifth local oscillation signal is supplied to the first terminal of the fifth amplifying element and the first terminal of the second amplifying element in an AC manner. No signal is supplied to the first terminal of the third amplifying element and the first terminal of the seventh amplifying element in an alternating manner, and the third terminal and the second amplifying element of the first amplifying element are not supplied. And the third terminal of the seventh amplifying element are connected to the first output terminal, the third terminal of the third amplifying element, the third terminal of the fifth amplifying element, and the third terminal. The third terminal of the amplifying element is connected to the second output terminal, and the sum of the frequency of the local oscillation signal of the first local oscillator and the frequency of the local oscillation signal of the second local oscillator with respect to the input signal or A two-frequency mixer that outputs a signal including a signal having a frequency added or subtracted by a difference frequency.   In the signal converting means for inputting the input signal, the local oscillation signal of the first local oscillator and the local oscillation signal of the second local oscillator, and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is A current input with a DC component superimposed is input from a first input terminal, and the output signal is output as a differential current output with a DC component superimposed from a first output terminal and a second output terminal, The local oscillation signal of the first local oscillator is composed of a first local oscillation signal and a second local oscillation signal which is an inverted signal of the first local oscillation signal. The local oscillation signal of the second local oscillator is the fifth local oscillation signal. And a sixth local oscillation signal that is an inverted signal of the fifth local oscillation signal, and has a first terminal, a second terminal, a third terminal, and a third terminal and a second terminal. The current flowing between the terminals and the first terminal Having a first to a fourth amplifying element that is a function of the voltage between the two terminals, the second terminal of the first amplifying element, the second terminal of the second amplifying element, and the third amplifying element. The second terminal and the second terminal of the fourth amplifying element are connected to the first input terminal, and the first local oscillation signal is supplied to the first terminal of the first amplifying element in an alternating current manner. The second local oscillation signal is supplied to the first terminal of the fourth amplifying element in an alternating manner, and the fifth local oscillation signal is supplied to the first terminal of the third amplifying element in an alternating manner, The local oscillation signal is supplied to the first terminal of the second amplifying element in an alternating manner, and the third terminal of the first amplifying element and the third terminal of the second amplifying element are connected to the first output terminal. The third terminal of the third amplifying element and the third terminal of the fourth amplifying element are connected to the second output terminal, and the first local oscillator is connected to the input signal. 2 frequency mixer and outputs the signal including the frequency and the frequency of the signal in which only the added or subtracted frequency of the sum or difference of the frequencies of the local oscillation signal of the second local oscillator parts oscillation signal.   In the signal converting means for inputting the input signal, the local oscillation signal of the first local oscillator and the local oscillation signal of the second local oscillator, and outputting an output signal whose frequency is shifted with respect to the input signal, the input signal is A current input with a DC component superimposed is input from a first input terminal, and the output signal is output as a differential current output with a DC component superimposed from a first output terminal and a second output terminal, The local oscillation signal of the first local oscillator is made up of the first local oscillation signal, the local oscillation signal of the second local oscillator is made up of the fifth local oscillation signal, the first terminal, the second terminal, and the third Having first to third amplifying elements in which the current flowing between the third terminal and the second terminal is a function of the voltage between the first terminal and the second terminal. The second terminal of the amplifying element and the second terminal of the second amplifying element And the second terminal of the third amplifying element are connected to the first input terminal, the first local oscillation signal is supplied to the first terminal of the first amplifying element in an AC manner, The local oscillation signal is supplied to the first terminal of the second amplifying element in an alternating manner, and no signal is supplied to the first terminal of the third amplifying element in an alternating manner. 3 and the third terminal of the second amplifying element are connected to the first output terminal, the third terminal of the third amplifying element is connected to the second output terminal, and 2. Outputting a signal including a signal having a frequency obtained by adding or subtracting only the sum or difference of the frequency of the local oscillation signal of the first local oscillator and the frequency of the local oscillation signal of the second local oscillator. Frequency mixer.   14. The even harmonic mixer or the two frequency mixer according to claim 1, wherein the input signal is a high frequency signal or an intermediate frequency signal, and the output signal is a baseband signal. Mixer. In the even harmonic mixer according to any one of claims 1 to 6 and the two-frequency mixer according to claims 9 to 11, the input signal is a baseband signal, and the output signal is a high frequency signal or an intermediate frequency signal. Feature even harmonic mixer or two frequency mixer.

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