EP3915186A1 - Convertisseur continu-continu comprenant un circuit de pont pour la mise hors tension ainsi que procédé correspondant - Google Patents

Convertisseur continu-continu comprenant un circuit de pont pour la mise hors tension ainsi que procédé correspondant

Info

Publication number
EP3915186A1
EP3915186A1 EP20701433.3A EP20701433A EP3915186A1 EP 3915186 A1 EP3915186 A1 EP 3915186A1 EP 20701433 A EP20701433 A EP 20701433A EP 3915186 A1 EP3915186 A1 EP 3915186A1
Authority
EP
European Patent Office
Prior art keywords
coil
zvs
current
bridge
transformer
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
EP20701433.3A
Other languages
German (de)
English (en)
Inventor
Nicolae Daniel BOLOHAN
Egi NAZERAJ
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Brusa Hypower Ag
Original Assignee
Brusa Elektronik AG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Brusa Elektronik AG filed Critical Brusa Elektronik AG
Publication of EP3915186A1 publication Critical patent/EP3915186A1/fr
Pending legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33573—Full-bridge at primary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0064—Magnetic structures combining different functions, e.g. storage, filtering or transformation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/01—Resonant DC/DC converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • DC-DC CONVERTER WITH BRIDGE CIRCUIT FOR POWERless SWITCHING AND RELATED METHOD
  • the invention relates to the technical field of bridge circuits.
  • the present invention relates to a bridge circuit, a DC-DC converter with the bridge circuit, a method for operating a bridge circuit and a programming element.
  • ZVS Zero Voltage Switching
  • Bridge circuit a method for operating a bridge circuit and a program element specified.
  • a bridge circuit has a first and a second high-side switch, a first and a second low-side switch, a transformer with a primary coil and a secondary coil, a coil and a current injection device.
  • the first high-side switch and the first low-side switch are connected to a first bridge connection in a series circuit in order to form a first bridge branch.
  • the second high-side switch and the second low-side switch are connected to a second bridge connection in a series connection in order to form a second bridge branch.
  • the first and second bridge branches are each connected to a first and a second input connection in a parallel circuit, the secondary coil having a first and a second output connection.
  • the primary coil and the coil or inductor are connected in series to the first
  • Current impressing device is set up to impress a predetermined current into the coil at a predetermined point in time.
  • a DC / DC converter direct current / direct current converter
  • a method for operating a bridge circuit is specified, the method comprising operating the switches of the bridge circuit in such a way that a predetermined circuit is operated
  • a program element comprising a program code, which is set up, when it is executed by a processor, to carry out the method for operating a bridge circuit.
  • a floppy disc, hard disk, USB (Universal Serial Bus) storage device, RAM (Random Access Memory), ROM (Read Only Memory) or EPROM (Erasable Programmable Read Only Memory) may be used as a computer-readable storage medium.
  • An ASIC application-specific integrated circuit
  • an FPGA field-programmable gate array
  • SSD solid-state drive
  • a web server or a cloud can also be used as a storage medium.
  • Computer-readable storage medium may also be viewed as a communications network, such as the Internet, which may allow program code to be downloaded. It can be a radio-based network technology and / or one
  • wired network technology can be used.
  • the use of a current injection device can ensure that existing energy is withdrawn from a switch of the bridge circuit in order to switch the switch in a state that is as currentless as possible.
  • the switch in a state that is as currentless as possible.
  • a coupling between the further coil and the coil is low.
  • the coupling between the further coil and the coil is less than the coupling between the primary coil and the secondary coil of the transformer.
  • a coupling of the further coil and the coil has a lower magnetic coupling factor than the coupling between the primary coil and the secondary coil of the transformer.
  • This low coupling factor of the ZVS transformer may allow a current to be injected into the coil, but not load the circuit with a high voltage.
  • the low coupling factor of the ZVS transformer can provide a large leakage inductance of the ZVS transformer, which allows magnetic energy to be stored, but which has only a minor influence on the output performance of an inverter. If, contrary to the low coupling factor, the ZVS transformer, which has the coil and the current shaping device, had a high or good coupling factor, the remaining inductance would not be sufficient to summarize or withdraw the energy which is required for ZVS conditions.
  • the high leakage inductance or the leakage inductance of the ZVS transformer is used to generate or impress a current that is required to achieve ZVS (Zero Voltage Switching).
  • the magnetic coupling factor between the further coil and the coil may have a value of approximately 0.9 with a maximum possible value of 1.
  • Coupling factors of typical power transformers may be in the range of 0.995.
  • the main transformer may also have a magnetic coupling factor of approximately 0.995 and thus be significantly larger than the magnetic coupling factor of the ZVS
  • the bridge circuit further has a high-side capacitor and a low-side capacitor.
  • the high-side capacitor and the low-side capacitor are connected in series at a third bridge connection to form a third bridge branch, the third bridge branch being connected to the first and second input connections and the further coil being the third bridge connection connects to at least one of the first bridge connector and the second bridge connector.
  • the two capacitors, the high-side capacitor and the low-side capacitor keep the ZVS transformer at a medium voltage potential.
  • the magnetic core of the ZVS transformer is balanced and the first high-side switch and the first low-side switch can be controlled with a symmetrical switching pattern.
  • Bridge circuit on a synchronous rectifier.
  • the synchronous rectifier is connected to the first and second output terminals.
  • the synchronous rectifier can be actively controlled.
  • the control can be designed such that the synchronous rectifier is short-circuited for a predeterminable duration during a free-running phase of the bridge circuit or the phase-shifted full bridge.
  • the current in the ZVS additional transformer can be increased, in particular an additional current can be impressed in a coil of the ZVS additional transformer T zvs .
  • This additional current can be used to switch the ZVS and / or ZCS to the respective one To enable switching phase belonging to the high-side switch and / or low-side switch by this switch making a transition from one switching state to the other, essentially without a voltage being present across this switch.
  • Bridge circuit a control device which is connected to each of the first and second high switches and low switches.
  • the control device is set up to operate the switches in such a way that the predetermined current is impressed into the coil by the current impressing device at the predetermined point in time.
  • Secondary switches may also be used for impressing, for example switches of a secondary rectifier and / or the synchronous rectifier. This switching of the switches may take place during a freewheeling phase.
  • the control device may, for example, be set up in such a way that it operates switches on the secondary side such that the predetermined current is impressed into the coil.
  • the switch or switches on the secondary side may be switches of a rectifier on the secondary side and / or a synchronous rectifier.
  • the secondary switch and / or the plurality of secondary switches may be implemented using MOSFET components.
  • the level of the impressed current may be able to be determined indirectly through the time period for which the one, the two and / or the plurality of secondary switches are switched simultaneously and thus the one, the two and / or the plurality of secondary coils are short-circuited. This short-circuiting of the secondary coil and / or the plurality of secondary coils may take place during one freewheeling phase of one of the high-side switches and / or the low-side switches.
  • control device is further configured to operate the and / or the high-side switch and / or low-side switch in such a way that the predetermined current is impressed into the coil when the predetermined one Time the current through the coil is below a predetermined threshold.
  • FIG. 1 shows a block diagram of a DC-DC converter with a bridge circuit according to an exemplary embodiment of the present invention.
  • Fig. 2 shows a block diagram of a DC-DC converter with a bridge circuit and two main transformers according to an exemplary embodiment! of the present invention.
  • FIG. 3 shows a block diagram of a DC-DC converter with a bridge circuit and a main transformer with center tap according to an example
  • FIG. 4a shows diagrams of various signal profiles of a PSFB without using the additional transformer according to an exemplary embodiment of the present invention.
  • FIG. 4b shows diagrams of different signal profiles of a PSFB using the additional transformer according to an exemplary embodiment of the present invention.
  • 5a shows a section from diagram 4a according to an example
  • 5b shows a section from diagram 4b according to an example
  • FIGS. 1 to 5b The representations in the figures are schematic and not to scale. In the following description of FIGS. 1 to 5b, the same reference numbers are used for identical or corresponding elements.
  • capacitor and “capacitance” as well as “coil” or “choke” and “inductance” may be used interchangeably and, unless stated otherwise, should not be interpreted restrictively.
  • high-side may refer to a connection to a live potential.
  • low-side may refer to a connection with a reference potential.
  • FIG. 1 shows a block diagram of a DC-DC converter 100 with a bridge circuit 101 according to an exemplary embodiment of the present invention.
  • PSFB phase-shifted full bridge
  • Bridge circuit 101 can be achieved with phase-shifted switching behavior. These good switching conditions may be achieved if an essentially voltage-free switching of the respectively active switches A, B, C, D can be established.
  • the voltage-free switching, ZVS (Zero Voltage Switching) or zero voltage switching makes it possible to avoid high switching losses, which can arise in particular when switching high voltages due to parasitic elements in the switches A, B, C, D, since energy is stored in these parasitic elements may be against which the switches A, B, C, D must be worked against.
  • ZCS Zero Current Switching
  • a bridge circuit 101 can be used, for example, in a DC-DC converter 100 to convert an input voltage V in to an output voltage V out .
  • V in and V out are direct voltages.
  • Bridge circuit 101 converted to an alternating current (AC) and converted back to the output DC voltage by means of rectification.
  • AC alternating current
  • V n high voltages
  • the voltages Vin are provided, for example, by the DC intermediate circuit of the electric vehicle.
  • the voltage Vin can also come from the on-board component of a charging device.
  • the DC-DC converter 100 can be used instead of an alternator of a vehicle for providing the on-board voltage 12V.
  • the 12V on-board voltage is not generated directly by mechanical work, but rather by the DC-DC converter 100 converting the high voltage (HV) of an HV battery (DC voltage, DC) into the 12V on-board voltage of an EV (electrical vechicle) or PHEV (plug - converts into hybrid electric vehiclescie).
  • the HV is in a load circuit or intermediate circuit
  • the energy extracted from the HV circuit is used to charge a 12V on-board supply battery on which the 12V
  • the OBC unit (not shown in FIG. 1) that Vin supplies is used to charge the DC link's HV battery.
  • the OBC unit itself obtains its energy, for example, from an AC power supply (also not shown in FIG. 1), the so-called main, for example via an AC or three-phase connection. Therefore, the voltages Vin of the HV direct voltages (DC) can be in the range of 400V - 800V or in a range less than 800V.
  • Bridge circuit 101 is configured in such a way that it can deal with voltages of corresponding size and fluctuation range,
  • the voltage V in is supplied to the bridge circuit 101 via a first input terminal 102 and a second input terminal 103rd
  • the first input connection 102 may be referred to as a high-side connection 102 and the second input connection 103 may be referred to as a low-side connection 103.
  • These input connections 102, 103 form a parallel connection of the first 107 and the second 108 bridge arm.
  • the first bridge branch 107 is formed from a series connection of the first high-side switch A and the first low-side switch B.
  • the second bridge branch 108 is formed from the series connection of the second high switch C and the second low-side switch D.
  • the first high-side switch A has the control connection 104a
  • the first low-side switch B has the control connection 104b
  • the second high-side switch C has the control connection 104c
  • the second low-side switch D has the control connection 104d.
  • the control connections 104a, 104b, 104c, 104d are connected to a control device, not shown in FIG. 1, which controls the switches ABC, D in a phase-shifted manner.
  • the control is carried out by means of the control device such that essentially the first high-side switch A and the second low-side switch D are switched simultaneously. And so that the second high-side switch C and the second low-side switch B are switched simultaneously.
  • a pause or dead time is provided between the switching of the switches belonging to one another, during which no switch is activated and during which all switches are open.
  • a switching ratio d of 50% is essentially provided during the switching process, so that essentially the switch combinations A, D and B, C are active for the same length of time.
  • the switch pairs A, D and and B, C which are switched essentially simultaneously, are arranged diagonally to the coil T and / or the coil T3 B , so that the switching of the switch pairs A, D and / or B, C for reversed current flow through the coil T3 B ensures.
  • the control pattern for the phase-shifted control of the switches ABC, D essentially corresponds to a control pattern or control scheme used for a phase shift switching full bridge (PSFB).
  • FIG. 4a shows a diagram 400a of an extended signal curve of a PSFB with subsequent A / B without using the additional transformer according to one
  • Circuit diagram 400a shows a selection of signal profiles for operating a phase-shifted full bridge converter circuit without a ZVS transformer T zvs .
  • the current I T1A through the primary coil decreases, since in this phase the leading branch C, D is switched.
  • the current I T1A continues to decrease since here, by simultaneously connecting switches B, D, a circuit with switch B, switch D and primary coil T 1 A is formed. The current decreases due to the current flow circulating in this freewheeling circuit.
  • the circuit formed in the freewheeling phase II behaves like an RL circuit, which is formed from the line resistances and the primary coil T 1A .
  • the line resistances cause losses caused by the current which flows to break down the stored magnetic energy. Due to the losses that occur during the freewheeling phase II, the magnetic energy stored in the inductance T1 A during the switching or transition phase 404 a of the lagging branch 107 (lagging leg transition) A, B is lower than in FIG.
  • Transition phase 406a of leading leg transition C, D Consequently, there is insufficient magnetic energy available to fully discharge the parasitic capacitances of switches A, B of the lagging branch, for example the parasitic capacitances of a MOSFET switch A, B
  • 4b shows diagrams of different signal profiles, in particular voltage profiles and current profiles depending on a switching behavior of a bridge circuit 101 and / or a synchronous rectifier SR1, SR2 when using the
  • Additional transformer T zvs according to an exemplary embodiment of the present invention.
  • the current I T1A continues to rise after the switchover phase 406b because the T3 B winding of the T zvs transformer is short-circuited, while at the same time half the input voltage is present at the T3 A winding of T zvs .
  • the increase in the primary current I T1A continues until the switchover instant 404b of the lagging branch (lagging leg) MB, in which the low-side switch B 104b is switched off and the high-side switch A 104a is switched on.
  • the increase in the primary current I T1A allows the available magnetic energy to be increased during the lagging leg MB transition 404b.
  • Transition phase 404b of the switching of the trailing branch 107 A / B take place as a soft transition and a soft ZVS on switching of the switch A 104a is carried out.
  • the circuit diagram 400b shows, as drain-source voltage Vds A, the profile of the voltage across the high-side switch A, that is, the profile of the voltage between the connection 102 and the bridge point 105 in the first bridge branch 107 in the event that the additional transformer T corresponds accordingly Fig. 1 is used.
  • Circuit diagram 400a shows as drain-source voltage Vds A the corresponding voltage curve in the event that no additional transformer is used and thus only the primary coil T1A is solely responsible for switching the high switch A.
  • 5a shows a section from diagram 4a according to an example
  • Embodiment of the present invention shows the switching phase 404a of the switch A of the trailing branch 107, in particular that
  • Control voltage of switch A for example the gate voltage, if switch A is implemented as a MOSFET.
  • Voltage curve A indicates that switch A cannot be discharged before the switching process is carried out, as can also be seen from point 407a of the curve of switching signal Vds A , so that only hard switching takes place.
  • 5b shows a section from diagram 4b according to an example
  • Embodiment of the present invention. 5 shows the ZVS switching process of switch A 104a. Assuming that switch A is implemented as a MOSFET, after the switching process in switching phase 404b at point 408b of the course of the gate voltage of switch A there is no Miller Plateau available. The voltage across the switch A 104a, for example the drain-source voltage Vds A , has already dropped to 0 V when switching, as is illustrated at point 407b. So is a
  • signal A corresponds to gate voltage Vg at switch A 104a
  • signal B corresponds to gate voltage Vg at switch B 104b
  • signal C corresponds to gate voltage Vg at Switch C 104c
  • the signal D of the gate voltage Vg at the switch D 1Q4d
  • the switches A 104a, B 104b, C 104c, D 104d are designed as normally blocking MOSFETS. This means that the application of a voltage to the respective gate or a high pulse in diagrams 400a, 400b corresponds to a closed switch through which current can flow.
  • the use of self-conducting MOSFETs is also possible with inverse signs.
  • the signal SR1 corresponds to the gate voltage at the switch SR1.
  • the signal SR2 corresponds to the gate voltage at the switch SR2.
  • the signal I 1A corresponds to the time course of the primary current through the coil T1 A , in particular through the primary coil T1 A.
  • the signal Vds A corresponds to the time course of the drain-source voltage in
  • FIGS. 4a, 5a, 4b, 5b show the same control patterns of switches A, B, C, D, SR1, SR2, although a different control pattern would possibly be used in a PSFB without T zvs according to FIG. 4a, since switches SR1, SR2 would not be short-circuited during freewheeling phase II in order to achieve ZVS switching.
  • a bridge branch 107, 108 can be referred to as a leg 107, 108.
  • the second bridge branch 108 or leg CD 108 which has the switches C and D, is actuated as a leading branch 108.
  • the first bridge branch 107 or leg AB 107 which has the switches A and B, is driven as a lagging leg 107.
  • leg CD 108 is phase-shifted compared to leg AB in order to control and / or regulate the output voltage Vout through the phase shift.
  • Diagram 400a shows the control pattern for the switches A, B, C, D in the event that no ZVS transformer T zvs , ie no coil T3 A and no coil T3 B is used.
  • the time profile of the diagram 400a is essentially divided into four phases I, II, III and IV.
  • the diagram 400b shows the control pattern for the switches A, B, C, D in the event that the ZVS transformer T zvs is used, that is to say that the coil T3 A and the coil T3 B are used.
  • control patterns for switches A, B, C, D are essentially the same for both diagram 400a and diagram 400b. Likewise, the division of phases I, II, III and IV.
  • the control patterns of the synchronous rectifiers SR1, SR2 in diagrams 400a and 400b also correspond.
  • phase I switches B 104b and C 104c are switched on or activated ("B & C on").
  • This phase I is referred to as the energizing phase.
  • energy and / or power from the supply source V in for example the HV battery, which is connected to the nodes 102, 103, is transferred to the load (not shown in FIG. 1) at the connections 1 10a, 110b, V transferred out .
  • the current flow therefore takes place in phase I essentially via node 102, switch C, primary coil T1 A and, if coil T3 B is present, via T3 B , via switch B in node 103.
  • phase I is considered for the case that no transformer T zvs is provided, for the case that neither the coil T3 A nor the coil T3 B is present.
  • the associated signal curves are shown in Figs. 4a, 5a shown.
  • the current IT IA in the main transformer T1 A increases with a slope according to the formula:
  • i denotes the current I T1A through the primary coil T1 A
  • Vo 'de notes the voltage at the primary coil T1 A , which is generated by the voltage V out at the connections 110a, 110b at the load (not shown) via the transformer T1 to the primary side of the transformer T1 A , is reflected.
  • L 1 'de notes the inductance of the coil T1 A. The dash at Vo 'and LT indicates that these are values that have been reflected in the primary coil T1 A.
  • i designates the primary current I T1A , n zvs the number of turns of the ZVS transformer T zvs and 2 n zvs the double number of turns, it being assumed that the coils T3 A and T3 B have the same number of turns n.
  • the energy supply phase I “B&C on” only the change in the current I T1A through the primary coil over time is affected by the provision of the ZVS transformer T zvs and there are therefore essentially no changes compared to the control method of a PSFB circuit in which the ZVS transformer T zvs is not provided.
  • the greater the number of turns n zvs of the ZVS transformer T zvs the less noticeable the ZVS transformer T zvs .
  • transition phase 406a, 406b between phase I and phase II.
  • the switch C 104c is switched off, via the in phase I the current I T1A has been supplied and the switch D 104d is switched on (turn-off C / turn-on D).
  • This transition phase 406a, 406b is called the transition of the leading bridge branch 108 (leading leg transition). 2.a) In the case of Figs.
  • the parasitic capacitance of switches C and D is substantially completely discharged or charged during transition phase 406a.
  • the energy used for discharging and / or charging is taken up or given off by the leakage inductance (not shown in FIG. 1) of the primary winding T1 A in the form of magnetic energy.
  • the magnetic energy of the leakage inductance of the primary winding T1 A is determined as follows:
  • DE L denotes the change in energy in the primary leakage inductance L lk of transformer T1 and I the current I T1A through the primary coil T1 A.
  • this formula generally refers to the achievement of a ZVS condition using switches A and B and is not limited to phase II only. If there is sufficient current in the main transformer T1A, C and D are switched and ZVS can also be reached for these two switches.
  • ZVS switching A and B
  • the change in the inductive energy stored in the primary leakage inductance of T1 should be greater than the change in the capacitive energy DE c stored in the parasitic capacitances C mos of the switches A and B.
  • the leakage inductance on the primary side should be dimensioned such that this condition is met.
  • Formula (4) expresses that the energy stored in the leakage inductance of the coil T1 A must be greater than the energy stored in the parasitic capacitances C mos of the switches C and D and the energy stored in the parasitic capacitance C tr of the transformer T1 is stored.
  • the switching operation “turn-off C / turn-on D” of the leading branch 108 during the transition phase 406a is usually a smooth transition, since the current I TA1 is at its maximum value and the energy of the leakage inductance is sufficiently large to fully charge and discharge the capacitors C mos and C tr .
  • transition phase 406a which follows the end of the energy supply phase I, the two switches C, D of the leading branch 108 (leading leg) 108 are switched over essentially simultaneously. There is only a small dead time between switching off C and switching on D.
  • the closed switch C of the leading branch 108 is opened during the transition phase 406a and the open switch D of the leading branch 108 is closed “turn-off C / turn-on D”. Since switches A, B of trailing branch 107 are not yet actuated, switch A remains open and switch B is closed.
  • switches A, C are open and / or are opened during the transition phase 406a and since the current flowing further through T1 A is sufficiently large to discharge parasitic charges from the bridge point 106 and thus from the switches C, D, both can Switch C and switch D are switched in the transition phase 406a essentially under ZVS conditions.
  • the diagrams 400b result, as shown in Figs. 4b, 5b.
  • these diagrams essentially do not differ from the transition process 406a from FIG. 2a), in which no ZVS transformer is provided.
  • the control procedure is also essentially the same.
  • the primary coil T1A drives the current I T1A that has flowed during phase I via the primary coil T1 A and the coil because of the drop in current T3 B , as well as via switch B, node 103 and switch D.
  • the freewheeling loop thus has the primary coil T1 A , the coil T3 B , the switch B, the low-side node 103 and the switch D.
  • Phase II following transition phase 406a, 406b is referred to as free-running phase II.
  • the low-side switches B 104b and D 104d are switched on (B & D on), i.e. closed and the high-side switches A, C opened.
  • l p is the peak current that flows during the transition phase 406a “transition of the leading leg branch” from 2. following the energy supply phase I.
  • the resistance value r ds, on is the on-resistance of the Switch B or D, for example the MOSFET B or D.
  • the end of the freewheeling phase II determines the further transition phase 404a, which is characterized in that the switches A, B of the trailing branch 107 are switched in this further transition phase 404a.
  • the high-side switch A is switched on or closed and the low-side switch B is switched off or opened. If the leakage inductance is too small and / or insufficient current I T1A flows through the primary winding T1 A of the main transformer T1, the lagging switching process can occur Branch 107 in the transition phase 404a no ZVS switching can be achieved. Because if one only increased the leakage inductance of T1, this would affect the output performance. Therefore, increasing the leakage inductance is essentially avoided. The current cannot be increased easily. However, the use of the ZVS transformer and the simultaneous activation of switches SR1 and SR2 during the free-running phase managed to increase the current
  • the current I T1A through the primary winding T1 A of the main transformer T1 can be increased if the transformer is used by means of the ZVS that during the free-running phase II before the transition phase 404b, the synchronous rectifiers SR1, SR2 are activated or closed simultaneously. Before the switches A, B of the lagging branch 107 are switched, the synchronous rectifiers SR1, SR2 are simultaneously activated or closed, as a result of which the output 110a, 110b and in particular the secondary coil T1B are short-circuited. This simultaneous activation of SR1, SR2 generates an additional current pulse in the primary coil T1 A , which increases the current I T1A and thus also results in an increase in the current through the ZVS transformer.
  • the ZVS transformer can be used to simultaneously activate the synchronous rectifiers SR1, SR2 during the freewheeling phase II, II B during the transition phase 404b ZVS to create conditions for switching switches A, B during transition phase 404b.
  • phase II by activating the low-side switches B and D, a closed circuit is formed from the series connection of the ZVS secondary coil T3 B , the primary coil T 1 A and the two switches B and D. While this primary-side circuit is formed by simultaneously connecting the first low-side switch B and the second low-side switch D to the negative potentials with the bridge connections 105 and 106, the two switches SR1, SR2 of the secondary-side rectifier become shortly before the activation of the switches A, B of the lagging branch 107 activated during the final phase II A , II B. According to FIGS. 4a and 4b, only the first synchronous rectifier SR1 is activated in the final phase II A , II B , since the second synchronous rectifier SR2 is already activated.
  • the second synchronous rectifier SR2 is switched off before the further transition phase 404a, 404b, that is to say before the switches A, B of the lagging branch 107 are actuated.
  • the two switches SR1, SR2 in the end phase II A , II B the two connections of the secondary coil T1 B are simultaneously connected to the same potential, for example to the ground potential and in this way, before the transition phase 404a, 404b of the trailing branch 107 a circuit is formed on the secondary side from the secondary coil T1 B and the two switches SR1, SR2.
  • This (in terms of magnitude) current increase which is additionally caused by the leakage inductance L Ik and the secondary-side short-circuiting, can be seen in FIG. 4b at point 409b in the region of the end of the free phase II B , while SR1 and SR2 are on.
  • This current rise is before the transition phase 404b, while in the same area II of FIG. 4a, without a T zvs , a drop in the current i T1A can be seen.
  • switch B 104b is switched off and switch A 104a is switched on (turn-off B / turn-on A).
  • This phase 404a, 404b “turn-off B / turn-on A” is referred to as the transition of lagging leg 107 (lagging leg transition) A / B.
  • the current increases continuously, but in the opposite direction, so that the current at points 405a, 405b of 0A differs.
  • the amount of current increase depends on the output power of converter 100. This current provides the ZVS conditions when switching the switches C, D of the leading branch 108.
  • phase II A and / or IV A the conditions for ZVS switching of A and B are not reached. Only if, as can be seen in phases II B and / or IVB, a ZVS transformer is present and the switches SR1, SR2 are switched on at the same or the same time, ZVS conditions for switching A and B can be achieved. Alternatively or additionally, the leakage inductance of T1 could also be increased, which, however, can lead to losses in the output performance and therefore, when it is carried out, is carried out only to a small extent.
  • the current i can 1A after a sudden surname in the transition phase 406a, 406b, the current flow i 1A during the freewheeling phase II after the other until the end portion II A, II B is reached.
  • the courses of the current i 1A of FIGS. 4a and 4b correspond regardless of whether the ZVS transformer T zvs is present or not
  • the phase 404a of the transition of the lagging branch 107 is a critical phase, since it is related to the freewheeling phase II connects. Because, as can be seen in FIG. 4a as well as in FIG. 5a at reference number 407a, lies in Area of transition 404a of trailing branch 107 still has voltage across switch A while switch A is actuated. The actuation of the switch is shown at reference number 408a. In the example that the switch A is realized by a MOSFET, the switch A is activated at its gate in the area 408a, the entire voltage VDSA still being present at its drain-source connection in this time area.
  • 5a shows the detail 404a in the region of the transition of the lagging leg transition 107 (lagging leg transition) in the event that no transformer T zvs is provided.
  • Transformer T zvs is provided, as shown in Figs. 4b, 5b, by activating the switches SR1, SR2 during the final phase II B, an increased current I T1A flows during the final phase II B. Because of the increased current flow in the final phase II B , a smooth transition when switching A and B can be generated. The current i T1A does not stop at the point 405b, but continues to flow, in particular it continues to rise during the final phase Ile of the freewheeling phase II up to the point 409b. This increase in
  • Rectifiers SR1, SR2 reinforced on the primary side.
  • the ZVS transformer T zvs i.e. the combination of the coils T3 A or T3 B , has the function during the freewheeling phase II or IV and in particular in an end region II B or IV B, ie during the time interval during which the switches SR1, SR2 are activated at the same time and short-circuit the secondary coil T1 B to increase the primary current I 1A . Since the low-side switches B and D during the freewheeling phase II
  • the voltage across T3 B is kept at 0V during the freewheeling phase II.
  • the voltage reflected in the primary coil from the secondary side is therefore also zero.
  • the voltage across the coil T3 A is half that
  • Input voltage 1 ⁇ 2 V in The voltage across T3 B is kept at 0V during freewheeling phase II. While the voltage of the T3 A winding is not equal to zero, the current increases linearly through the ZVS transformer T zvs . This current is proportional to the time that SR1 and SR2 are activated and inversely proportional to the leakage inductance of T zvs .
  • the switch B can be switched under ZVS conditions during the transition phase 404b immediately after the freewheeling phase II, in particular the low-side switch B can be switched under ZVS Conditions are turned off.
  • the current additionally impressed by the coil T3 A into the coil T3 B is conducted into the connection node 105 between the switches A and B and thereby helps all the charge in parasitic elements from the high-side switch A and / or to remove all voltage across the high-side switch A and to provide ZVS conditions for switching the switch A.
  • the high-side switch A of the lagging branch 107 can be switched by a short dead time after the low-side switch B of the lagging branch 107 under ZVS conditions, as shown in FIG. 5b.
  • the two switches A, B of the lagging branch 107 may apply that the two switches A, B of the lagging branch 107 are switched essentially simultaneously during the transition phase 406b.
  • the high-side switch A of the lagging branch 107 is switched in time after the low-side switch B of the lagging branch 107.
  • the high-side switch A of the lagging branch 107 may be switched during phase III after the low-side switch B of the lagging branch 107, which is switched during the freewheeling phase II.
  • the low-side switch B of the lagging branch 107 is switched before the second synchronous rectifier SR2 and the high-side switch A of the lagging branch 107 is switched after the second synchronous rectifier SR2.
  • the switch A of the trailing branch 107 which is in the freewheeling loop, is again switched first. Since the voltage in this freewheeling loop is kept at 0V, switch A of the following branch can be switched under ZVS conditions. If this switch is switched, the current additionally generated by switching the synchronous rectifiers SR1, SR2 can be used to also switch the second switch B under ZVS conditions.
  • the switching behavior of the switches A 104a, B 104b, C 104c, D 104d is shown in Figs. 4a, 4b, 5a, 5b the same, regardless of whether the ZVS transformer Tzvs is present, as shown in Figs. 4b, 5b is required or does not exist, as shown in Figs. 4a, 5a is required.
  • This switching behavior corresponds to the switching behavior of a phase shifted full bridge (PSFB), so that the ZVS transformer T zvs can be retrofitted to every PSFB without changing the switching behavior.
  • PSFB phase shifted full bridge
  • the ZVS transformer Tzvs provides the current increase 409a in the final phase II B of the freewheeling phase II or the current increase with the opposite sign in the
  • V in Vds A + Fds B
  • 5b shows the detail in the area of the switching interval 404b or the transition phase 404b.
  • the switching time 407b of the switches A and B of the lagging leg branch in the event that a transformer T zvs is provided, the voltage Vds A across the switch A has dropped to essentially 0 V, so that ZVS Switching is possible.
  • the switches A, B are connected in the first bridge connection 105 and the switches C, D are connected in series in the second bridge connection 106.
  • the first bridge connection 105 and the second bridge connection 106 are also connected via a series connection of the coil T3 B and the primary coil T1 A of the main transformer T1.
  • the coil T3 B may 1 A of the main transformer to be construed as an additional coil T3 B TO the primary coil T, since it can be used to increase the total inductance of the series connection of T1 A and T3 B.
  • a high total inductance between the nodes 105 and 106 can improve the ZVS behavior of the bridge circuit 101.
  • the additional coil T3 B can with a current injection device T3 A or
  • the current injection device T3 A can be coupled.
  • the current injection device T3 A is also a coil T3 A.
  • the coil B T3 may be coupled to low magnetic coupling and thus form the additional transformer T zvs or ZVS transformer T zvs with the auxiliary coil B T3.
  • the ZVS switching of switches A and B can be achieved using a small transformer T zvs with low magnetic coupling.
  • the Stromeingarge stimulating T3 A forms the primary coil T3 A of the auxiliary transformer T and the auxiliary coil zvs T3 A, the secondary coil T3 A forms the additional transformer T ⁇ zvs
  • the DC-DC converter By connecting the additional transformer T zvs in series with the main transformer T1, good output capability for the phase shifted full bridge can be achieved. If the input voltage V in falls below a predeterminable value, the DC-DC converter cannot generate a voltage which is able to supply a load connected to the output 110a, 110b, for example the output of the DC-DC converter manages it not to charge a 12V battery if that
  • Input voltage V in is too low. If a current injection device T3 A or a primary winding T3 A is provided, which is coupled to a secondary coil T3 B , which is connected in series with the primary coil T1A of the main transformer, this performance of the output 110a, 110b can be increased.
  • a current injection device T3 A or a primary winding T3 A is provided, which is coupled to a secondary coil T3 B , which is connected in series with the primary coil T1A of the main transformer, this performance of the output 110a, 110b can be increased.
  • Output performance can therefore be characterized in that even with a low input voltage V in , a load can still be supplied with a power at the output of the DC-DC converter, but this is then also due to the low power
  • Input voltage V may be low.
  • Voltage range V in depending on the state of charge of the high-voltage battery (HV battery) connected to the high-side node 102 and the low-side node 103 can be large. All switches A, B, C, connected to the primary coil T1 A of the main transformer T1
  • D are called primary switches. These can be realized with the help of MOSFETs A, B, C, D. In order to enable a ZVS for all primary switches A, B, C, D, the series connection of the auxiliary coil T3 B with the primary coil T1 A is
  • Main transformer T1 provided.
  • the additional voltage at the additional coil T3 B enables the good output capability at the output 110 to be achieved.
  • T3 B The voltage drop across T3 B affects the performance of output 110 and the addition of a primary coil T3 A which is magnetically coupled to T3 B increases the performance of the output by increasing the voltage applied to the primary side of main transformer T1 becomes.
  • T zvs has a two-fold effect on increasing the performance of the output.
  • the voltage applied to the primary coil T1 A of the main transformer T1 increases by a value given by the formula. Due to the increased input voltage of the
  • n tr is the number of turns of the main transformer T1.
  • a ZVS transformer T zvs can reduce switching losses.
  • Transformer T zvs it takes a predetermined time until a primary voltage on the primary coil T1 A also appears on the secondary coil T1 B after this
  • Free-running state must transition into a state in which the output current is reflected at the primary coil T 1 A. It is desirable to increase the stored magnetic energy in order to enable a long free run in which the
  • the magnetic energy is broken down. If this magnetic energy were increased by providing a high inductance of T 1A , this would result in high switching losses (duty loss) lead. Using the ZVS transformer, the magnetic energy can be increased by providing a current without increasing the inductance of T 1A .
  • T 1A Stray inductance of T 1A and thus the switching losses (duty loss) can be reduced.
  • the storage of high magnetic energy is necessary in order to establish ZVS conditions for the transition of the switches A, B of the downstream branch 107, in particular if the switches A, B are implemented as MOSFETs.
  • the ZVS transformer T zvs is dimensioned in such a way that the magnetic energy that enables the ZVS transition of the trailing branch 107 is stored. Storing a higher magnetic energy essentially does not improve the switching behavior.
  • the ZVS transformer Since the ZVS transformer also has a leakage inductance, the ZVS transformer stores the magnetic energy in its leakage inductance. This magnetic energy is proportional to the peak current which flows through the ZVS transformer T zvs . This peak current in turn is proportional to that
  • Time interval of the freewheeling phase during which the switches SR1 and SR2 are switched on simultaneously is determined in the design of the circuit so that it can take up enough energy to bring about ZVS conditions, and is difficult to change thereafter.
  • the current required to create ZVS conditions is determined by the length of time controlled during which the switches SR1 and SR2 are switched on simultaneously during the freewheeling phase.
  • Freewheeling phases II and IV is required can be regarded as a duty loss, which can be quantified as follows:
  • DI is the current difference between the current through T1 A after the
  • DD is a time value that corresponds to a region along a time axis and f is the frequency of the PWM.
  • DD Is the amount of time it takes for the current to change. This time duration DD should be as short as possible in order to achieve good output voltage capability.
  • the time interval DD increases with increasing load at output 110, since the current difference DI increases. This increase in switching losses DD can only take place in a limited range, since from a certain value they are so severe that output 110 is no longer able to provide the required output voltage Vout, for example for charging a 12V battery.
  • the ZVS region ie the range of input voltages v in , in which ZVS is possible can be increased by the
  • the ZVS region i.e. the area of
  • Input voltages V in at which the DC-DC converter circuit 100 can still be operated efficiently, are increased by the current I T1A , which during the Free-running phase II flowing through T1 A is increased, while at the same time the leakage inductance L ik of the transformer T1 is kept low.
  • Dl is also increased, which increases switch-on losses, more magnetic energy can also be stored at the same time. If the current is increased, more magnetic energy can be stored, but power losses and / or line losses (RMS (Root Mean Square) losses) also increase. Soft switching or ZVS switching, however, reduces the line losses
  • the primary side of the DC-DC converter is configured as a phase-shifted full bridge (PSFB) with an additional small transformer T zvs to switch the zero-voltage switching (ZVS) of the primary-side switches A and B of the lagging branch 107 to support.
  • PSFB phase-shifted full bridge
  • ZVS zero-voltage switching
  • the stored magnetic energy can be increased by impressing a current, in particular the current for neutralizing parasitic charges on the switches A, B, C, D and in particular on the switches A, B of the lagging branch 107. This neutralization can take place very quickly, so that the DC-DC converter 100 can work with a high switching frequency f.
  • a soft switching or a ZVS switching can essentially always be implemented in a PSFB, that is to say regardless of whether the ZVS transformer T zvs is present or not.
  • the DC input voltage V in corresponds to the voltage of the HV battery.
  • the voltage V in can range from 240V to 470V or 400V to 800V for
  • Input voltage V in can depend on the state of charge of the HV battery.
  • Duty cycle ratio of the PWM used depends on the input voltage Vin present. However, other types of
  • T zvs if different voltage ranges are to be supplied, for example 240V to 470V or 400V to 800V.
  • the same voltages are present at the primary switches A, B, C, D as at points 105, 106.
  • the DC-DC converter is a control circuit is provided (not shown in Fig. 1), the duty, the duty ratio ( ratio) of the control signal of the switches A, B, C, D changed to
  • Vout 12V.
  • the pulse duty factor and / or the frequency of the switches A, B, C, D must be increased in order to ensure a stable and / or constant output voltage Vout.
  • the pulse duty factor is determined from the quotient of the duration of the energy supply phase I and the sum of the duration of the energy supply phase I and the duration of the
  • Frequency for the control signals for A, B, C, D, SR1, SR2 remains constant and is not varied.
  • the energy transmission and / or power transmission via the main transformer T1 depends on the primary voltage, only a small amount of power and / or energy could be transmitted via the main transformer T1 due to the reduced primary voltage and the power that can be provided with the voltage Vout would be reduced.
  • connection circuit between 105 and 106 there is a high in the connection circuit between 105 and 106
  • Inductance is desirable in order to provide high magnetic energy at a high input voltage v in for discharging the switches A, B of the lagging branch 107 and thereby to enable ZVS switching.
  • the inductance provided by the inductance of the primary coil T1 A was increased further and further by series connection of an additional inductance T3 B , the performance of the output voltage Vout or the output power would be reduced further and further, since the discharging of the switches A, B of the lagging branch 107 especially at high voltages v in either could not be done quickly enough or not completely. This means that the DC-DC converter could only be operated in very low voltage ranges. While the primary side of the main transformer T1 is essentially on the
  • Main transformer T1 a DC voltage of 14.5V or a voltage from the range of about 12 V to 15V, which is provided as output voltage V out, for example, a radio or other consumer of the vehicle electrical system.
  • Output power by increasing the voltage applied to the primary coil T1 A of the main transformer T1. Since the primary coil T1 A of the main transformer T 1 is connected in series with the secondary coil T3 B of the ZVS transformer, the performance of the output voltage (output voltage capability) increases. In order to compensate for this influence, the primary coil T3 A is provided, which is connected between the switching node 105 and the fixed potential 11. A voltage which is applied to the primary coil T3 A generates a voltage at the secondary coil T3 B. This voltage on the secondary coil T3 B increases the voltage on the primary coil T1 A and ensures good output voltage performance.
  • a single-stage DC-DC converter is a DC-DC converter that converts a first voltage level into a second voltage level only once without generating further intermediate voltage levels
  • One side or a connection of the primary coil T3 A of the additional transformer T zvs is connected to the first bridge connection 105 and to one side of the additional coil T3 B or the secondary coil T3 B of the additional transformer T zvs .
  • the other side or the other connection of the primary coil T3 A of the additional transformer T zvs is connected to a third bridge branch 109, which is formed as a series connection of two capacitors C1 and C2.
  • This other side of the primary coil T3 A of the additional transformer T zvs is connected between the first capacitor C1 and the second capacitor C2.
  • the third bridge branch 109 is connected to the first input connection 102 and connected to the second input connection 103 and is connected in parallel to the first 107 and second 108 bridge branch.
  • the third bridge arm 109 ensures that a connection of the coil T3 A is kept at a fixed or constant potential.
  • a change in the voltage of the primary coil T3 A of the ZVS transformer, which impresses a current into the secondary coil T3 B thus depends on a change in the potential of the bridge points 105 and 106. This also affects the by switching the synchronous
  • a first synchronous rectifier (Synchronous Rectifier, SR) SR1 and a second synchronous rectifier (Synchronous Rectifier, SR) SR2 is connected in parallel to the secondary coil T1 B of the main transformer T1. These are connected via a first output coil L1 and a second output coil L2 and an output capacitor C0 to the output 110 of the DC-DC converter 100, via which the output voltage V out is provided.
  • the synchronous rectifier SR1, SR2 is operated in such a way that the positive or negative half-wave which is induced in the secondary coil T1 B is passed on to the smoothing capacitor Co with the same polarity, so that an output DC voltage V out is generated.
  • FIG. 2 shows a block diagram of a DC-DC converter 200 with a bridge circuit 101 and two main transformers T1, T2 according to an example
  • the current on the secondary side of the main transformer 1 is divided into four coils L1, L2, L3, L4 and four synchronous rectifiers SR1, SR2, SR 1 ', SR2', which simplifies the efficiency of the circuit and the treatment of the current leaves.
  • the main transformer T1 from FIG. 1 is divided into the two main transformers T1, T2.
  • the primary coil T1 A of the first main transformer is coupled to the secondary coils T1 B and T1 C of the first main transformer.
  • Main transformer is with the secondary coils T2B and T2c of the first
  • the output circuits 112a, 112b essentially correspond to the output circuit 112 from FIG. 1. However, in each of them
  • Output circuits 112a, 112b a secondary side of the two transformers T1, T2 utilized.
  • the synchronous rectifiers SR1 and SR1 ' are operated in the same way and the synchronous rectifiers SR2, SR2' are operated in the same way.
  • FIG. 3 shows a block diagram of a DC-DC converter with a bridge circuit and a main transformer with center tap according to an exemplary embodiment
  • Embodiment of the present invention In this circuit variant, only one output coil L1 is provided.
  • the converter circuits shown in FIGS. 1-3 can be used both as a current doubler and as a center tap configuration on the secondary side.
  • the center tap 301 is arranged on the secondary side of the main transformer T1 ”and connected to the two sub-secondary coils T1 B “ and T1 C “and the coil L1.
  • the two sub-secondary coils T1 B “and T1 C " are also with the
  • Rectifiers SR1 "and SR2" connected. There is a ground connection between the rectifiers SR1 "and SR2", which is also connected to one of the output connections.
  • the capacitor C0 is connected in parallel to the output.
  • lagging leg A / B is included for a case in which there is no load at the output 110, that is to say for the no-load case or idling.
  • the synchronous rectifiers SR1 and SR2 are switched on simultaneously during the freewheeling phase II B of the low-side switches B, D in order to provide a short pulse across the secondary coil T1 B through the
  • the additional transformer T zvs is connected in series with the main transformer T1 and helps to impress a current into the coil T3 B of the additional transformer.
  • ZVS switching of high switch A 104a can be achieved. Because if there is no load at the output, the output current is 0A and the output load R load is undetermined.
  • the output voltage V out is regulated to a constant 14.5 V independently of the load, for example by changing the frequency and / or the duty cycle of the PWM switches A, B, C, D.
  • the energy supply phase III is followed by another free-running phase IV, namely the free-running phase of the high-side switches A 104a and C 104c.
  • a free-wheeling circuit is formed from switch A 104a, C 104c, additional coil T3 B and primary coil T1 A.
  • phase-shifted full-bridge topology with an additional inductance T3 B , which is connected in series with the transformer T 1
  • ZVS switching or soft switching can be achieved if the additional inductance T3 B is part of a transformer T zvs .
  • the additional transformer T zvs has a low coupling factor between the primary coil T3 A and the secondary coil T3 B - the low coupling is achieved, for example, by a magnetic core with a slot. Energy that can be used for ZVS can be temporarily stored in the additional transformer T zvs . Due to the low coupling of the ZVS
  • Transformer T zvs maintains a leakage inductance in T zvs , because the part of the magnetic flux that does not couple into the secondary coil becomes noticeable as leakage inductance.
  • This additional leakage inductance can be regarded as a further inductance, which is in series with T3 B , even if the leakage inductance is not a tangible component.
  • the size of the leakage inductance can also be influenced via the coupling factor.
  • the leakage inductance can also store magnetic energy, which can then be converted back into an electrical current flow in order to support ZVS by discharging the bridge point 105. If a configuration with only one additional coil T3 B without primary coil T3 A or another coil T3 A is used, i.e.
  • Transformer T zvs magnetic energy can be used.
  • the energy controlled by the current determined by the length of time
  • the ZVS transformer T zvs thus, by activating the synchronous rectifiers SR1, SR2 over a predeterminable period of time II B, contributes to increasing the primary current I T1A to such an extent as it does in the freewheeling phase II for the ZVS switching of the switches of the lagging branch 107 is required.
  • ZVS switching can be achieved in the primary switches A, B, C, D, regardless of the load at output 110
  • Primary current ITIA is increased instead of increasing the inductance of the secondary coil T3 B ZU, which would lead to a reduction in output power. Since the magnetic energy in the secondary coil is T3 B according to formula (3), the increase is
  • Each additional series connected inductor which as a real component or as
  • the output capability of the output 110 of the DC-DC converter 100 is reduced, for example in relation to a constant output voltage v out to be provided as a function of a wide range of input voltages V in .
  • This reduction in output performance can have a negative effect if the output voltage V out of converter 100 is to be regulated to a constant output voltage
  • the input voltage varies within a wide range, for example in the range from 240 V to 470V, depending on the state of charge of an HV battery.
  • the inductance connected in series may be necessary to enable smooth switching under ZVS conditions.
  • a series inductance would degrade the output performance of converter 100 because, for example, it is no longer possible to generate a constant output voltage of 14.5V when the input voltage Vin is at a lower range limit, e.g. at 240V in a range of 240V to 470 V, and at the same time ZVS conditions should be met. Because it would actually be desirable to get by without the T3 B series inductor. But then no ZVS would be possible and the efficiency of the converter would be low.

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  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne un circuit de pont (101) présentant : un premier (A) et un deuxième (C) commutateur High Side ; un premier (B) et un deuxième (D) commutateur Low Side ; un transformateur (T1) comprenant une bobine primaire (T1A) et une bobine secondaire (T1B) ; une bobine (T3B) ; un dispositif d'applique de courant (T3A) ; le premier commutateur High Side (A) et le premier commutateur Low Side (B) étant connectés dans une connexion en série à un premier raccordement de pont (105), pour former une première branche de pont (107) ; le deuxième commutateur High Side (C) et le deuxième commutateur Low Side (D) étant connectés dans une connexion en série à un deuxième raccordement de pont (106) pour former une deuxième branche de pont (108) ; les première (107) et deuxième (108) branches de pont étant connectées dans ne connexion en parallèle à un premier (102) et à un deuxième (103) raccordement d'entrée ; la bobine secondaire (T1B) présentant un premier (110a) et un deuxième (110b) raccordement de sortie ; la bobine primaire (T1A) et la bobine (T3B) étant connectées dans une connexion en série, pour connecter le premier raccordement de pont au deuxième raccordement de pont ; et le dispositif d'applique de courant (T3A) étant configuré pour appliquer dans la bobine (T3B) un courant prédéterminé à un moment prédéterminé.
EP20701433.3A 2019-01-24 2020-01-20 Convertisseur continu-continu comprenant un circuit de pont pour la mise hors tension ainsi que procédé correspondant Pending EP3915186A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102019101748.3A DE102019101748A1 (de) 2019-01-24 2019-01-24 Brückenschaltkreis und Verfahren zum Betreiben eines Brückenschaltkreises
PCT/EP2020/051222 WO2020152076A1 (fr) 2019-01-24 2020-01-20 Convertisseur continu-continu comprenant un circuit de pont pour la mise hors tension ainsi que procédé correspondant

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EP3915186A1 true EP3915186A1 (fr) 2021-12-01

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EP20701433.3A Pending EP3915186A1 (fr) 2019-01-24 2020-01-20 Convertisseur continu-continu comprenant un circuit de pont pour la mise hors tension ainsi que procédé correspondant

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US (1) US12021457B2 (fr)
EP (1) EP3915186A1 (fr)
DE (1) DE102019101748A1 (fr)
WO (1) WO2020152076A1 (fr)

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CN114257219B (zh) * 2021-12-24 2022-08-16 西南科技大学 一种可编程超窄功率脉冲锐化电路及方法

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Publication number Priority date Publication date Assignee Title
CA2249755C (fr) * 1998-10-02 2006-12-12 Praveen K. Jain Convertisseurs c.c/c.c. a double alternance
US6310785B1 (en) * 1999-09-01 2001-10-30 Regents Of The University Of Minnesota Zero voltage switching DC-DC converter
JP5530212B2 (ja) * 2010-02-10 2014-06-25 株式会社日立製作所 電源装置、ハードディスク装置、及び電源装置のスイッチング方法
AT515242B1 (de) 2013-12-20 2020-04-15 Fronius Int Gmbh Verfahren zum Steuern eines Vollbrücken DC/DC-Wandlers
JP6097270B2 (ja) * 2014-12-10 2017-03-15 株式会社豊田中央研究所 電力変換回路システム
DE102018121268A1 (de) * 2018-08-31 2020-03-05 Brusa Elektronik Ag Verfahren und Vorrichtung zur Spannungsanpassung des Glättungskondensators eines DC-DC-Wandlers vor Konnektierung einer Hochvoltbatterie
EP3700074B1 (fr) * 2019-02-19 2021-10-06 BRUSA HyPower AG Convertisseur cc-cc

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US20230136912A1 (en) 2023-05-04
WO2020152076A1 (fr) 2020-07-30
US12021457B2 (en) 2024-06-25
DE102019101748A1 (de) 2020-07-30

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