EP2494652A1 - Combineur de signaux haute fréquence - Google Patents

Combineur de signaux haute fréquence

Info

Publication number
EP2494652A1
EP2494652A1 EP10762876A EP10762876A EP2494652A1 EP 2494652 A1 EP2494652 A1 EP 2494652A1 EP 10762876 A EP10762876 A EP 10762876A EP 10762876 A EP10762876 A EP 10762876A EP 2494652 A1 EP2494652 A1 EP 2494652A1
Authority
EP
European Patent Office
Prior art keywords
frequency signal
coaxial line
signal combiner
coaxial
line
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP10762876A
Other languages
German (de)
English (en)
Other versions
EP2494652B1 (fr
Inventor
Michael Morgenstern
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Rohde and Schwarz GmbH and Co KG
Original Assignee
Rohde and Schwarz GmbH and Co KG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Rohde and Schwarz GmbH and Co KG filed Critical Rohde and Schwarz GmbH and Co KG
Publication of EP2494652A1 publication Critical patent/EP2494652A1/fr
Application granted granted Critical
Publication of EP2494652B1 publication Critical patent/EP2494652B1/fr
Not-in-force legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/08—Coupling devices of the waveguide type for linking dissimilar lines or devices
    • H01P5/10—Coupling devices of the waveguide type for linking dissimilar lines or devices for coupling balanced lines or devices with unbalanced lines or devices
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P5/00—Coupling devices of the waveguide type
    • H01P5/12—Coupling devices having more than two ports

Definitions

  • High frequency signal combiner The invention relates to a high frequency signal combiner.
  • High frequency amplifiers are based on semiconductor
  • High frequency amplifiers is supplied simultaneously, whose outputs with a high-frequency combiner for
  • High frequency signal combiner unbalanced applied.
  • This asymmetry in the driving of the high-frequency signal combiner causes interfering high-frequency signals on the outside of the coaxial lines of the high-frequency signal combiner, so-called sheath waves, which are attenuated by the ferrite core-reinforced inductance of the coaxial cables.
  • sheath waves which are attenuated by the ferrite core-reinforced inductance of the coaxial cables. Due to the spatial extent of the coaxial lines and the ferrite core, the arrangement of the high-frequency signal combiner disadvantageously has a high construction volume.
  • the object of the invention is therefore to provide a high-frequency signal combiner, the lower
  • Construction volume has.
  • the invention is characterized by a high frequency signal combiner having the features of patent claim 1 solved.
  • a core of an axially wound strip which consists of a first layer of a magnetizable material and of a second layer of an insulating layer
  • Material existing first layer has a significantly higher thickness, namely preferably 5 to 50 microns, more preferably 16 to 20 microns, than those of e.g.
  • Magnesium oxide insulating material the thickness of which is preferably 0.1 to 1 micron, e.g. 0.5 microns.
  • a part of the lines of the high-frequency signal combiner are formed as strip lines. These correspond to those coaxial lines of the high-frequency signal combiner according to US 6,246,299 Bl, each of which from one end to the other end of the coaxial line on the inside of the shield
  • High-frequency signal combiner for example, better S-parameters, the characteristic impedance of the
  • Coaxial lines which is preferably 35 ⁇ , for
  • Characteristic impedance of the strip lines which is preferably 15 ⁇ , a different value.
  • the physical length of the coaxial lines which is preferably 187 mm, also has a different value from the physical length of the strip lines, which is preferably 92.3 mm.
  • Fig. 1A is a circuit diagram of an inventive
  • Fig. 1B is a circuit diagram of an inventive
  • Fig. 2 is a three-dimensional representation of
  • High-frequency signal with the signal level U Ei for example, the output signal of a first high-frequency amplifier, and at the second input terminal, hereinafter also second input port 2, a second high-frequency signal with the signal level U E2 , for example, the output signal of a second high-frequency amplifier, fed.
  • the first high-frequency signal U El and the second high-frequency signal U E2 ideally have the same phase and the same amplitude.
  • the first input port 1 is connected at the input end of a first coaxial line 4 to the inner conductor 3 of a first coaxial line 4.
  • the second input port 2 is at the input end of a second
  • Coaxial line 6 connected.
  • High frequency line 4 and 6 are each in
  • the inner conductor 3 of the first coaxial line 4 and the inner conductor 5 of the second coaxial line 6 are each brought together at the output end of the first coaxial line 4 and the second coaxial line 6 and to an output terminal, hereinafter also output port 8, guided, at which the third high-frequency signal is applied its signal amplitude U A of the signal amplitude U Ei and U E2 of the ideal in terms of amplitude and phase
  • One of the first strip line 9 associated ground line 10 is connected to the ground terminal on the
  • the outer conductor of the second coaxial line 6 is at the output side end of the second coaxial line 6 with the output side end of a second
  • a belonging to the second stripline 11 ground line 12 is
  • Coaxial line 4 and 6 is between the outer conductor of the first and second coaxial line 4 and 6 a
  • Signal amplitude or signal power asymmetric first and second high-frequency signal and in parallel a capacitor 19 for the compensation of residual reactances
  • Input compensation resistor 14 of 50 ⁇ to compensate for a signal amplitude in terms of
  • the characteristic impedance of the first and second coaxial line 4 and 6 in the exemplary embodiment is in each case 35 ⁇ , whereas the characteristic impedance of the first and second strip line 9 and 11 in the exemplary embodiment is 15 ⁇ in each case. Due to the electrical connection of the
  • Outer conductor of the first and second coaxial line 4 and 6 with the first and second strip line 9 and 11 are the first coaxial line 4 and the first
  • Stripline 9 and 11 Each of these two
  • Voltage divider is shown schematically in dashed lines in Fig. 1A and 1B by the series-connected
  • Resistors 15i and 15 2 and 15 3 and 15 4 each with 35 ⁇ and each 15 ⁇ indicated.
  • Coaxial line 4 and 6 respectively a voltage drop of 0, 7 - U E1 and 0, 7 - U E2 between the inner and the outer conductor of the first and second coaxial line 4 and 6 and input and output side of the first and second
  • Strip line 9 and 11 each have a voltage drop of 0.3 - U or 0.3 - U E2 between the actual first and second strip line 9 and 11 and the associated ground line 10 and 12 respectively.
  • the input impedance of the high-frequency signal combiner is at the two input ports 1 and 2 due to the series connection of first coaxial line 4 and first stripline 9 and second coaxial line 6 and second stripline 11 at the preferred values for the characteristic impedance of the first and second coaxial and stripline in Embodiment 50 ⁇ each.
  • the output impedance of the high frequency signal combiner at the output port 8 is due to the parallel connection of from the first coaxial line 4 and the first
  • Stripline 9 represents first series circuit of RF lines and the second of the second coaxial line 6 and the second stripline 11 second best
  • Output port 8 of the high-frequency signal combiner is obtained according to equation (1) from the sum of
  • Strip line 9 and the associated ground line 10 (corresponding to voltage drop at the fictitious resistor 15 4 ), the signal level U Ei or U E2 of the first or second in both cases in a case of identical amplitude and phase first and second high frequency signal
  • High frequency signal at the first and second input port 1 and 2 corresponds.
  • the current I A at the output port 8 of the high-frequency signal combiner is obtained according to equation (2) as addition of the current /, through the inner conductor of the first coaxial line 4 and of the current I 2 through the inner conductor of the second coaxial line 6: (2)
  • Coaxial line 6 flowing current I 2 is closed via the second strip conductor 11.
  • the power P A at the output port 8 results from equations (1) and (2) according to equation (3) from the addition of the powers P and P E2 at the first and second input ports 1 and 2.
  • the voltage drop between the inner and outer conductors of the second coaxial line 6 input and output side of the second coaxial line 6 is 0V. Consequently, the voltage drop from the second stripline 11 to the associated ground line 12 is input and
  • the output current I A at the output port 8 of the high-frequency signal combiner corresponds according to equation (5) the only current flowing /, through the inner conductor of the first coaxial line 4:
  • Coaxial line 6 in the amount of OV to an output-side potential of the outer conductor of the second coaxial line 6 to ground also in the amount of 0.5 -U E. Since that
  • Input-side potential of the outer conductor of the second coaxial line 6 due to the non-driven second input port 2 is at ground potential, is a
  • the input-side potential of the outer conductor of the first coaxial line 4 has due to the activation of the first input port 1 with the first high-frequency signal whose signal level has the value U, and due to the
  • Coaxial line 4 and 6 has a value in the amount of 0.5-U Ei and the voltage drop between the inner conductor and outer conductor of the first coaxial line 4 0.7-U E ⁇ , the output-side potential of the outer conductor of the first coaxial line 4 has a value in height from -0,2 -U E] to.
  • there is a voltage drop across the outer conductor between the input and the output side end of the first coaxial line 4 in the amount of 0.5-U El which is a current I Manle n on the outside of the shield of the first coaxial line 4 as a so-called mantle wave
  • Coaxial line 1 and 2 are undesirable, they must be compensated or at least damped. Since these are high-frequency signals, they are already damped to a certain extent by the inductance pads of the first and second coaxial lines 4 and 6 alone.
  • Inductance of the first and second coaxial line and thus their damping characteristic is increased by enclosing the first and second coaxial line 4 and 6 with an annular core of a magnetizable material.
  • An additional increase in the inductance of the first and second coaxial lines 4 and 6 can be achieved by an advantageous arrangement of the first and second
  • Coaxial line 4 and 6 are achieved, as shown below with reference to Figures 4A and 4B.
  • Inductances of the first and second coaxial lines 4 and 6 would thus form a series connection between the first and second input ports 1 and 2. If the first and second coaxial lines 4 and 6 were to be in the identical orientation through the recess or bore 20 of the toroidal core 7 - i. Input side end of the first and second coaxial line 4 and 6 on one side of the bore 20 and the output side end of the first and second coaxial line 4 and 6 on the other side of the bore 20 -, we obtain the in Fig. 4A
  • the induced in the other inductance mutual inductance M has the same sign in the inductance L, and
  • Equation (9) is modeled by a plus sign before the term IM in the mathematical relationship for the total inductance L.
  • Z, Z, + Z-, + 2 «4Z (7)
  • Total inductance L for the coupler arrangement of first and second coaxial line 4 and 6 is determined by the
  • a toroidal core 7 which, according to FIG. 3, is made of an axially wound band which consists of a first layer 16 of magnetizable iron and of a second layer 17 of a
  • insulating layer for example of an oxide or nitride, preferably, consists of an insulating magnesium oxide.
  • Toroidal core reduces the eddy current cutoff frequency f
  • Material density of the magnetizable iron in the ring core results in a threefold higher saturation inductance B s and a particular at higher frequencies significantly higher permeability ⁇ ⁇ ( ⁇ «1 00000 compared to a R « 5000 in ferrite cores produced by conventional sintering technology).
  • Higher saturation inductance B s and higher permeability ⁇ ⁇ allow higher self-inductance Z, and and higher
  • the physical length of the first and second stripline 9 and 11 in the amount of 70mm to 120mm, preferably 92.3 mm, is thus shorter than the physical length of the first and second coaxial line 4 and 6 in height from 150mm to 200mm, preferably 187mm.
  • the invention is not limited to the one shown

Landscapes

  • Amplifiers (AREA)
  • Control Of Motors That Do Not Use Commutators (AREA)
  • Coils Or Transformers For Communication (AREA)
  • Cable Transmission Systems, Equalization Of Radio And Reduction Of Echo (AREA)

Abstract

L'invention concerne un combineur de signaux haute fréquence qui se compose d'un premier raccord d'entrée (1) pour le raccord d'un premier signal haute fréquence, d'un deuxième raccord d'entrée (2) pour le raccord d'un deuxième signal haute fréquence, et d'un raccord de sortie (8) pour émettre le troisième signal haute fréquence combiné à partir du premier et du deuxième signal haute fréquence. Une première conduite coaxiale (4) s'étend entre le premier raccord d'entrée (1) et le raccord de sortie (8). Une deuxième conduite coaxiale (6) s'étend entre le deuxième raccord d'entrée (2) et le raccord de sortie (8). En outre, un noyau (7) de forme annulaire présente un évidement (20) à travers lequel sont guidées la première et la deuxième conduite coaxiale (4, 6) à chaque fois dans une direction différente. Le noyau (7) de forme annulaire est fabriqué en une bande enroulée axialement, qui se compose d'une première couche (16) en matériau aimantable, et d'une deuxième couche (17) en matériau isolant.
EP10762876.0A 2009-10-29 2010-10-07 Combineur de signaux haute fréquence Not-in-force EP2494652B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE102009051229A DE102009051229A1 (de) 2009-10-29 2009-10-29 Hochfrequenz-Signalkombinierer
PCT/EP2010/006137 WO2011050898A1 (fr) 2009-10-29 2010-10-07 Combineur de signaux haute fréquence

Publications (2)

Publication Number Publication Date
EP2494652A1 true EP2494652A1 (fr) 2012-09-05
EP2494652B1 EP2494652B1 (fr) 2018-04-04

Family

ID=43502628

Family Applications (1)

Application Number Title Priority Date Filing Date
EP10762876.0A Not-in-force EP2494652B1 (fr) 2009-10-29 2010-10-07 Combineur de signaux haute fréquence

Country Status (4)

Country Link
US (1) US8912864B2 (fr)
EP (1) EP2494652B1 (fr)
DE (1) DE102009051229A1 (fr)
WO (1) WO2011050898A1 (fr)

Families Citing this family (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US8791772B2 (en) * 2010-09-07 2014-07-29 Mks Instruments, Inc. LCL high power combiner
US9073850B2 (en) 2011-11-24 2015-07-07 Jnc Corporation Polymerizable compound
JP5555725B2 (ja) 2012-01-13 2014-07-23 本田技研工業株式会社 電気負荷制御装置
JP2014195189A (ja) * 2013-03-29 2014-10-09 Daihen Corp 電力合成器および電力分配器
DE102015214494A1 (de) * 2015-07-30 2017-02-02 Rohde & Schwarz Gmbh & Co. Kg Hochfrequenz-Signalkombinierer

Family Cites Families (8)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
FR2698479B1 (fr) * 1992-11-25 1994-12-23 Commissariat Energie Atomique Composite hyperfréquence anisotrope.
US6741814B1 (en) * 1999-04-01 2004-05-25 Koninklijke Philips Electronics N.V. Balun for coaxial cable transmission
US7077919B2 (en) * 1999-05-20 2006-07-18 Magnetic Metals Corporation Magnetic core insulation
US6246299B1 (en) 1999-07-20 2001-06-12 Werlatone, Inc. High power broadband combiner having ferrite cores
WO2002095775A1 (fr) * 2001-05-21 2002-11-28 Milli Sensor Systems & Actuators, Inc. Inducteurs et transformateurs miniatures plans et transformateurs miniatures pour instruments micro-usines
JP2004103742A (ja) * 2002-09-06 2004-04-02 Mitsubishi Heavy Ind Ltd 電気機器用鉄心及び電気機器用鉄心製造方法
DE10352784A1 (de) * 2003-11-12 2005-06-16 Rohde & Schwarz Gmbh & Co. Kg Richtkoppler in Koaxialleitungstechnik
CN101465457B (zh) * 2009-01-15 2012-11-21 电子科技大学 一种高功率宽带四路功率分配、合成器

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO2011050898A1 *

Also Published As

Publication number Publication date
US20120212302A1 (en) 2012-08-23
US8912864B2 (en) 2014-12-16
EP2494652B1 (fr) 2018-04-04
DE102009051229A1 (de) 2011-05-12
WO2011050898A1 (fr) 2011-05-05

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