EP2345308B1 - Circuit de fonctionnement destiné à des led - Google Patents

Circuit de fonctionnement destiné à des led Download PDF

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Publication number
EP2345308B1
EP2345308B1 EP09752099A EP09752099A EP2345308B1 EP 2345308 B1 EP2345308 B1 EP 2345308B1 EP 09752099 A EP09752099 A EP 09752099A EP 09752099 A EP09752099 A EP 09752099A EP 2345308 B1 EP2345308 B1 EP 2345308B1
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EP
European Patent Office
Prior art keywords
switch
coil
led
voltage
current
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EP09752099A
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German (de)
English (en)
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EP2345308A1 (fr
Inventor
Michael Zimmermann
Eduardo Pereira
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Tridonic AG
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Tridonic AG
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]
    • H05B45/375—Switched mode power supply [SMPS] using buck topology
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
    • H05B45/30—Driver circuits
    • H05B45/37—Converter circuits
    • H05B45/3725—Switched mode power supply [SMPS]

Definitions

  • the invention relates to an operating circuit with light emitting diodes according to the preamble of patent claim 1 and a method for operating light emitting diodes according to the preamble of patent claim 13.
  • LEDs have become an attractive alternative to conventional light sources such as incandescent or gas discharge lamps.
  • LED light-emitting diode
  • This term is intended below to include both light emitting diodes of inorganic materials and light emitting diodes of organic materials. It is known that the light emission of LEDs correlates with the current flow through the LEDs.
  • switching regulators for example step-down or buck converters, are preferably used to drive an arrangement of one or more LEDs.
  • a switching regulator is for example from the DE 10 2006 034 371 A1 known.
  • a control unit controls a high-frequency clocked switch (for example, a power transistor). When the switch is turned on, current flows through the LED assembly and a coil, which is charged by it. The cached energy of the coil discharges in the off state of the switch via the LEDs (freewheeling phase).
  • the current through the LED arrangement shows a zigzag time course: when the switch is on, the LED current shows a rising edge, with the switch off, there is a falling edge.
  • the time average of the LED current represents the RMS current through the LED array and is a measure of the brightness of the LEDs. By appropriate timing of the circuit breaker, the average, effective current can be controlled.
  • the function of the operating device is now to set a desired average current flow through the LEDs and to minimize the temporal fluctuation of the current due to the high frequency switching on and off of the switch (typically in the range above 10 kHz).
  • a large fluctuation range of the current has a disadvantageous effect particularly with LEDs, since the spectrum of the emitted light can change as the current amplitude changes.
  • the LEDs are supplied by the operating device low-frequency (typically with a frequency in the range of 100-1000 Hz) pulse packets with (on average over time) constant current amplitude.
  • the current within a pulse packet is superimposed on the above-mentioned high-frequency ripple.
  • the brightness of the LEDs can now be controlled by the frequency of the pulse packets; For example, the LEDs can be dimmed by increasing the time interval between the pulse packets.
  • a practical requirement of the operating device is that it can be used as flexibly and versatile as possible, for example, regardless of how many LEDs are actually connected as a load and should be operated.
  • the load may also change during operation if, for example, an LED fails.
  • the LEDs are operated in a so-called 'continuous conduction mode' or non-looping operation. This procedure is based on FIG. 1a and FIG. 1b explained in more detail (prior art).
  • a buck converter for the operation of at least one LED (or a plurality of LEDs connected in series), which has a first switch S1, is shown as the basic circuit.
  • the operating circuit is supplied with a DC voltage or a rectified AC voltage U0.
  • these times may be selected so that the first switch S1 is turned on when the current falls below a certain minimum reference value and the switch is turned off when the current exceeds a maximum reference value.
  • this method has several disadvantages: First, to achieve the lowest possible ripple, a rapid sequence of switching on and Ausschaltvor réellen is necessary. The slope (positive or negative edge) of the current is namely not controllable by the operating device and considered to be given, since it is determined inter alia by the inductance of the coil L1 and the power consumption of the LEDS.
  • the operating circuit is supplied with a DC voltage or rectified AC voltage for at least one LED.
  • a supply voltage for at least one LED is provided by means of a coil and a clocked by a control / control unit first switch, with the first switch in the coil, an energy is temporarily stored, which is switched off with the first switch via a diode and the at least one LED discharges.
  • the operating circuit has a capacitor arranged in parallel with the at least one LED, which maintains the current through the LED during the demagnetization phase of the coil L1, so that the current through the LEDs is smoothed.
  • control / regulating unit selects the switch-off time of the first switch so that the lowest possible switching losses occur and still the current flow through the at least one LED has the smallest possible ripple.
  • the operating circuit has a first sensor unit, which generates a first sensor signal dependent on the current flow through the first switch, and a second sensor unit, which detects reaching the demagnetization of the coil and generates a sensor signal.
  • the sensor signals are supplied to the control unit and processed.
  • control unit uses a combination of both signals to determine the on and / or off timing of the first switch.
  • the control unit turns off the first switch when the current through the first switch exceeds a maximum reference value, and turns on again at the time when the coil is demagnetized and the freewheeling diode (D1) blocks.
  • the first sensor unit is a measuring resistor (shunt).
  • the second sensor unit is an inductively coupled to the coil secondary winding or a Hall sensor.
  • the second sensor unit detects the achievement of the demagnetization of the coil by monitoring the voltage above the first switch by means of a (ohmic) voltage divider.
  • FIG. 1a and FIG. 1b show the state of the art.
  • FIG. 2a illustrated circuitry is used to operate at least one (or more in series and / or parallel connected) LED.
  • two LEDs are connected in series, it may of course be only one or more LEDs.
  • the LED or the serially and / or parallel-connected LEDs are also referred to below as the LED track.
  • An advantage of the present invention is that the operating circuit adapts very flexibly to the type and number of serially connected LEDs.
  • the circuit is supplied with a DC voltage U0, which of course can also be a rectified AC voltage.
  • the LEDs are connected in series with a coil L1 and a first switch S1.
  • the circuit arrangement has a diode D1 (the diode D1 is connected in parallel with the LEDs and the coil L1) and a capacitor C1 connected in parallel with the LEDs.
  • the switched-on state of the first switch S1 current flows through the LEDs and through the coil L1, which is thereby magnetized.
  • the switched-off state of the first switch S1 the energy stored in the magnetic field of the coil discharges in the form of a current via the diode D1 and the LEDs.
  • the capacitor C1 is charged.
  • the capacitor C1 discharges and contributes to the flow of current through the LED track. With suitable dimensioning of the capacitor C1, this leads to a smoothing of the current through the LEDs.
  • a field effect transistor or bipolar transistor is preferably used as a first switch S1.
  • the first switch S1 is switched to high-frequency, typically in a frequency range of about 10 kHz.
  • An advantage of the invention is that the first switch S1 is protected in operation, as it is preferably switched on, as explained later, when the power applied to it is almost zero.
  • a high-quality component with a very short switching duration must be used for the first switch S1 in order to keep the switching losses within a tolerable range.
  • An advantage of the circuit according to the invention is that for the first switch S1 and the diode D1 quite a comparatively cheaper component can be used with a comparatively slightly longer switching time or longer Aus Hurmzeit.
  • a control and / or control unit SR is provided, which determines the timing of the first switch S1 to control the LED power.
  • the control / regulating unit SR uses as input variables signals from a first sensor unit SE1 and / or signals from a second sensor unit SE2 to determine the exact switch-on and output time of the first switch S1.
  • the first sensor unit SE1 is arranged in series with the first switch S1 and detects the current flow through the first switch S1. This serves to monitor the flow of current through the first switch S1. If the current flow through the first switch S1 exceeds a certain maximum reference value, the first switch S1 is switched off.
  • the first sensor unit SE1 can be, for example, a measuring resistor (shunt or current measuring resistor).
  • the voltage drop at the measuring resistor can now be tapped off and, for example, compared with a reference value by means of a comparator.
  • the first switch S1 is switched off.
  • the second sensor unit SE2 is arranged within the current branch, which is traversed by the current during the freewheeling phase, preferably in the vicinity or on the coil L1. With the aid of the second sensor unit SE2, the control unit / control unit SR can set a suitable time for the switch-on time of the first switch S1.
  • the first switch S1 is preferably switched on when the current through the coil L1 is for the first time zero or at least very low, that is preferably in the time range, when the diode D1 blocks at the end of the freewheeling phase.
  • the lowest possible current is applied to the switch S1 at the switch-on time of the first switch S1.
  • the current through the LEDs shows only slight ripple and does not vary greatly. This is due to the smoothing effect of the capacitor C1 connected in parallel with the LEDs. During the phase of a low coil current, the capacitor C1 takes over the supply of the LED.
  • the individual current curves and the optimal switch-on time of the first switch S1 are to be determined on the basis of the diagram in FIG. 2b be explained in more detail.
  • Analogous to Diagram in FIG. 1b is the time course of the current i_L shown over two pulse packets.
  • the magnified representation shows the course of the current within a PWM pulse packet:
  • the time profile of the current i_L through the coil L1, the time profile of the current i_LED through the LEDs and the time profile of the state of the first switch S1 are plotted (in state 0, the The first switch S1 is turned off, the switch is closed in the state 1, and the signals for the state of the switch S1 correspond to the drive signal (ie at the gate) of the switch S1).
  • the first switch S1 is closed and a current begins to flow through the LED and the coil L1.
  • the current i_L shows an increase according to an exponential function, wherein a quasi-linear increase of the current i_L can be seen in the region of interest here.
  • i_LED differs from i_L in that part of the current i_L contributes to the charge of the capacitor C1.
  • the opening of the first switch S1 at time t_1 has the consequence that the energy stored in the magnetic field of the coil is discharged via the diode D1 and the LEDs or the capacitor C1.
  • the current i_L continues to flow in the same direction, but decreases continuously and can even reach a negative value.
  • a negative current ie a reverse current flow
  • the current i_LED decreases only weakly and is maintained because the capacitor C1 has a smoothing effect.
  • the diode blocks.
  • the current i_L decreases (but is still negative) and goes to zero.
  • parasitic capacitances at the diode D1 and other parasitic capacitances in the rest of the circuit are reloaded.
  • the voltages at the node Ux above the first switch S1 and at the coil L1 change very rapidly in this period.
  • the voltage at the node Ux drops to a low value (due to the diode D1 being disabled).
  • An advantageous switch-on time t_3 for the first switch S1 is now given when the current i_L reaches the zero crossing, or at least the vicinity of the zero crossing. At this time, the coil L1 is not or hardly magnetized. The first switch S1 can be turned on at this time with very low losses, since hardly any current flows through the coil L1. A reconnection is also already possible at the time t_2 or shortly before, because the current through the coil L1 is very low in this time range.
  • a second sensor unit SE2 For detecting the advantageous switch-on time for the first switch S1, a second sensor unit SE2 is now used.
  • the current i_L can be detected by the coil L1.
  • the current i_L through the coil L1 can be detected, for example, by means of a Hall sensor. Additionally or alternatively, therefore, other / other variables can be used which are suitable for detecting an advantageous switch-on time.
  • the magnetization state of the coil L1 can be detected.
  • the second sensor unit SE2 may be, for example, a secondary winding L2 on the coil L1, which taps the voltage across the coil L1.
  • the monitoring of the temporal voltage profile at the coil L1 (in particular the 'break-in' shortly after the diode D1 has been blocked after the instant t_2) makes it possible to say something about the advantageous switch-on time of the first switch S1.
  • a comparator would suffice, which can detect the achievement of demagnetization (and thus the zero crossing) on the basis of exceeding or falling below a threshold value.
  • the voltage at the node Ux above the first switch S1 can be monitored.
  • the voltage at node Ux drops significantly from a high value to a low value when the diode is turned off.
  • the signal for restarting the first switch S1 can therefore be triggered below the voltage Ux below a certain threshold value.
  • the control unit SR turns on the first switch S1 again at the time when the coil L1 is demagnetized and / or the diode D1 is off.
  • the second sensor unit SE2 can consist of a inductively coupled to the coil L1 secondary winding L2 or from a voltage divider (R1, R2) at the node Ux.
  • the control / regulating unit SR uses the information from the first sensor unit SE1 and / or the second sensor unit SE2 to determine the switch-on and switch-on time of the first switch S1
  • the regulation of the (time-averaged) LED power by SR can take place, for example, in the form of PWM signals ,
  • the frequency of the PWM signal is typically of the order of 100-1000 Hz.
  • FIG. 3 and FIG. 4 show specific embodiments of the invention.
  • FIG. 3 is a special embodiment of the above-described switching arrangement (a buck converter).
  • the advantageous switch-off time is detected by detecting the voltage at the node Ux above the first switch S1. This is done by the ohmic voltage divider R1 and R2.
  • the node Ux is located between the coil L1, the diode D1 and the switch S1.
  • a voltage divider for example, a capacitive voltage divider or combined voltage divider, which is composed of resistance and capacity, possible.
  • the measuring resistor (shunt) RS is used for current detection by the first switch S1.
  • the monitoring of the temporal voltage profile at the node Ux (in particular of the 'break-in' shortly after the diode D1 is blocked near the instant t_2) makes it possible to say something about the advantageous switch-on time of the first switch S1.
  • the voltage at the node Ux above the first switch S1 can be monitored.
  • the voltage at node Ux drops significantly from a high value to a low value when the diode is turned off.
  • the signal for restarting the first switch S1 can therefore be triggered below the voltage Ux below a certain threshold value.
  • a second switch S2 is arranged parallel to the LEDs and the capacitor C1.
  • the second switch S2 is selectively / independently controllable and may for example be a transistor (MOSFET or bipolar transistor). If the second switch S2 is closed, the discharge process of the capacitor C1 is accelerated. Due to the accelerated discharge of the capacitor C1 is achieved that the current flow through the LED goes to zero as quickly as possible. This is desirable, for example, at the end of a PWM packet, where the current flow through the LED should drop as quickly as possible, ie the falling edge of the current profile should be as steep as possible (for reasons of color constancy).
  • the second switch S2 can be activated and driven at a low dimming level, where the PWM packets are very short and it is important that the current through the LED rapidly approaches zero at the end of a pulse packet.
  • a low dimming level can be achieved by suitable activation of the second switch S2.
  • this second switch S2 bridges the LEDs when switched on. This is required, for example, when the LEDs are to be turned off, i. should not emit light, but the supply voltage U0 is still present. Without bridging by the second switch S2, a (smaller) current would flow across the LEDs and resistors R1 and R2, and the LEDs would (slightly) light up.
  • FIG. 4 shows a modification of the circuit in FIG FIG. 3 in that the voltage monitoring takes place at the coil L1.
  • the voltage at the coil S1 can be detected, for example, by means of a secondary winding L2, which is coupled to the coil S1 (or an additional coil L2, which inductively couples to the coil L1).
  • a secondary winding L2 is now used.
  • the monitoring of the temporal voltage profile at the coil L1 (in particular the 'break-in' in the vicinity of the blocking of the diode D1 after the time t_2) makes it possible to say something about the advantageous switch-on time of the first switch S1. As already mentioned, this monitoring can also take place on the basis of a secondary winding L2.
  • the determination of the time point of the zero crossing or the demagnetization can also take place by means of a threshold value monitoring (in the case of monitoring by means of a secondary winding L2, the polarity of the voltage depends on the winding sense of the secondary winding L2) Coil L1 off).
  • FIG. 5 shows a modification of the circuit of FIG. 2a in that the arrangement of the choke L1, the diode D1 and the orientation of the LED track is modified (forms a flyback converter or buck-boost converter).
  • FIG. 6 A development of the invention is in Fig. 6 shown.
  • the detection of the achievement of the demagnetization of the coil L1 by monitoring the voltage across the winding L2 can be performed by a standard available control circuit IC.
  • This control circuit IC (integrated circuit) corresponds to the control unit SR according to FIG Fig. 2 to 5 , Has an input for detecting the achievement of the demagnetization of a coil by monitoring the voltage applied to a coil on the secondary winding.
  • the control circuit IC has an output for driving a switch and other monitoring inputs.
  • a first of these monitoring inputs can be used for specifying a reference value, such as a reference voltage.
  • a second monitoring input can be used for monitoring the achievement of a maximum voltage or even using a voltage measurement on a resistor for monitoring the achievement of a maximum current.
  • a third monitoring input can be used for the monitoring of another voltage or also for the activation and deactivation of the control circuit IC or the control of the control circuit IC controlled switch.
  • the control circuit IC monitors the current through the first switch S1 during the switch-on phase of the first switch S1 via the measuring resistor (shunt) Rs and the input 4 on the control circuit IC. As soon as the voltage which is tapped across the measuring resistor (shunt) Rs reaches a certain maximum value, the first switch S1 is opened.
  • the specification of the voltage required to open the first switch S1 amount of voltage can be adjusted by specifying a reference value (ie, a reference voltage) at the input 3 of the control circuit IC. For example, by a microcontroller, a reference voltage can be specified, which determines the height of the maximum voltage across the measuring resistor (shunt) Rs permissible voltage and thus the maximum permissible by the first switch S1 current.
  • the microcontroller can output a PWM signal, which is then smoothed by a filter 10 (for example an RC element) and thus applied as a DC signal with a specific amplitude to the input 3 of the control circuit IC.
  • a filter 10 for example an RC element
  • the amplitude of the signal at the input 3 of the control circuit IC can be adjusted.
  • the control circuit IC can detect the achievement of the demagnetization of the coil L1 via the input 5 by monitoring the voltage across a secondary winding L2 applied to the coil L1. This detection can be used as a reclosing signal. Once the demagnetization of the coil L1 has been detected by the control circuit IC, the control circuit IC, the first switch S1 by a control via the output 7 turn on.
  • the control circuit IC can be activated and / or deactivated by applying a voltage at the input 1.
  • This input enable voltage 1 may also switch between a high and a low level, at high level activating the control circuit IC and at low, at least interrupting the actuation of the first switch S1.
  • This control of the input 1 can be done by a microcontroller. For example, in this way a low-frequency activation and deactivation of the control circuit IC and thus the activation of the first switch S1 can be achieved and thus the low-frequency control of the operating circuit for dimming the LED.
  • a further reference voltage for the control circuit IC can also be preset via the amplitude of the signal present at this input. This voltage can, for example, also influence the height of the maximum permissible current through the switch or also the permissible duty cycle of the first switch S1.
  • the control circuit IC and / or the control circuit IC combined with the microcontroller can together form the control unit SR.
  • the switch-on duration of the first switch S1 can also be dependent on a further voltage measurement within the operating circuit.
  • the control circuit IC can also be supplied with a voltage measurement Vsense. About this voltage measurement can be done via a voltage divider R40 / R47, for example, a monitoring or measurement of the voltage at the junction between coil L1 and LED.
  • This voltage measurement Vsense can either be supplied to an additional input of the control circuit IC, as an additional variable additively to an already occupied input of the control circuit IC or else to an input of the microcontroller.
  • a system can be constructed in which on the one hand a simple control for dimming of LED by low-frequency PWM is made possible, on the other hand low-loss as possible high-frequency operation of the operating device combined with a constant current as possible through the LED.
  • both the frequency and the duty cycle of a PWM signal for dimming LED, next to the height of the maximum allowable current can be specified by the first switch S1.
  • the microcontroller can control the dimming of the LED by low-frequency PWM via a signal which is fed to the input 1 of the control circuit IC. Furthermore, the microcontroller via a signal which is fed to the input 3 of the control circuit IC, the height of the maximum allowable current through the first switch S1 or the required duty cycle of the first switch S1 specified.
  • the operating circuit may further include a further switch S2, which is arranged so that this second switch S2 can bridge the LED.
  • the second switch S2 may further be arranged so that it can take over the current through an existing high-impedance voltage measuring path or a similar existing high-resistance circuit arrangement of the LED or interrupt it.
  • the second switch S2 By connecting the second switch S2 in parallel to the LED, the latter can bridge the LED and thus deactivate it.
  • This method can be used to adjust the brightness (dimming) of the LED.
  • a possible variant would be that the dimming takes place via the second switch S2, while only the current through the LED is set and regulated via the activation of the first switch S1.
  • the control of the two switches S1 and S2 can be used in combination for optimized dimming control.
  • the second switch S2 can be additionally used only for dimming to a low dimming level.
  • the operating circuit due to the existing topology and control circuitry, is designed to limit the output voltage of the operating circuit (i.e., the voltage across the LED) to a maximum allowable value. If the LED is bridged by closing the second switch S2, then the operating circuit limits the output voltage such that no excessive current can flow, which can lead to possible destruction. This activation of the second switch S2 can be used, for example, only for dimming to a low dimming level.
  • the LEDs can only be dimmed with second switch S2, which should be very low impedance, and the losses are still low.
  • the second switch S2 can be controlled so that it can take over the current through an existing high-impedance voltage measuring path or a similar existing high-resistance circuit arrangement of the LED. If, for example, according to Fig. 6 the first switch S1 is not clocked, no current should flow through the LED. However, due to the existing voltage divider R40 / R47, a small current can flow through the LED.
  • the second switch S2 can be closed, so that the current flow through the LED is interrupted or avoided.
  • the second switch S2 can at least always be triggered following a low-frequency PWM packet in order to bridge or deactivate the LED (during the last discharge edge, ie at the end of a PWM pulse packet).
  • An interruption of the current through the LED can also be done by arranging the second switch S2 in series with the LED.
  • Fig. 6 (and the others, of course) can be extended to include multiple operational circuits according to FIG. 6 available.
  • the control circuits IC and the control units SR of the individual operating circuits are controlled by a common microcontroller.
  • the individual operating circuits can drive, for example, LED strands of different wavelength or color.
  • the microcontroller can be controlled via an interface (wireless or wired). In this case, control signals for adjusting the brightness or color or status information can be transmitted via the interface.

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  • Circuit Arrangement For Electric Light Sources In General (AREA)

Claims (14)

  1. Circuit de fonctionnement destiné à au moins une LED, auquel une tension continue ou une tension alternée redressée est appliquée et qui met une tension d'alimentation à la disposition d'au moins une LED à l'aide d'une bobine (L1) et d'un premier interrupteur (S1) cadencé par une unité de commande/régulation (SR), une énergie étant stockée provisoirement dans la bobine (L1) lorsque le premier interrupteur S1 est fermé, laquelle énergie se décharge via une diode de roue libre (D1) et au moins une LED lorsque le premier interrupteur (S1) est ouvert, un condensateur (C1) étant prévu, lequel est disposé en parallèle à ladite au moins une LED et maintient le courant dans la LED pendant la phase de démagnétisation de la bobine (L1),
    caractérisé en ce qu'une première unité de capteur (SE1) est prévue, laquelle génère un premier signal de capteur (SES1) dépendant du flux de courant dans le premier interrupteur (S1), de même qu'une seconde unité de capteur (SE2) qui détecte le moment où la démagnétisation de la bobine (L1) est terminée et génère un signal de capteur (SES2), et en ce que les signaux de capteur (SES1, SES2) sont envoyés à l'unité de commande/régulation (SR) puis traités, l'unité de commande/régulation (SR) fermant à nouveau le premier interrupteur (S1) au moment où la bobine (L1) est démagnétisée et où elle bloque alors la diode de roue libre (D1).
  2. Circuit de fonctionnement conformément à la revendication 1, caractérisé en ce que l'unité de commande (SR) utilise une combinaison d'un signal (SES1) de la première unité de capteur (SE1) et d'un signal (SES2) de la seconde unité de capteur (SE2) pour déterminer le moment de fermeture et d'ouverture du premier interrupteur (S1).
  3. Circuit de fonctionnement conformément à la revendication 2, caractérisé en ce que l'unité de commande/régulation (SR) ouvre le premier interrupteur (S1) lorsque le courant dans le premier interrupteur (S1) dépasse une valeur maximale de référence.
  4. Circuit de fonctionnement conformément à l'une des revendications ci-dessus, caractérisé en ce que la première unité de capteur (SE1) est une résistance de mesure (Shunt, RS).
  5. Circuit de fonctionnement conformément à l'une des revendications ci-dessus, caractérisé en ce que la seconde unité de capteur (SE2) consiste en un enroulement secondaire (L2) couplé par induction à la bobine (L1).
  6. Circuit de fonctionnement conformément à l'une des revendications ci-dessus, caractérisé en ce que la seconde unité de capteur (SE2) est un capteur à effet Hall.
  7. Circuit de fonctionnement conformément à l'une des revendications ci-dessus, caractérisé en ce que la seconde unité de capteur (SE2) détecte le moment où la démagnétisation de la bobine (L1) est terminée, dans la mesure où elle surveille la tension (Ux) dans le point de connexion entre le premier interrupteur (S1) et la bobine (L1).
  8. Circuit de fonctionnement conformément à la revendication 7, caractérisé en ce que la saisie de la tension (Ux) est effectuée à l'aide d'un diviseur de tension résistif (R1/ R2), d'un diviseur de tension capacitif ou d'un diviseur de tension combiné résistif et capacitif.
  9. Circuit de fonctionnement conformément à l'une des revendications ci-dessus, comportant un circuit de commande IC disposant d'une entrée qui permet de détecter le moment où la démagnétisation d'une bobine (L1) est terminée et commandant un premier interrupteur (S1).
  10. Circuit de fonctionnement conformément à l'une des revendications ci-dessus, comportant un microcontrôleur, lequel par application d'une tension à une entrée du circuit de commande IC active et/ou désactive ce dernier et lequel spécifie sur une autre entrée une tension de référence pour le circuit de commande IC.
  11. Circuit de fonctionnement conformément à l'une des revendications ci-dessus, caractérisé par un second interrupteur (S2) disposé en parallèle au condensateur (C1) et aux LED et pouvant être commandé indépendamment du premier interrupteur (S1).
  12. Circuit de fonctionnement conformément à la revendication 11, caractérisé en ce que le second interrupteur (S2) est fermé afin d'accélérer l'opération de décharge du condensateur (C1).
  13. Procédé de fonctionnement d'au moins une LED à l'aide d'un circuit régulateur de commutation auquel une tension continue ou une tension alternée redressée est appliquée et qui, à l'aide d'une bobine (L1) et d'un premier interrupteur (S1) cadencé par une unité de commande et de régulation (SR), met une tension d'alimentation à la disposition d'au moins une LED, une énergie étant stockée provisoirement dans la bobine (L1) lorsque le premier interrupteur S1 est fermé, laquelle énergie se décharge via une diode de roue libre (D1) et au moins une LED lorsque le premier interrupteur (S1) est ouvert, un condensateur (C1) étant prévu, lequel est disposé en parallèle à ladite au moins une LED et maintient le courant dans la LED pendant la phase de démagnétisation de la bobine (L1), caractérisé en ce qu'une première unité de capteur (SE1) est prévue, laquelle génère un premier signal de capteur (SES1) dépendant du flux de courant dans le premier interrupteur (S1), de même qu'une seconde unité de capteur (SE2) qui détecte le moment où la démagnétisation de la bobine (L1) est terminée, l'unité de commande/régulation (SR) fermant à nouveau le premier interrupteur (S1) au moment où la bobine (L1) est démagnétisée et où elle bloque alors la diode de roue libre (D1).
  14. Procédé de fonctionnement d'au moins une LED conformément à la revendication 13, caractérisé en ce que l'unité de commande/régulation (SR) ouvre le premier interrupteur (S1) lorsque le courant dans le premier interrupteur (S1) dépasse une valeur maximale de référence.
EP09752099A 2008-10-20 2009-10-16 Circuit de fonctionnement destiné à des led Active EP2345308B1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
AT5992008 2008-10-20
PCT/EP2009/007455 WO2010046065A1 (fr) 2008-10-20 2009-10-16 Circuit de fonctionnement destiné à des led

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EP2345308A1 EP2345308A1 (fr) 2011-07-20
EP2345308B1 true EP2345308B1 (fr) 2012-08-29

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US (1) US8525442B2 (fr)
EP (1) EP2345308B1 (fr)
CN (1) CN102187736B (fr)
DE (1) DE112009002593A5 (fr)
GB (1) GB2476609B (fr)
WO (1) WO2010046065A1 (fr)

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US8525442B2 (en) 2013-09-03
EP2345308A1 (fr) 2011-07-20
GB201106312D0 (en) 2011-06-01
US20110199023A1 (en) 2011-08-18
GB2476609B (en) 2014-02-19
WO2010046065A1 (fr) 2010-04-29
CN102187736A (zh) 2011-09-14
DE112009002593A5 (de) 2011-09-29
CN102187736B (zh) 2013-06-19
GB2476609A (en) 2011-06-29

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