EP2202839B1 - Kompakte Speiseeinrichtung zur Erzeugung einer Zirkularpolarisation in einer Antenne und Herstellungsvervahren einer solchen Speiseeinrichtung - Google Patents

Kompakte Speiseeinrichtung zur Erzeugung einer Zirkularpolarisation in einer Antenne und Herstellungsvervahren einer solchen Speiseeinrichtung Download PDF

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Publication number
EP2202839B1
EP2202839B1 EP09169222.8A EP09169222A EP2202839B1 EP 2202839 B1 EP2202839 B1 EP 2202839B1 EP 09169222 A EP09169222 A EP 09169222A EP 2202839 B1 EP2202839 B1 EP 2202839B1
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Prior art keywords
omt
coupling slots
coupler
electric field
main waveguide
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English (en)
French (fr)
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EP2202839A1 (de
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Pierre Bosshard
Philippe Lepeltier
Sophie Verlhac
Alain Lasserre
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Thales SA
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Thales SA
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/16—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion
    • H01P1/161—Auxiliary devices for mode selection, e.g. mode suppression or mode promotion; for mode conversion sustaining two independent orthogonal modes, e.g. orthomode transducer
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies
    • H01P1/2131—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies with combining or separating polarisations

Definitions

  • the present invention relates to a compact excitation unit for generating a circular polarization in an antenna, to an antenna comprising such a compact excitation assembly and to a method for producing such a compact excitation assembly. It applies in particular to the field of transmitting and / or receiving antennas and more particularly to antennas comprising an array of elementary radiating elements connected to an orthomode transducer device associated with a coupler, such as for example multibeam antennas.
  • the development of a large number of contiguous beams involves producing an antenna comprising a large number of elementary radiating elements, placed in the focal plane of a parabolic reflector, the spacing of which depends directly on the angular difference between the beams.
  • the volume allocated for the location of an RF radio frequency chain responsible for performing the circular bipolarization transmission and reception functions is limited by the radiative surface of a radiating element, in the case of a multibeam application.
  • each source consisting of a radiating element coupled to a radiofrequency chain
  • produces a beam also called a spot
  • each formed beam is emitted for example by a dedicated horn constituting the elementary radiating element and the radiofrequency chain performs, for each beam, transmission / reception functions in mono-polarization or bi-polarization in a frequency band chosen according to the needs of users and / or operators.
  • a radiofrequency chain mainly comprises an exciter and waveguide paths, also called recombination circuits, for connecting the radio frequency components.
  • an exciter comprising an orthomode transducer known by the acronym OMT (in English: OrthoMode Transducer) connected to an elementary radiating element by example of cornet type.
  • OMT orthomode transducer
  • the OMT feeds the horn (in transmission), or is fed by the horn (in reception), selectively either with a first electromagnetic mode having a first polarization, or with a second electromagnetic mode having a second polarization orthogonal to the first.
  • the first and second polarizations, to which two electric field components are associated are linear and called respectively horizontal polarization H and vertical polarization V.
  • Circular polarization is achieved by associating the OMT with a branch coupler (in English: branch line coupler ) responsible for placing the electric field components H and V in quadrature phase.
  • branch coupler in English: branch line coupler
  • the search for a compact solution leads to grouping the radio frequency components and the recombination circuits of the radiofrequency chain on several levels stacked one below the other, as represented for example on the Figures 1a and 1b described below.
  • the higher the number of beams the greater the complexity, the mass and the cost of the radiofrequency chain.
  • the document DE 31 11,106 describes an OMT with two diametrically opposite branches, and connected to a branch coupler.
  • the document WO 00/16431 describes a two-branch OMT.
  • the coupling between the main waveguide and the two branches of the OMT is achieved by two orthogonal slots in the wall of the main waveguide of the UNWTO.
  • the document US 4,060,808 describes a system for automatically correcting the depolarization of a signal due to the Faraday effect when the signal passes through an ionized medium.
  • the system includes a rotational OMT connected to two hybrid couplers connected in series via two flexible waveguides.
  • the document US 7,408,427 describes a symmetrical OMT coupled to a balanced branch coupler.
  • the object of the present invention is to remedy this problem by proposing a new excitation unit operating in bi-polarization, not requiring adjustment and making it possible to simplify and make more compact the radiofrequency chain and thereby reduce its mass. and the cost.
  • the invention relates to a compact excitation unit, according to claim 1, for generating a circular polarization in an antenna comprising a diplexant orthomode transducer and a branch coupler, characterized in that the orthomode transducer, called OMT, is asymmetrical and comprises a main waveguide with square or circular section of longitudinal axis ZZ 'and two branches coupled to the main waveguide respectively by two parallel coupling slots, the two coupling slots being made in two orthogonal walls of the waveguide, the two branches of the OMT being respectively connected to two waveguides of an unbalanced branch coupler, the branch coupler having two different partition coefficients and optimized so as to compensate for orthogonal parasitic components of the electric field generated by the dissymmetry of the OMT.
  • the orthomode transducer called OMT
  • the branch coupler having two different partition coefficients and optimized so as to compensate for orthogonal parasitic components of the electric field generated by the dissymmetry of the OMT.
  • the section of the main waveguide of the OMT downstream of the coupling slots is smaller than the section of the main waveguide of the OMT upstream of the coupling slots, the section breaking forming a plane of short circuit.
  • the coupling slots of the OMT having a length L1 and a width L2 are connected to the branch coupler by means of two stub filters placed at a distance D1 from the coupling slots, the distance D1, the length L1 and width L2 are chosen so as to achieve an orthogonality between the parasitic components of the electric field generated by the dissymmetry of the OMT.
  • the invention also relates to an antenna characterized in that it comprises at least one such compact excitation assembly.
  • the invention also relates to a method for producing a compact excitation assembly for generating a circular polarization in an antenna, characterized in that it consists in coupling an asymmetric OMT orthomode transducer with two branches with an unbalanced branch coupler comprising two different partition coefficients, to size the OMT so as to establish a phase quadrature between two parasitic electric field components generated by the dissymmetry of the OMT, and to optimize the coupling coefficients of the coupler with branches to compensate for the two parasitic components of the electric field.
  • the dimensioning of the OMT consists in determining a length L1 of the coupling slots of the OMT, in determining a distance D1 separating the coupling slots of two stub filters placed between the coupling slots and the branch coupler. placing a short-circuit plane in the main waveguide of the OMT downstream of the coupling slots, the distance D1, the length L1 and the width L2 being chosen so as to achieve orthogonality between the parasitic components of electric field generated by the dissymmetry of the OMT.
  • the orthomode transducer 5 with four branches shown in FIG. figure 1a comprises a main waveguide 10 of longitudinal axis ZZ ', with a square section or circular, for example, having a first end intended to be connected to a horn, not shown, and a second end end, the two ends being located in the longitudinal axis of the body of the main waveguide.
  • a group of four parallel, or parallel, longitudinal slots 11, 12, 13, 14 are formed in the wall of each of the four lateral faces of the main waveguide and arranged diametrically opposite in pairs. Between the horn and the coupling slots, the dimensions of the main waveguide 10 are adapted to the propagation of the fundamental electromagnetic modes associated with the H and V field components of the main waveguide in the transmit and transmit frequency bands. reception.
  • the section of the main waveguide decreases which generates a short circuit plane for the low frequency band.
  • the waveguide behaves like a high-pass filter that passes only the high frequency band.
  • the H and V field components associated with the fundamental electromagnetic modes TE01 and TE10 of the square section waveguide, or the modes TE11H and TE11V of the circular section waveguide are coupled in the low frequency band, for example the transmission band, by the four parallel coupling slots 11, 12, 13, 14.
  • the high frequency band for example the reception band, is rejected by four stub filters 15, 16, 17, 18 connected to each other. to the four parallel access slots and propagates in the main waveguide to its output end.
  • the OMT and filters unit thus has six physical ports and its operation is compatible with an application in linear polarization or circular polarization.
  • the low frequency band may, for example, be reserved for the transmission of RF radio frequency signals and the high frequency band may be reserved for receiving the RF signals.
  • the development of a circular polarization is provided by a 3 dB balanced branch coupler 19 which supplies the four coupling slots 11, 12, 13, 14 in pairs in quadrature phase. Opposite slots are phase-fed via in-phase recombination circuits.
  • the various components of the excitation assembly consisting of the OMT diplexant and the branch coupler are optimized separately and the overall transfer function results from intrinsic performance of each component.
  • the geometry of the four-pointed OMT 5 imposes, at the location of the coupling slots, a plane of symmetry to the electric field which propagates in the OMT which minimizes the amplitude of the cross-components of the electric field.
  • the circular polarization purity does not depend on the OMT 5 but only the branch coupler 19 and recombination circuits 20 which perform power sharing and phase quadrature between the coupling slots.
  • a septum polarizer is connected to the output end of the main waveguide of the OMT, the septum polarizer realizing the development of circular polarization on reception.
  • the radio frequency components and the recombination circuits of the radiofrequency chain are stacked on several levels, two levels 1, 2 are represented on the figure 1b but there are usually three, arranged one below the other.
  • the integration of the components is then maximal and to further reduce the mass, the volume and the cost of the radiofrequency chain, it is necessary to modify its architecture.
  • the figure 2 represents an example of a simplified architecture of an RF chain comprising a compact excitation unit, according to the invention.
  • the RF chain essentially comprises a diplexant orthomode transducer 21 with two branches represented on the Figures 3a and 3b and an unbalanced branch coupler 40.
  • the OMT 21 comprises a main waveguide 22, for example of square or circular section, and of longitudinal axis ZZ ', comprising two ends 23, 24, the first end 23 coupled to a circular access 31 being intended to be connected to a horn, not shown, and having two parallel access coupling slots 25, 26 formed in the wall of the main waveguide and opening into the respective two branches of the OMT.
  • the two parallel access slots 25, 26 are formed in two orthogonal sidewalls of the main waveguide and arranged, for example and preferably at the same height relative to the two ends 23, 24 of the waveguide main.
  • the low frequency band may for example be reserved for the transmission of RF signals and the high frequency band may be reserved for receiving the RF signals.
  • each of the two coupling slots 25, 26 is connected to the branch coupler 40 via a stub filter 27, 28 and recombination circuits 29, 30.
  • the circular access 31 constitutes the input and output port common to two electric field components, respectively horizontal H and vertical V, corresponding to two orthogonally polarized electromagnetic modes propagating on transmission and reception.
  • Each parallel access slot associated with a stub filter constitutes an input and output port of one of the electric field components, called a coupled port for this component, the other port being called an isolated port.
  • a coupled port for this component the other port being called an isolated port.
  • the horizontal electric field component H passes through the coupled port 32, the port 33 being the isolated port for this component H.
  • the coupled port is the port 33 and the isolated port is the port 32.
  • the coupler 40 has two rectangular waveguides 35, 36 forming two main branches respectively connected at one end to one of the ports 32, 33 of the OMT, and a second end, a respective supply port 37, 38, the supply ports 37, 38 having the same electrical length.
  • Each supply port is connected to each of the two main branches 35, 36 of the branch coupler 40 to supply it with an electric field.
  • the two main branches of the branch coupler are coupled together by means of coupling slots, not shown, opening into at least one transverse waveguide 39 constituting a transverse branch.
  • the length of the transverse guides 39 in a predetermined number, for example equal to three on the figure 2 , is equal to ⁇ g / 4 so as to produce, at the output of the branch coupler 40, a phase shift of 90 ° between the two electric field components, ⁇ g being the guided wavelength of the fundamental mode propagating in the main branches 35, 36 of the coupler 40.
  • a septum polarizer may be connected to the second end 24 of the main waveguide of the OMT.
  • the diplexant OMT with two branches does not allow the natural decoupling of the horizontal and vertical electric field components V due to the absence of symmetry at the location of the coupling slots 25, 26
  • the analysis of the parameters of the energy dispersion matrix between the common port 31 and the coupled port 32 corresponding to one of the components of the field electrical, then between the common port and the isolated port 33 of the same component of the electric field shows, as shown on the Figures 4 and 5 , that there is an energy coupling, of the order of -20 dB, between the coupled port and the isolated port and that there is a frequency-dispersive phase difference between the two ports, the phase quadrature being obtained only for a particular frequency, although physically the lengths from the common port 31 to the two coupled and isolated ports 32, 33 are identical.
  • the fundamental mode energy propagating in the main waveguide does not pass entirely into the coupled port but partly to the isolated port.
  • the power distribution between the two ports is due to the fact that in addition to the coupling of the TE10 fundamental mode at -20 dB, there is a -20 dB coupling of the TE20 mode (or TE02 depending on whether the component is considered H or V of the electric field) between the coupled port and the isolated port.
  • the TE20 (or TE02) mode interferes with the power sharing and induces a phase insertion different from the electric field on the port coupled to the isolated port.
  • the two-branched OMT does not allow to completely decouple the two components of the electric field when it is associated with a 3 dB balanced branch coupler which realizes the sharing of power in equal parts and the quadrature of phase between the coupling slots, it is not possible to obtain a circular polarization.
  • the polarization obtained is elliptic, with an ellipticity ratio of the radiated field equal to 1.7 dB.
  • the distance D1 between the slots 25, 26 and the beginning of the stub filters 27, 28 it is possible, as shown in the example of the figure 6 , to put the field component on the isolated port in phase quadrature with the field component on the coupled port and to make the differential phase behavior between these two coupled and isolated aperiodic field components over a bandwidth greater than 7% of the low total frequency band.
  • the distance D1 acts on the dispersion in phase frequency of the main field component on the coupled port relative to the parasitic cross-field component on the isolated port.
  • the length L1 and the width L2 make it possible to adjust the absolute phase at -90 ° between the field component on the coupled port and the parasitic field component on the isolated port.
  • the distance between the slot and the short circuit plane may for example be zero.
  • the optimization of the OMT shape parameters is a multivariate optimization for which other parameters act in the second order, creating for example energy beats between radiofrequency discontinuities, and that it does not It is possible to optimize only by successive iterations and by an analysis of the electromagnetic modes that propagate.
  • the figure 7 shows that the electric field resulting from a supply on the port of access 32, 33 of the horizontal polarization H, respectively vertical V, is then decomposed into two components out of phase by -90 °.
  • Ey for the access port 33 of the vertical component V of the electric field Ey is added a parasitic horizontal component ⁇ y that is out of phase by -90 ° with respect to Ey and for the access port 32 of the horizontal component H of the field Ex electric is added a parasitic vertical component ⁇ x phase-shifted by -90 ° with respect to Ex.
  • the spurious components ⁇ y and ⁇ x are attenuated by 20 dB with respect to the amplitude of Ex and Ey.
  • the asymmetrical OMT associated with an unbalanced branched coupler, allows the compensation of the defect induced by the dissymmetry of the OMT and an operation of the antenna in mono-polarization and bi-polarization with excellent purity of polarization.
  • the Figures 8a and 8b show a perspective view and a longitudinal sectional view of an example of unbalanced branch coupler 40, according to the invention.
  • the branch coupler 40 has four ports 1 to 4 located at the four ends of the two main branches. Ports 1 and 4 are intended to be connected to the two power ports, the two ports 2 and 3 are respectively intended to be connected to the ports coupled and isolated from the OMT.
  • ⁇ 1 - ⁇ 2
  • the phase delay of 90 ° between the two electric field components at the output of the branch coupler on the ports 2 and 3 corresponds to the lengths of the transversal guides equal to a quarter of the wavelength ⁇ g / 4.
  • the transverse guides have identical lengths but different widths.
  • the number of transverse branches is chosen according to the bandwidth requirement.
  • the widths of the transverse branches are defined as a function of the values of the coupling coefficient ⁇ and ⁇ to be produced.
  • the sharing coefficients ⁇ and ⁇ are chosen so as to compensate for the parasitic defect related to the dissymmetry of the OMT.
  • the ⁇ and ⁇ coefficients will no longer be equal as is the case in the balanced couplers usually used with a four-branch OMT, but will be different.
  • the partition coefficients are optimized in the presence of the OMT and compensate the horizontal and vertical parasitic components ⁇ y and ⁇ x so as to obtain on each port 2 and 3 of output, half of the power received on the input port 1.
  • the optimization of the sharing coefficients can be performed in reception, so as to compensate for the horizontal and vertical parasitic components ⁇ y and ⁇ x related to the dissymmetry of the OMT.
  • the Figures 9a and 9b show that the ellipticity rate obtained by combining a two-branch OMT and an unbalanced branch coupler according to the invention, is less than 0.1 dB on the Ka band between 19.7GHz and 20.2 GHz.
  • the ellipticity rate is less than 0.4 dB on 1.5 GHz bandwidth, which allows a use of this structure for a mission users but also for other applications regardless of the frequency bands.
  • the new architecture has the advantages of being very compact, the bulk of the sources, consisting of the RF chain and the horn of emission and reception, thus realized is of 60mm of diameter and 100mm of height.
  • an equivalent source assembly according to the prior art has a footprint of 150mm in height and 72mm in diameter.
  • the cost of implementation is optimal compared to the number of components. Indeed, reducing the number of mechanical parts allows a gain in preparation time.
  • the mass of the RF chain out of the horn is reduced by 60%.
  • the structure is simplified and the number of electric layers is reduced to one instead of three since the OMT, the branch coupler and the recombination circuits are on the same level.
  • the length of the guide paths is reduced by 50%, which allows a reduction in ohmic losses of 0.1 dB compared to the prior art with four-branched OMT whose ohmic losses were 0.25 dB.

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Claims (8)

  1. Kompakte Erregungsbaugruppe zum Erzeugen einer Zirkularpolarisierung in einer Antenne, welche einen diplexierenden Orthomodus-Wandler mit zwei Armen und einen Arm-Koppler beinhaltet, dadurch gekennzeichnet, dass der Orthomodus-Wandler (21), genannt OMT, asymmetrisch ist und einen Hauptwellenleiter (22) mit quadratischer oder kreisförmiger Querschnittsfläche und mit Längsachse ZZ' beinhaltet und zwei Enden (23, 24) entlang der Längsachse ZZ' beinhaltet, wobei der OMT zudem zwei Arme beinhaltet, welche mit dem Hauptwellenleiter (22) durch jeweils zwei Kopplungsschlitze (25, 26) gekoppelt sind, wobei die beiden Kopplungsschlitze (25, 26) in mindestens einer Wand des Wellenleiters praktiziert sind und voneinander um 90° entfernt sind, und in einer gleichen Höhe in Bezug auf die beiden Enden (23, 24) des Hauptwellenleiters (22) angeordnet sind, wobei die beiden Arme des OMT jeweils mit zwei Wellenleitern (35, 36) des Kopplers verbunden sind, wobei der Koppler ein unausgewogener Arm-Koppler (40) ist, wobei der Arm-Koppler (40) zwei unterschiedliche Teilungskoeffizienten (α, β) besitzt, welche so optimiert sind, dass sie rechtwinklige Störkomponenten (δy, δx) eines elektrischen Feldes, welche durch die Asymmetrie des OMT (21) erzeugt werden, kompensieren.
  2. Erregungsbaugruppe nach Anspruch 1, dadurch gekennzeichnet, dass die Querschnittsfläche des Hauptwellenleiters (22) des OMT im nachgelagerten Bereich der Kopplungsschlitze (25, 26) kleiner ist als die Querschnittsfläche des Hauptwellenleiters (22) des OMT im vorgelagerten Bereich der Kopplungsschlitze (25, 26), wobei der Querschnittsbruch eine Kurzschlussebene bildet.
  3. Erregungsbaugruppe nach einem der Ansprüche 1 oder 2, dadurch gekennzeichnet, dass die Kopplungsschlitze (25, 26) des OMT (21), welche eine Länge L1 und eine Breite L2 besitzen, mit dem Arm-Koppler (40) über zwei Stub-Filter (27, 28) verbunden sind, welche in einem Abstand D1 von den Kopplungsschlitzen (25, 26) angeordnet sind, und dadurch, dass der Abstand D1, die Länge L1 und die Breite L2 so gewählt sind, dass eine Rechtwinkligkeit zwischen den Störkomponenten (δy, δx) des elektrischen Feldes geschaffen wird, welche durch die Asymmetrie des OMT erzeugt werden.
  4. Erregungsbaugruppe nach einem der vorhergehenden Ansprüche, dadurch gekennzeichnet, dass die Teilungskoeffizienten (α, β) des Arm-Kopplers (40) anhand der drei folgenden Beziehungen bestimmt werden:
    - α2+β2 = 1
    - α.Ex - β.δy = 1/√2 Volt/Meter,
    - β.Ey + α.δx = 1/√2 Volt/Meter.
  5. Antenne, dadurch gekennzeichnet, dass sie einen kompakte Erregungsbaugruppe nach einem der vorhergehenden Ansprüche beinhaltet.
  6. Verfahren zum Schaffen einer kompakten Erregungsbaugruppe nach Anspruch 1 zum Erzeugen einer Zirkularpolarisierung in einer Antenne, dadurch gekennzeichnet, dass es darin besteht, einen asymmetrischen Orthomodus-Wandler OMT (21) mit zwei Armen durch jeweils zwei Kopplungsschlitze (25, 26) mit einem unausgewogenen Arm-Koppler (40) zu koppeln, welcher zwei unterschiedliche Teilungskoeffizienten (α, β) beinhaltet, den OMT (21) so zu dimensionieren, dass eine Phasenquadratur zwischen zwei Störkomponenten (δy,δx) eines elektrischen Feldes etabliert wird, welche durch die Asymmetrie des OMT erzeugt werden, und die Teilungskoeffizienten (α, β) des Arm-Kopplers (40) zu optimieren, um die beiden Störkomponenten (δy,δx) des elektrischen Feldes zu kompensieren.
  7. Verfahren nach Anspruch 6, dadurch gekennzeichnet, dass die Dimensionierung des OMT darin besteht, eine Länge L1 und eine Breite L2 der Kopplungsschlitze (25, 26) des OMT (21) zu bestimmen, eine Kurzschlussebene im Hauptwellenleiter des OMT im nachgelagerten Bereich der Kopplungsschlitze zu platzieren, einen Abstand D1 zu bestimmen, welcher die Kopplungsschlitze (25, 26) von zwei Stub-Filtern (27, 28) trennt, welche zwischen den Kopplungsschlitzen und dem Arm-Koppler (40) platziert sind, wobei der Abstand D1, die Länge L1 und die Breite L2 so gewählt sind, dass eine Rechtwinkligkeit zwischen den Störkomponenten (δy,δx) des elektrischen Feldes geschaffen wird, welche durch die Asymmetrie des OMT erzeugt werden.
  8. Verfahren nach einem der Ansprüche 6 oder 7, dadurch gekennzeichnet, dass die Teilungskoeffizienten (α, β) des Arm-Kopplers (40) anhand der drei folgenden Beziehungen bestimmt werden:
    - α2+β2 = 1
    - α.Ex - β.δy = 1/√2 Volt/Meter,
    - β.Ey + α.δx = 1/√2 Volt/Meter.
EP09169222.8A 2008-12-16 2009-09-02 Kompakte Speiseeinrichtung zur Erzeugung einer Zirkularpolarisation in einer Antenne und Herstellungsvervahren einer solchen Speiseeinrichtung Active EP2202839B1 (de)

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FR0807063A FR2939971B1 (fr) 2008-12-16 2008-12-16 Ensemble d'excitation compact pour la generation d'une polarisation circulaire dans une antenne et procede d'elaboration d'un tel ensemble d'excitation

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EP2202839B1 true EP2202839B1 (de) 2019-05-22

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US (1) US8493161B2 (de)
EP (1) EP2202839B1 (de)
JP (1) JP5678314B2 (de)
CN (1) CN101752632B (de)
CA (1) CA2678530C (de)
FR (1) FR2939971B1 (de)
RU (1) RU2511488C2 (de)

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FR3035546B1 (fr) * 2015-04-24 2017-04-21 Thales Sa Module structural d'antenne integrant des sources rayonnantes elementaires a orientation individuelle, panneau rayonnant, reseau rayonnant et antenne multifaisceaux comportant au moins un tel module
FR3035548B1 (fr) 2015-04-24 2017-05-05 Thales Sa Architecture d'antenne a plusieurs sources par faisceau et comportant un reseau focal modulaire
CN104868205B (zh) * 2015-05-28 2018-05-08 成都赛纳赛德科技有限公司 Y形结构准平面正交模转接器
RU2647203C2 (ru) * 2016-08-09 2018-03-14 Российская Федерация, от имени которой выступает Государственная корпорация по космической деятельности "РОСКОСМОС" Частотно-поляризационный селектор
CN106299554B (zh) * 2016-08-31 2019-05-14 电子科技大学 新型宽带矩形波导TEn,0模式激励器
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FR3071363B1 (fr) 2017-09-19 2019-09-06 Thales Joint tournant pour une antenne rotative et antenne rotative comportant un tel joint
FR3071365B1 (fr) 2017-09-19 2019-09-06 Thales Antenne biaxe comportant une premiere partie fixe, une deuxieme partie rotative et un joint tournant
CN108847521B (zh) * 2018-05-04 2020-03-17 杭州电子科技大学 宽带差分馈电微带滤波天线
EP3836302B1 (de) * 2018-09-30 2023-06-14 Huawei Technologies Co., Ltd. Antenne und endgerät
US11228116B1 (en) * 2018-11-06 2022-01-18 Lockhead Martin Corporation Multi-band circularly polarized waveguide feed network
US10763593B1 (en) * 2018-11-07 2020-09-01 Lockheed Martin Corporation Broadband single pol TX, dual pol RX, circular polarization waveguide network
JP7252054B2 (ja) * 2019-05-15 2023-04-04 日本無線株式会社 ターンスタイル型偏分波器
US11658379B2 (en) * 2019-10-18 2023-05-23 Lockheed Martin Corpora Tion Waveguide hybrid couplers
WO2021083498A1 (en) * 2019-10-29 2021-05-06 European Space Agency Waveguide component for use in an orthomode junction or an orthomode transducer
US11710907B1 (en) * 2020-01-09 2023-07-25 Lockheed Martin Corporation Clone carousel waveguide feed network
CN111613857B (zh) * 2020-05-25 2022-02-01 南京师范大学 一种采用双层开槽圆形贴片的双通带滤波耦合器
CN111900513B (zh) * 2020-09-04 2021-11-19 北京邮电大学 正交模转换器、天线设备及通信系统
CN112103656A (zh) * 2020-09-17 2020-12-18 成都天锐星通科技有限公司 一种双线极化馈源喇叭
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CN112563710B (zh) * 2020-12-07 2022-02-01 江苏亨通太赫兹技术有限公司 一种e波段正交模耦合器
CN112510339B (zh) * 2020-12-22 2021-10-15 华南理工大学 一种高选择性增益的双极化滤波贴片天线
CN113036387B (zh) * 2021-04-21 2021-10-22 中国电子科技集团公司第五十四研究所 一种正交模转换器的加工方法
CN114256581B (zh) * 2021-12-06 2023-02-28 电子科技大学 基于高隔离网络的径向波导功率分配/合成器
CN115295983B (zh) * 2022-07-26 2024-01-02 武汉凡谷电子技术股份有限公司 一种滤波器

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CN101752632A (zh) 2010-06-23
US8493161B2 (en) 2013-07-23
FR2939971A1 (fr) 2010-06-18
US20100149058A1 (en) 2010-06-17
CA2678530C (fr) 2017-03-21
EP2202839A1 (de) 2010-06-30
FR2939971B1 (fr) 2011-02-11
JP2010148109A (ja) 2010-07-01
JP5678314B2 (ja) 2015-03-04
RU2009133480A (ru) 2011-03-20
CA2678530A1 (fr) 2010-06-16
RU2511488C2 (ru) 2014-04-10
CN101752632B (zh) 2014-05-21

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