Classifications

• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
  • H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
  • H02P6/08—Arrangements for controlling the speed or torque of a single motor
  • H02P6/085—Arrangements for controlling the speed or torque of a single motor in a bridge configuration
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
  • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
  • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
  • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
  • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
  • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
  • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
  • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
  • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
  • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
  • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
  • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
  • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
  • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
  • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
  • H02P27/00—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage
  • H02P27/04—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage
  • H02P27/06—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters
  • H02P27/08—Arrangements or methods for the control of AC motors characterised by the kind of supply voltage using variable-frequency supply voltage, e.g. inverter or converter supply voltage using dc to ac converters or inverters with pulse width modulation
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
  • H02P29/00—Arrangements for regulating or controlling electric motors, appropriate for both AC and DC motors
  • H02P29/60—Controlling or determining the temperature of the motor or of the drive
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
  • H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
  • H02P7/03—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors
  • H02P7/04—Arrangements for regulating or controlling the speed or torque of electric DC motors for controlling the direction of rotation of DC motors by means of a H-bridge circuit
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
  • H02P7/00—Arrangements for regulating or controlling the speed or torque of electric DC motors
  • H02P7/06—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current
  • H02P7/18—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power
  • H02P7/24—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices
  • H02P7/28—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices
  • H02P7/285—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only
  • H02P7/29—Arrangements for regulating or controlling the speed or torque of electric DC motors for regulating or controlling an individual dc dynamo-electric motor by varying field or armature current by master control with auxiliary power using discharge tubes or semiconductor devices using semiconductor devices controlling armature supply only using pulse modulation
• • H—ELECTRICITY
  • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
  • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
  • H02M1/00—Details of apparatus for conversion
  • H02M1/0003—Details of control, feedback or regulation circuits
  • H02M1/0012—Control circuits using digital or numerical techniques

Definitions

• the invention relates to an electronic electric motor commutator and a method for driving such a commutator.
• An electronic commutator is used to control the speed and torque of a brushless electric motor.
• Each electric motor has at least one stator and / or rotor coil, which is energized by the commutator.
• the commutator has a switching bridge with a so-called low-side semiconductor and a high-side semiconductor.
• the switching bridge is controlled by a pulse width modulator.
• the pulse width modulator generates a pulse-width-modulated periodic signal with which one of the two switching semiconductors of the switching bridge is driven.
• the modulation frequency is so high that due to the electrical time constant of the motor and the stored energy in the strand inductances, the current periodically introduced into the motor coils by the pulse width modulator is smoothed to a mean current in the respective motor coil.
• either the low-side semiconductor or the high-side semiconductor of the switching bridge is driven by the pulse-width modulator, the complementary switching semiconductor being closed during the entire modulation phase, ie, being conductive.
• the permanently closed complementary switching semiconductor forms in the energizing pauses between two pulses of the pulse width-modulated signal a freewheel.
• the jumper is half-bridge or full-bridge, and regardless of whether the jumper drives one, two, three or more motor coils, the respective one of them will Lowside and highside semiconductors subjected to different loads. Only at a pulse width ratio of 100%, ie at a ratio of the pulse length to the cycle length of 1.0, the electrical and the thermal load of the low-side and the high-side semiconductor is at the same level of about 50% of the total power loss.
• the object of the invention is in contrast to provide an electric motor commutator or a method for driving an electric motor commutator, in which the power semiconductors of the switching bridge are loaded symmetrically.
• the pulse width modulator is connected to both the low side semiconductor and the high side semiconductor.
• An operating mode changeover switch is provided which switches the pulse width modulator alternately to the highside or the low side semiconductor.
• the switching frequency f H ⁇ _ with which the mode switch between the low-side and the high-side mode switches back and forth, depending on the thermal inertia of the two semiconductor concerned to choose.
• the mode switching frequency f H ⁇ _ must be so high that at pulse widths between 0% and 100% unbalanced heating of one of the two mutually corresponding switching semiconductor with respect to the other corresponding switching semiconductor is excluded.
• Mode switching can be used with various switching bridge topologies, ie IH, 3H, M6, B6, etc. topologies.
• the maximum temperature of the switching bridge semiconductors can be reduced by 15 - 20 K and more.
• the respective semiconductors can therefore be dimensioned correspondingly smaller, which in turn results in cost advantages. If necessary, lower demands are placed on heat-dissipating agents. Furthermore, the avoidable temperature peaks also increase safety against destruction and reliability.
• the operating mode switching frequency f H ⁇ _ below modulation frequency f M of the pulse width modulator is at least 60% below the modulation frequency f M.
• the mode switching frequency f HL is always to be selected so high that a significant increase in the temperature of the one semiconductor over that of the other corresponding semiconductor over the duration of an operating mode is virtually eliminated until switching.
• the operating mode switching frequency f HL is less than 5 kHz.
• the mode switch is timed. Regardless of the speed or rotational frequency of the electric motor switching the mode is operated at a constant frequency. As a result, too low a switching frequency, which could lead to an undesirable heating of one of the corresponding semiconductors, can be reliably excluded.
• a position-controlled switching of the operating mode can be realized.
• this represents the simpler solution since rotor positional information is present anyway with electrically commutated electric motors.
• the operating mode can be switched every 15 °, 30 ° or 60 ° of a full rotor turn.
• position-controlled mode switching it must be ensured that a minimum mode switching frequency is not undershot, in order to avoid unwanted heating of one of the two corresponding semiconductors.
• the switching bridge of the commutator can be designed as a half bridge. According to a preferred embodiment, however, the switching bridge is designed as a full bridge. As a result, the motor coils or strands can be energized in both directions. This opens u. a. the possibility of operating the motor in both directions of rotation.
• the commutator is designed such that an active freewheel can be realized during the clock break or is realized. As a result, the total power loss is reduced because the freewheeling current no longer runs via a freewheeling diode, but via a closed switching semiconductor.
• Commutator including a reduced illustrated Switching bridge and switching bridge control with a pulse width modulator
• Fig. 2 shows the curves of the current through the motor coil
• Fig. 3 shows the curves of the current through the motor coil
• FIG. 1 Shown in FIG. 1 is a simplified and reduced illustrated motor assembly 10 which is essentially formed by a commutator 12 and an electric motor 14.
• the electric motor 14 is a brushless electronically commutated electric motor having a permanent magnet motor rotor 16 and three stator side motor coils L. , L ', L ".
• the three motor coils L, L', L" are supplied with current by the commutator 12.
• FIG. 1 shows the commutator 12 in a greatly reduced manner in order to explain, by way of example and clearly, two different operating states with respect to a half-bridge formed by the semiconductors Ti and T 3 .
• the commutator 12 has a switching bridge 20 designed as a full bridge whose switching semiconductors Ti, T 2 , T 3 , T 4 are driven by a switching bridge driver 22.
• the switching semiconductors Ti, T 2 , T 3 , T 4 are MOSFET semiconductors, but can also be formed from other switchable power semiconductors.
• Parallel to the semiconductors Ti - T 4 are freewheeling diodes Di - D 4 , which allow a current flow during the switching pauses.
• the switching bridge driver 22 has inter alia a microcomputer 24, a pulse width modulator 26 and a mode switch 28.
• the control 22 is more complex since only two modes of operation in a direction of current flow with respect to a half-bridge are explained by way of example here and, inter alia, a representation of the control of the semiconductor T 2 and T 4 VOlNg has been omitted. In fact, all three motor coils L, L ', L "are energized with alternating current directions. The principle of control 22 will be explained by way of example at one of the three H-bridges.
• the signal generated by the pulse width modulator is passed either to a high-side semiconductor Ti, T 2 or to a low-side semiconductor T 3 , T 4 .
• the complementary switching semiconductor T 3 , T 4 , or Ti, T 2 which likewise lies in the bridge branch, can be activated for active freewheeling.
• the pulse width modulator is connected exclusively to the respective high-side semiconductor Ti.
• the corresponding low-side semiconductor T 4 is then permanently closed.
• the clock break of the pulse-width-modulated signal of the highside semiconductor Ti is open, ie it falls there during the clock break no power loss and thus no further heating.
• the corresponding semiconductor T 4 remains closed, so that in the lower half of the switching bridge 20, a freewheel can be set in the clockwise direction by the motor coil L, the low side semiconductor T 4 and the freewheeling diode D4 or optionally the closed semiconductor T 3 in Circle is running. Only at a duty cycle of 100% is the power dissipation in the high-side semiconductor Ti and the corresponding low-side semiconductor T 4 identical.
• the considered low-side semiconductor T 4 is also stressed during the active freewheeling phases when the high-side semiconductor T 2 modulating the energization of the motor coil L in the opposite direction is opened.
• a mode switch 28 is provided, which can turn on the pulse width modulator 26 alternately on the or the high-side semiconductor Ti, T 2 and the low-side semiconductor T 4 , T 3 . It is always possible to switch between a highside mode and a low side mode. As a result, the power dissipation asymmetry between the high-side semiconductors Ti, T 2 and the low-side semiconductors T 3 and T 4 is always reversed at the frequency of the mode switching, ie, the possibly higher power dissipation alternately on the high-side semiconductor Ti, T 2 on the one hand and the low-side semiconductors T 3 , T 4 switched on the other hand.
• a rotor circulation of 360 ° is divided into six phases A - F, each of 60 °.
• the nine timing diagrams of FIGS. 2 and 3 show the time courses of the coil current I L (1), the switching states of the semiconductors Ti, T 3 , T 2 and T 4 (FIGS. 2 to 5) and the corresponding semiconductor currents I T i. I ⁇ 3, I T2 and I T4 through the semiconductors Ti to T 4 , in Fig. 2 with passive and in Fig. 3 with active freewheeling.
• the highside and lowside phases are marked with "h" and "I" in the diagrams.
• phase A (0 ° -60 °), the pulse-width-modulated signal of the pulse width modulator 26 is connected to the high-side semiconductor Ti, so that a corresponding current profile I T i results through the semiconductor Ti.
• the corresponding low-side semiconductor T 4 is permanently closed in phase A.
• the high side semiconductor Ti is turned on and a current flows from the pulse pole via the semiconductor Ti, the motor coil, the semiconductor T 4 to the negative pole.
• the low signal of the modulator 26 the current flow through the coil L via the diode D 3 or the semiconductor T3 and the lowside half-T 4 is maintained, which is the so-called freewheel.
• the other highside semiconductor T 2 is open in phase A.
• the low-side semiconductor T 3 is open during passive freewheeling (see FIG. 2).
• the current flow is kept upright via the diode D3.
• the low-side semiconductor T 3 is switched or clocked in a manner complementary to the high-side semiconductor Ti (see FIG. 3).
• phase B (60 ° - 120 °) is switched from the highside mode to the Lowside mode, so that the pulse width modulated signal of the pulse width modulator 26 now on the corresponding to the highside semiconductor Ti lowside semiconductor T 4 is switched.
• the corresponding high-side semiconductor Ti is closed during the entire phase B, so switched through.
• the high-side semiconductor Ti conducts the current during the pulses of the pulse-width-modulated signal and also during the pulse pauses in free-running, so that a corresponding power loss continuously occurs during the phase B in Ti.
• phase C (120 ° - 180 °) serves as well as the phase F (300 ° - 360 °) the Umkommuttechnik.
• phase F 300 ° - 360 °
• all of the semiconductors Ti - T 4 are opened so that no currents flow through the semiconductors Ti - T 4 and through the coil L, respectively.
• phase D the low-side mode of operation applies, so that the pulse-width-modulated signal is conducted to the first low-side semiconductor T 3 .
• the corresponding second high-side semiconductor T 2 is thus completely and uninterrupted closed during phase D.
• phase E the pulse-width-modulated signal is switched to the second high-side semiconductor T 2 . Accordingly, the corresponding first low-side semiconductor T 3 is closed completely and without interruption.
• the integral of the respective current characteristics is All four semiconductors Ti - T 4 equal, so that the power loss on all four semiconductors Ti - T 4 is the same, that is symmetrical. This applies regardless of the duty cycle of the pulse-width-modulated signal, ie for a duty cycle of 0% - 100%. As a result, compared to unbalanced load during operation without mode switching, the maximum occurring on a semiconductor power loss and thus the maximum heating can be reduced and the semiconductors and the cooling measures are dimensioned correspondingly smaller.

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• Engineering & Computer Science (AREA)
• Power Engineering (AREA)
• Control Of Motors That Do Not Use Commutators (AREA)
• Control Of Direct Current Motors (AREA)

Applications Claiming Priority (2)

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• 2007
  • 2007-07-06 DE DE102007031548A patent/DE102007031548A1/de not_active Withdrawn
• 2008
  • 2008-05-29 EP EP08760164A patent/EP2165411A2/de not_active Withdrawn
  • 2008-05-29 CN CN200880023532XA patent/CN101689822B/zh not_active Expired - Fee Related
  • 2008-05-29 WO PCT/EP2008/056572 patent/WO2009007175A2/de active Application Filing

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