EP1969707A1 - Circuiterie dotee d'une double bobine destinee a la generation d'une tension alternative ou d'un courant alternatif - Google Patents

Circuiterie dotee d'une double bobine destinee a la generation d'une tension alternative ou d'un courant alternatif

Info

Publication number
EP1969707A1
EP1969707A1 EP06841242A EP06841242A EP1969707A1 EP 1969707 A1 EP1969707 A1 EP 1969707A1 EP 06841242 A EP06841242 A EP 06841242A EP 06841242 A EP06841242 A EP 06841242A EP 1969707 A1 EP1969707 A1 EP 1969707A1
Authority
EP
European Patent Office
Prior art keywords
circuit arrangement
arrangement according
winding
voltage
switch
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP06841242A
Other languages
German (de)
English (en)
Inventor
Heribert Schmidt
Bruno Burger
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV
Original Assignee
Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV filed Critical Fraunhofer Gesellschaft zur Forderung der Angewandten Forschung eV
Publication of EP1969707A1 publication Critical patent/EP1969707A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/538—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a push-pull configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load
    • H02M1/007—Plural converter units in cascade
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0083—Converters characterised by their input or output configuration
    • H02M1/009—Converters characterised by their input or output configuration having two or more independently controlled outputs
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/483—Converters with outputs that each can have more than two voltages levels
    • H02M7/487—Neutral point clamped inverters

Definitions

  • the invention relates to a circuit arrangement for generating an alternating voltage or an alternating current according to the preamble of the main claim.
  • Transformerless concepts are also known, e.g. from DE 196 42 522 C1 and DE 197 32 218 Cl, in which a connection of the solar generator is fixedly connected to the neutral conductor and thus has a fixed potential relative to ground potential.
  • no leakage currents can flow in these known circuit arrangements even with arbitrarily high leakage capacitances.
  • These single-phase inverters require a buffer capacitor located at the input of the inverter to cover the entire input voltage range. This design is therefore not optimal and costly.
  • Neutral is connected to the mains and supplies a DC link with two buffering capacitors, which is bipolar with respect to the neutral conductor. Since the output voltage of the solar generator directly forms the positive intermediate circuit voltage in relation to the potential of the neutral conductor, only solar generator voltages greater than 350 V can be used, for example at 230 V mains voltage, which is a considerable limitation in practice.
  • the invention is therefore an object of the invention to provide a circuit arrangement for generating an alternating voltage or an alternating current from a grounded, unipolar voltage, ie a Gleichwoodsquel- Ie, which is firmly connected to the neutral, to provide a high efficiency, based on simple , cost-effective, reliable and controllable easily controlled structures based and an input voltage range both below and above the mains voltage amplitude
  • the concept consists of a converter stage which controls the input voltage, i. the voltage provided by a DC voltage source, such as a solar generator, into a bipolar DC link voltage of e.g. +/- 350 V, which is stored in a capacitor, and an inverter, which generates an alternating current from this bipolar intermediate circuit voltage, which can then be fed into the grid.
  • the DC voltage source i. The solar generator is connected to a connection fixed to the neutral conductor.
  • An advantage of this concept is the decoupling of the input side from the output side via the regulated voltage DC link. Furthermore, the lies in a single-phase feeding inverter for caching energy required capacitor, in the present invention, the two intermediate circuit capacitors, on a high and independent of the input voltage level and can be optimized to this voltage level and thus significantly cheaper.
  • the converter is designed as a choke converter having a clocked switch and two windings arranged in close coupling to each other, and in contrast to the prior art (DE 196 42 522 Cl and DE 197 32 218 Cl) designed only for the rated power of the inverter and not to the twice as high power occurring in the maximum of the output current, since energy can be stored in the voltage intermediate circuit.
  • Another advantage of this concept is that the input voltage can be both smaller and larger in magnitude than the voltage of the DC link capacitors, and thus energy sources with a wide voltage range can be connected.
  • the embodiment according to the invention also has the advantage that, for the energy stored in the double throttle, there is always inherently a freewheeling path via the associated freewheeling diodes into the high-capacitance intermediate circuit capacitors. This is necessary for safe shutdown in all operating states (emergency shutdown).
  • windings of the double choke are connected in such a way that one of the respectively assigned winding ends is supported on a resting coil. lie the potential (neutral conductor or intermediate circuit capacitor), and the other of the respectively associated winding ends have the same, offset by the amount of the DC link voltage waveform, and thus no cyclic transhipment of the coupling capacitances between the windings is necessary, resulting in lower peak currents at the switch S 0 occur and the efficiency and the EMC behavior can be improved.
  • the windings of the converter choke referred to as double choke have the same number of turns and are formed in close coupling with each other, as this induces the same voltage in both, so that ideally the two buffer capacitors or DC link capacitors without further balancing measures to the same Voltage to be charged.
  • the energy stored in the unavoidable leakage inductances of the double choke can be absorbed when the switch S 0 is opened and passed on to the intermediate circuit in the next clock section with virtually no loss.
  • a limiter circuit for limiting the voltage across the second winding of the double choke when switching the clocked switch having a coupling capacitor connected to the second winding and diodes connected to it.
  • the limiter circuit prevents in the interaction of the coupling capacitor with the diodes, the occurrence of harmful high voltages over the second
  • the windings are designed differently with respect to their turns, that is, the second winding has more turns, whereby the coupling capacitor can be kept small.
  • the obtained bipolar DC link voltage is converted via the known downstream inverter into a grid-compatible alternating current.
  • the circuit arrangement according to the invention can also be designed to be multi-phase, e.g. three-phase for feeding into the usual public three-phase network.
  • the invention is not limited to a solar generator as a DC voltage source, fuel cells, batteries or the like can be used.
  • Fig. 2 shows a second circuit-specific embodiment the invention
  • Fig. 5 shows a fifth circuit configuration of the invention
  • Fig. 6 is a sixth circuit configuration of the invention.
  • the circuit arrangement shown in Fig. 1 has a DC voltage source, which is in the embodiment, a solar generator 1, which lies with its terminals on a positive line 2 and a neutral or ground conductor 3.
  • This solar generator 1 supplies a DC input voltage U SG -
  • a capacitor C 0 is provided which buffers the input voltage U S Q.
  • a first winding Wi of a choke which is referred to as Dop- choke DRi
  • a control unit not shown switch S 0
  • the points on the windings Vl 1 , W 2 indicate in a known manner their winding beginnings.
  • the second winding W 2 of the double inductor DR x is connected to the beginning of the winding to the neutral conductor 3, wherein the winding end is connected to a first freewheeling diode D x, which is connected with its other terminal to a first storage capacitor Ci, the other Connection on the neutral conductor 3 is located.
  • a second freewheeling diode D 2 is connected, whose second terminal is connected to a second storage capacitor C 2 , the second terminal is also on the neutral conductor 3.
  • the double choke represents a transformer with energy storage properties, the galvanic separation is not used in the present case.
  • the winding W 1 is used twice to store the energy and to generate an inverted voltage related to the potential of the neutral conductor 3.
  • the winding W 2 is used to generate a reference to the neutral voltage with the same polarity as the input voltage. It is advantageous that the two DC link voltages +/- U WR amount can be both smaller and larger than the predetermined input voltage U SG .
  • the windings Wi and W 2 advantageously have the same number of turns and are wound in close coupling on a core, wherein they can also be wound bifilar.
  • the buffered input voltage U SG is applied to the first winding W x of the double choke DR x via the switch S 0 clocked, for example, at 16 kHz, whereby in the first clock phase, in which the switch S 0 is turned on, a time-increasing current in the winding Wi, connected to an energy storage in the magnetic circuit of the double choke DRi.
  • the second clock phase of the switch S 0 is opened and in the two windings W 1 and W 2 of the double choke OR 1 , a freewheeling voltage is induced such that via the diode Di a charging current in the capacitor d and at the same time via the diode D 2 a charging current flows into the capacitor C 2 .
  • the switches Si and S 2 of the half-bridge circuit are driven in a manner known per se according to a specific clock pattern (eg pulse width modulation, PWM) by a control circuit, not shown, and a mains supply can be made via the supply choke L x ,
  • PWM pulse width modulation
  • FIG. 2 shows a further embodiment of the inventive circuit arrangement of an inverter is shown with voltage intermediate circuit.
  • Circuit differs from the circuit arrangement of FIG. 1 in that a so-called three-point circuit is used as the inverter, which consists of two series-connected switches Si, S 3 and S 2 , S 4 , wherein between the connection point of the switch Si and S 3, a freewheeling diode D 3 is connected, which lies with its second terminal on the neutral conductor 3, while the connection point between the switches S 4 and S 2 is connected via a freewheeling diode D 4 to the neutral conductor 3.
  • the feed throttle L 1 is located with its one
  • the three-point circuit according to FIG. 2 allows three switching states.
  • S 3 is permanently closed, S 1 is clocked with eg 16 kHz and the switches S 2 and S 4 remain open.
  • switch S 1 is closed, the voltage + U WR is at the input of the inductor Li and a current builds up. After opening S 1 , the current continues to flow through the diode D 3 and the closed switch S 3 .
  • the voltage drop across them would be zero volts, corresponding to the input voltage at the inductor Li.
  • the switches S 2 and S 4 are used accordingly.
  • the illustrated inverter circuit furthermore has the advantage that semiconductors with a lower dielectric strength and thus better electrical properties can be used.
  • the disadvantage, however, is that the current must always flow through at least two semiconductors.
  • Fig. 3 is another advantageous embodiment Example of a circuit arrangement which, like that in Fig. 1 consists of a half-bridge with the switches Si and S 2 and the downstream inductor Li, but differs in that additional freewheeling branches between the connection point between the switches S 1 and S 2 and the Neutral conductor 3 are provided, which consist of a switch S 3 and a diode D 3 and a diode D 4 and a switch S 4 . Also, this circuit allows like that of FIG. 2, three switching states with the stated advantages. The same function of the additional freewheeling path here meet the switch S 3 , S 4 , together with the diodes D 3 , D 4 . In the positive half wave S 3 is permanently closed, corresponding to S 4 in the negative half.
  • the advantage over the circuit of Fig. 2 is that in the construction phase of the current, in which, for example, switch S 1 is closed, the current only through a switch, ie Si must flow, whereby the efficiency compared to the circuit of FIG. 2 increased.
  • Fig. 3 a dashed line between the two freewheel paths is shown.
  • so-called co-packs are used as electronic switches in which an IGBT, eg switch S 3 with a free-wheeling diode, for example diode D 4 , are connected in a common housing.
  • IGBT eg switch S 3 with a free-wheeling diode, for example diode D 4
  • switches With two such commercially available components can then build the desired switch / diode combination.
  • MOS-FETs are used as switches - here take over the inherent in MOS-FETs body diodes the function of freewheeling diodes.
  • FIG. 4 differs from the exemplary embodiment according to FIG. 3 in that the sequence within the series connection of the winding W 2 of the double choke DRi and the freewheeling diode D 1 is reversed.
  • the freewheeling diode D 1 is connected with its one terminal to the neutral conductor 3 and with its other terminal at the winding start of the winding W 2 , whose other terminal is connected to the capacitor C 1 .
  • a capacitor C 3 is in each case connected to the winding start of the winding W 1 and the winding start of the winding W 2 .
  • the operation is as previously described, ie, the general function remains unchanged.
  • both winding ends of the windings W 1 , W 2 are at rest, ie at the reference potential, which is predetermined by the neutral conductor 3, or at the intermediate circuit voltage + U WR applied to the DC link capacitor C 1 .
  • the two winding starts thus have the same, to the height of the intermediate circuit voltage + U WR offset temporal voltage curve to each other.
  • the two windings W 1 , W 2 can be wound very closely adjacent to each other, for example as a bifilar winding, since the forming between the two windings parasitic coupling capacitance does not have to be reloaded in each clock. From the spatially tight structure results in a very good magnetic coupling of the windings W 1 , W 2 and thus a low leakage inductance, improved EMC behavior, and lower switching losses in the switch S 0 .
  • the coupling capacitor C 3 has the task of absorbing the energies stored in the leakage inductances and of ensuring a balance between the two intermediate circuits.
  • the capacitor must be designed to be relatively large, for example, several 100 uF in a 5 kW device.
  • a compromise with respect to a smaller capacitor would be to make the number of turns of the windings W x and W 2 is not exactly equal, but the winding W 2 to give a slightly higher number of turns.
  • the voltage at the intermediate circuit capacitor Ci would be somewhat excessive, and at full power both would agree well and at full power, the negative intermediate circuit capacitor C 2 would be fed additionally from the leakage inductance of the first winding Wi, so that its voltage would be slightly above that of Ci would.
  • a clock-frequency AC voltage is then applied to the coupling capacitor C 3 , connected to undesirable currents through C 3 and through all the surrounding components.
  • a coupling capacitor C 3 between second winding W 2 and associated freewheeling diode Di connected wherein the other terminal of C 3 is connected to a first and second diode D 6 and D 7 .
  • D 7 lies with its other terminal at the negative DC link voltage -U WR and D 6 is connected to a further capacitor C 4 , which is applied to the positive line 2 or to the corresponding terminal of the clocked switch S 0 .
  • a third diode D 5 is connected, which lies with its cathode at the connection point between switch S 0 and the first winding W 1 .
  • a freewheeling diode D 0 is provided, which may be present in the other embodiments.
  • Capacitor C3 no longer has the task (see FIG. 4) of holding the two intermediate-circuit capacitors together in terms of voltage. Rather, it prevents in conjunction with the diodes D 5 , D 6 , D 7, the occurrence of harmful high voltages across the diode Dl due to transients at the winding W 2 when switching the switch S 0 .
  • the coupling capacitor C 3 is charged on average to the positive intermediate circuit voltage + U WR .
  • the switch S 0 is closed, the beginning of the winding W 2 is at the voltage (U SG + U WR ). If overshoots occur, the diodes D 0 , D 5 and D 6 become conductive and limit the voltage at the second winding W 2 . If only this elementary important limiter function can be realized, then the third diode D 5 and the capacitor C 4 can be dispensed with.
  • the capacitor C 4 is charged to the sum of the input voltage U SG and the negative intermediate circuit voltage -U WR .
  • the switch S 0 is turned on, the energy stored in the capacitor C 4 is fed back to the input circuit virtually loss-free, by means of the second winding W 2 , the coupling capacitor C 3 and the first diode D 6 until a recharging current flows through
  • Capacitor C 4 is completely discharged again. Another reloading is prevented via the diodes D 5 and D 0 .
  • select C 3 >> C 4 but this is anyway due to the double function of C 3 .
  • the circuits according to FIGS. 1 to 5 can be constructed, also complementary.
  • FIG. 6 shows by way of example the complementary construction of the circuit according to FIG. 4.
  • the positive terminal of the DC voltage source 1, ie the solar generator, is located on the neutral conductor 3.
  • the switch S 0 is in the negative supply voltage line 6, which simplifies its control circuitry, especially when several parallel input stages are provided.
  • MOS-FETs or N-channel type IGBTs are preferably used as switches. N-channel transistors require a positive gate voltage of, for example, 15 V with respect to the emitter potential, for which an auxiliary voltage must be provided. If several transistors with their emitters are at the same potential, advantageously a common auxiliary voltage source can be used.
  • the input stage consisting of the capacitor C 0 , the switch S 0 , the double choke DRi, the freewheeling diodes D 1 , D 2 and the coupling capacitor C 3 may be provided in all embodiments, multiple times and a common intermediate circuit consisting of the DC link capacitors Ci, Dine C 2 .
  • the individual input stages can be connected to the input terminals connected to lines 2 and 3 or 3 and 6 and fed from the same source.
  • the associated switches S 0 are clocked with a time offset so that both at the input, ie at the respective capacitors Co and at the output, ie at the capacitors C 1 , C 2 , a uniform power flow results, resulting in a smaller one AC load of these capacitors.
  • a so-called master-slave operation is possible in which the individual input stages are switched on depending on the current power to be transmitted. As a result, the efficiency curve can be significantly improved, especially in the partial load range.
  • input stages can also have separate input terminals, which in turn can be connected to associated, also different solar generators or other DC voltage sources.
  • a solar generator is used as a DC power source.
  • fuel cells or batteries or the like may be provided.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)

Abstract

L'invention concerne une circuiterie permettant de générer une tension alternative ou un courant alternatif à partir d'une source de tension continue unipolaire par rapport à un conducteur neutre et comportant un onduleur. La source de tension continue est raccordée à un convertisseur qui transforme la tension unipolaire de la source de tension continue en une tension tampon bipolaire qui est stockée dans un circuit tampon (C1, C2) raccordé à l'onduleur. Le convertisseur comprend un commutateur cadencé (So) et une unité de conversion d'énergie conçue sous la forme d'une double bobine (DR1,DR2) constituée de deux enroulements (W1,W2) en couplage étroit.
EP06841242A 2005-12-23 2006-12-22 Circuiterie dotee d'une double bobine destinee a la generation d'une tension alternative ou d'un courant alternatif Withdrawn EP1969707A1 (fr)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
DE102005062845 2005-12-23
DE102006010954 2006-03-03
DE102006012164A DE102006012164B4 (de) 2005-12-23 2006-03-13 Schaltungsanordnung zur Erzeugung einer Wechselspannung oder eines Wechselstroms
PCT/EP2006/012650 WO2007073946A1 (fr) 2005-12-23 2006-12-22 Circuiterie dotee d'une double bobine destinee a la generation d'une tension alternative ou d'un courant alternatif

Publications (1)

Publication Number Publication Date
EP1969707A1 true EP1969707A1 (fr) 2008-09-17

Family

ID=38135880

Family Applications (1)

Application Number Title Priority Date Filing Date
EP06841242A Withdrawn EP1969707A1 (fr) 2005-12-23 2006-12-22 Circuiterie dotee d'une double bobine destinee a la generation d'une tension alternative ou d'un courant alternatif

Country Status (4)

Country Link
US (1) US8315076B2 (fr)
EP (1) EP1969707A1 (fr)
DE (1) DE102006012164B4 (fr)
WO (1) WO2007073946A1 (fr)

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US20090168467A1 (en) 2009-07-02
US8315076B2 (en) 2012-11-20
DE102006012164B4 (de) 2009-12-17
DE102006012164A1 (de) 2007-07-05
WO2007073946A1 (fr) 2007-07-05

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