EP1570290A2 - Detecteur radar et son mode de fonctionnement - Google Patents

Detecteur radar et son mode de fonctionnement

Info

Publication number
EP1570290A2
EP1570290A2 EP03779670A EP03779670A EP1570290A2 EP 1570290 A2 EP1570290 A2 EP 1570290A2 EP 03779670 A EP03779670 A EP 03779670A EP 03779670 A EP03779670 A EP 03779670A EP 1570290 A2 EP1570290 A2 EP 1570290A2
Authority
EP
European Patent Office
Prior art keywords
radar sensor
switch
pulse
sensor according
signal
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP03779670A
Other languages
German (de)
English (en)
Inventor
Dirk Steinbuch
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Robert Bosch GmbH
Original Assignee
Robert Bosch GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Robert Bosch GmbH filed Critical Robert Bosch GmbH
Publication of EP1570290A2 publication Critical patent/EP1570290A2/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/06—Systems determining position data of a target
    • G01S13/08—Systems for measuring distance only
    • G01S13/10—Systems for measuring distance only using transmission of interrupted, pulse modulated waves
    • G01S13/106—Systems for measuring distance only using transmission of interrupted, pulse modulated waves using transmission of pulses having some particular characteristics
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/0209—Systems with very large relative bandwidth, i.e. larger than 10 %, e.g. baseband, pulse, carrier-free, ultrawideband
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S13/00—Systems using the reflection or reradiation of radio waves, e.g. radar systems; Analogous systems using reflection or reradiation of waves whose nature or wavelength is irrelevant or unspecified
    • G01S13/02—Systems using reflection of radio waves, e.g. primary radar systems; Analogous systems
    • G01S13/06—Systems determining position data of a target
    • G01S13/08—Systems for measuring distance only
    • G01S13/10—Systems for measuring distance only using transmission of interrupted, pulse modulated waves
    • G01S13/26—Systems for measuring distance only using transmission of interrupted, pulse modulated waves wherein the transmitted pulses use a frequency- or phase-modulated carrier wave
    • G01S13/28—Systems for measuring distance only using transmission of interrupted, pulse modulated waves wherein the transmitted pulses use a frequency- or phase-modulated carrier wave with time compression of received pulses
    • G01S13/282—Systems for measuring distance only using transmission of interrupted, pulse modulated waves wherein the transmitted pulses use a frequency- or phase-modulated carrier wave with time compression of received pulses using a frequency modulated carrier wave
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/03—Details of HF subsystems specially adapted therefor, e.g. common to transmitter and receiver
    • G01S7/032—Constructional details for solid-state radar subsystems
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/28—Details of pulse systems
    • G01S7/282—Transmitters
    • G—PHYSICS
    • G01—MEASURING; TESTING
    • G01S—RADIO DIRECTION-FINDING; RADIO NAVIGATION; DETERMINING DISTANCE OR VELOCITY BY USE OF RADIO WAVES; LOCATING OR PRESENCE-DETECTING BY USE OF THE REFLECTION OR RERADIATION OF RADIO WAVES; ANALOGOUS ARRANGEMENTS USING OTHER WAVES
    • G01S7/00—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00
    • G01S7/02—Details of systems according to groups G01S13/00, G01S15/00, G01S17/00 of systems according to group G01S13/00
    • G01S7/28—Details of pulse systems
    • G01S7/285—Receivers

Definitions

  • the invention is based on a method for operating a radar sensor, the radar pulses of which are generated by passing a continuous microwave signal over an RF switch that is periodically controlled by a pulse signal.
  • the mixed received pulses are fed on the one hand to an amplitude detector for obtaining a range signal and on the other hand to a phase detector for obtaining an angular error signal.
  • Pulse signal expanded without decorrelation occurring. This causes that After mixing the radar signal in IF position regardless of frequency drifts, the same high noise level always occurs on the receiving side, which almost corresponds to the minimum achievable noise level regardless of the relative position of the LO (carrier oscillator) frequency and PRF (pulse repetition frequency) to one another. This avoids the critical case of f _o n * PRF.
  • SRR short-range radar
  • diodes with a linear characteristic e.g. PIN diodes as HF switches also reduce the harmonics.
  • the required fast switching times with the SRR, e.g. 400 ps for radar pulses, can be achieved with very thin pin diodes
  • Intrinsic layer can be achieved.
  • phase detector can advantageously have a pair of diodes on one
  • an oscillator for controlling the RF switch is advantageous, which oscillates in a clean mode and has a buffer amplifier operated on the output side in saturation.
  • FIG. 1 shows a basic circuit diagram of a radar sensor according to the invention
  • FIG. 2 shows the spectral relationship between the baseband pulse spectrum and the reception pulse spectrum
  • FIGS. 3 and 4 the demodulation of the phase noise of the baseband pulse spectral line with the neighboring received pulse spectral line within the IF bandwidth.
  • FIG. 5 shows the power of a baseband pulse spectral line over the RF pulse width with and without modulation of the pulse signal for controlling the transmitter-side RF switch
  • FIG. 6 shows the transmitter-side RF switch with pulse shaping
  • Figure 7 shows the performance of a baseband spectral line across the RF pulse width with and without
  • FIG. 8 the noise figure over the HF pulse width with Schottky and PIN diodes
  • FIG. 9 shows a layout for a phase detector
  • FIG. 10 shows the noise figure over the RF pulse width with different sources
  • an oscillator 3 for microwave signals which delivers a continuous high-frequency signal (CW signal). Via a signal divider in the form of the hybrid circuit 4, this high-frequency signal reaches the input of a transmitter-side RF switch 1 for emitting radar pulses to the transmitter antenna 5 on the one hand, and a receiver-side RF switch 2, on the other hand, which controls a receive mixer 7 in the signal path to a receive antenna 8 ,
  • the control of the transmitter-side RF switch 1 takes place via the control device 9, which has a pulse signal source 10 and a delay circuit 11. If the pulse signal source 10 supplies a pulse, the RF switch 1 receives the high-frequency wave of the oscillator 3 for the duration of this pulse to the transmitting antenna.
  • the echo signal reflected from an object arrives at the mixer 7, which receives a reference signal via the switch 2 when the delay circuit 11 is set in accordance with a desired time gate for a certain distance in which objects are to be detected. If the same high-frequency sources are present at both inputs of the mixer 7, an IF output signal is generated which is proportional to the coincidence and is further processed in an evaluation circuit 12.
  • the SRR system is operated, for example, with a pulse repetition frequency PRF for the pulse signal source 10 of typically 5 MHz, which means that a pulse is emitted every 200 ns.
  • the PRF is derived from a very pure quartz and has little phase noise.
  • the drive pulse, hereinafter referred to as baseband pulse, for the RF switches has a width of 400 ps.
  • the spectrum of the baseband pulse corresponds to the Fourier transform of the pulse in the time domain and has a sin (x) / x-like shape around 0 Hz with spectral lines that are spaced apart from the pulse repetition frequency.
  • the HF switch 1 works unintentionally as a harmonic multiplier for the baseband pulse, since the switch output is not band-limited. The spectral lines of the baseband pulse are thus multiplied beyond 24.125 GHz.
  • the baseband pulse spectral lines are extremely widened, ie have very high phase noise around 24.125 GHz, although they are derived from a very pure source.
  • frequency modulation (PRF modulation) of the pulse signal for controlling the RF switch 1 is carried out according to the invention used by means of the modulator stage 20, which independent of frequency drifts ensures that the same high noise level always occurs at the IF output, which corresponds almost to the minimum achievable noise level.
  • the PRF is frequency modulated, with the frequency deviation eg 1kHz and the modulation frequency eg Is 10 kHz.
  • the low modulation index of 0.1 ensures that the radar signal does not decorrelate itself.
  • the modulation index is also multiplied by the harmonic multiplication, in order to get from 5 MHz to 24.125 GHz, for example, a factor of 4850 is necessary.
  • n * PRF compared to the HF
  • This flatness therefore results in a constant noise figure that almost corresponds to the optimal noise figure with an optimal frequency offset.
  • FIG. 2 shows the spectral relationship between the baseband pulse spectrum and the received pulse spectrum, that is to say the baseband pulse spectrum 13 and the LO spectrum 14 modulated with the carrier.
  • FIGS. 3 and 4 show enlarged how the phase noise of the baseband pulse spectral line with the adjacent receive pulse spectrum.
  • the baseband pulse spectral lines have an extreme phase noise
  • this phase noise is demodulated by the spectral lines of the received pulse. This phenomenon occurs with every pair of spectral lines and adds up uncorrelated.
  • This demodulated signal has a noise character and increases the IF noise and thus the system noise figure.
  • the noise figure can be further reduced by lowering the harmonics of the baseband pulse by 24 GHz.
  • the performance of the harmonics of the baseband pulse around 24 GHz does not depend on the baseband pulse width, but rather on the slope of the pulses.
  • Appropriate pulse shaping can reduce the slope and thus lower the harmonics.
  • One proposal is low-pass filtering, which can be achieved, for example, by a 10 pF capacitor at the input of the RF switch 1.
  • Another option is Use of a Gaussian filter or other filter for more precise pulse shaping and more targeted lowering of the harmonics and thus improvement of the noise figure.
  • Figure 6 shows a possible implementation of a
  • the HF switch 1 shown in FIG. 6 has a capacitor 23 for pulse shaping (low pass) between the control input 21 for the frequency-modulated baseband pulse in particular and the ground connection 22.
  • the baseband pulse arrives after a ⁇ / 4 transformation 29 on a pair of diodes 24, 25, which is connected on the one hand to ground 28 and, on the other hand, via blocking circuits 26, 27 for a baseband pulse in the form of finger couplers, the output signal of the oscillator 3 present at the input 30 during the Switching state connects with the transmitting antenna 5 via output 31.
  • the transform circuits 32 and 33 form RF short circuits.
  • the switch 1 is strictly symmetrical except for the secondary branch in the form of the capacitor 23. This makes it possible
  • Insulation strength (switch-through state / blocking state) of 50 dB.
  • FIG. 7 shows the measurement results of the baseband pulse spectral line at 24.125 GHz: power / dBm over the pulse width / ps with (reference numeral 24) and without (25) pulse shaping.
  • the phase noise generated by the baseband spectral lines can be reduced by reducing the harmonics of the baseband pulse by 24 GHz.
  • These harmonics are generated in the RF switch 1, for example by two Schottky diodes. These diodes are preferred because they switch very quickly due to the Schottky metal layer. However, they have an extremely non-linear characteristic, which makes them ideal for mixer applications. This non-linearity is very negative for the switch because this characteristic enables the harmonics of the baseband pulse to be generated so effectively.
  • diodes with a linear characteristic such as PIN diodes used. These diodes generate harmonics that are 10 dB lower and produce a rapid number which, depending on the pulse shape, is also lower by this order of magnitude. The problem of the inertia of these diodes in relation to the very fast pulse of 400 ps
  • FIG. 8 shows the reduction in the noise figure due to the use of PIN diodes (reference number 34) in comparison to Schottky diodes (reference number 35).
  • the previously presented SRR system with a pulse repetition frequency of typically 5 MHz and an RF pulse width of typically 400 ps has an output spectrum of the reception switch, which is around the carrier frequency of e.g. 24.125 GHz is centered, and consists of strung spectral lines at a distance from the pulse repetition frequency and has a shape that corresponds to the Fourier transform of the RF pulse. Each individual spectral line has emerged from the carrier and therefore has its amplitude and phase noise.
  • This spectrum is fed into the phase detector or the reception mixer 7.
  • a simply balanced phase detector theoretically provides perfect AM suppression, i.e. amplitude noise of the local oscillator signal is canceled out in phase opposition. Real at a frequency of e.g. 24 GHz to reach approx. 20 dB.
  • the phase detector can thus function as a poor AM demodulator. Because there is a large number of spectral lines, the individually demodulated amplitude noise is added in a correlated manner and manifests itself in an increased noise level at the IF output and thus results in an increased noise figure.
  • the noise figure can be reduced by improving the balance of the phase detector.
  • the phase detector For this purpose, not two physically separate diodes ' are used, but two diode junctions (diode pair 37, 38) on a chip which, according to FIG. 9, is placed in the middle inside and not outside of the ring mixer 39. This has the advantage that the diode junctions are almost identical and therefore different the balance improves.
  • the use of an alternative phase detector, eg double balanced, with improved AM suppression is also advantageous.
  • the amplitude noise can be seen in FIGS. 2 to 4.
  • FIG. 10 shows the system noise figure with two different oscillators, a DRO (reference number 41) and a Gunn oscillator with 10 dB less noise (reference number 40). The noise figure can be reduced by a few dB.

Landscapes

  • Engineering & Computer Science (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Remote Sensing (AREA)
  • Computer Networks & Wireless Communication (AREA)
  • Physics & Mathematics (AREA)
  • General Physics & Mathematics (AREA)
  • Radar Systems Or Details Thereof (AREA)

Abstract

L'invention concerne un détecteur radar. Un signal hyperfréquence continu est cédé par un commutateur HF (1) qui est commandé périodiquement par un signal impulsionnel. Ce signal impulsionnel est modulé en fréquence (20) de telle façon que le spectre du signal impulsionnel soit élargi mais qu'aucune décorrélation n'apparaisse. Cette mesure permet de maintenir un faible niveau de bruit, ce qui augmente la plage de détection.
EP03779670A 2002-12-03 2003-10-27 Detecteur radar et son mode de fonctionnement Withdrawn EP1570290A2 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
DE10256330 2002-12-03
DE10256330A DE10256330A1 (de) 2002-12-03 2002-12-03 Radarsensor sowie Verfahren zum Betrieb eines Radarsensors
PCT/DE2003/003563 WO2004051305A2 (fr) 2002-12-03 2003-10-27 Detecteur radar et son mode de fonctionnement

Publications (1)

Publication Number Publication Date
EP1570290A2 true EP1570290A2 (fr) 2005-09-07

Family

ID=32335915

Family Applications (1)

Application Number Title Priority Date Filing Date
EP03779670A Withdrawn EP1570290A2 (fr) 2002-12-03 2003-10-27 Detecteur radar et son mode de fonctionnement

Country Status (4)

Country Link
US (1) US7304604B2 (fr)
EP (1) EP1570290A2 (fr)
DE (1) DE10256330A1 (fr)
WO (1) WO2004051305A2 (fr)

Families Citing this family (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE102005037960A1 (de) * 2005-08-11 2007-02-15 Robert Bosch Gmbh Radarsensor in Kompaktbauweise
DE102006032539A1 (de) * 2006-07-13 2008-01-17 Robert Bosch Gmbh FMCW-Radarsensor
EP2769235B1 (fr) * 2011-10-19 2023-11-29 Balu Subramanya Capteur de vitesse et de distance directionnel
US11004337B2 (en) 2012-12-28 2021-05-11 Balu Subramanya Advanced parking management system

Family Cites Families (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4427982A (en) * 1981-04-28 1984-01-24 The United States Of America As Represented By The Secretary Of The Navy Radar clutter reduction by use of frequency-diverse, wideband pulse-compression waveforms
US6067040A (en) * 1997-05-30 2000-05-23 The Whitaker Corporation Low cost-high resolution radar for commercial and industrial applications
DE19963005A1 (de) * 1999-12-24 2001-06-28 Bosch Gmbh Robert Verfahren und Vorrichtung zur Erfassung und Auswertung von Objekten im Umgebungsbereich eines Fahrzeuges
DE10100416A1 (de) * 2001-01-08 2002-07-11 Bosch Gmbh Robert Radareinrichtung und Verfahren zum Unterdrücken von Störungen einer Radareinrichtung
JP2005265461A (ja) * 2004-03-16 2005-09-29 Fujitsu Ten Ltd レーダ装置

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO2004051305A3 *

Also Published As

Publication number Publication date
US7304604B2 (en) 2007-12-04
WO2004051305A2 (fr) 2004-06-17
US20060125683A1 (en) 2006-06-15
WO2004051305A3 (fr) 2004-09-16
DE10256330A1 (de) 2004-06-24

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