EP1529336A1 - Convertisseur de commutation - Google Patents

Convertisseur de commutation

Info

Publication number
EP1529336A1
EP1529336A1 EP03735143A EP03735143A EP1529336A1 EP 1529336 A1 EP1529336 A1 EP 1529336A1 EP 03735143 A EP03735143 A EP 03735143A EP 03735143 A EP03735143 A EP 03735143A EP 1529336 A1 EP1529336 A1 EP 1529336A1
Authority
EP
European Patent Office
Prior art keywords
primary
switch
switches
switching
ast
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP03735143A
Other languages
German (de)
English (en)
Inventor
Harald Schweigert
Stefan Gut
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Siemens AG
Original Assignee
Siemens AG Oesterreich
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Siemens AG Oesterreich filed Critical Siemens AG Oesterreich
Publication of EP1529336A1 publication Critical patent/EP1529336A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the invention relates to a switching converter with a transformer, which has at least one primary winding and at least one secondary winding, with at least one controlled primary switch via which a DC input voltage can be periodically and with a predefined pulse duty factor and / or predeterminable frequency to the at least one primary winding, and with at least one controlled synchronous switch for synchronous rectification assigned to the at least one secondary winding.
  • a switching converter of this type can be seen, for example, from EP 1 148 624 AI.
  • the switching converters disclosed in this document are designed as flux or flyback converters, the switch or switches controlled on the primary side being controlled by a conventional control circuit with pulse width modulation.
  • Synchronous rectification on the secondary side of switching converters usually using osf ets, has the advantage of lower losses, since the forward flow resistances of Mosfets, for example, are lower than with conventional diodes.
  • osf ets since the forward flow resistances of Mosfets, for example, are lower than with conventional diodes.
  • the voltage capability of the rectifier diodes or switching elements in practice must be between 150 200 V, which is primarily due to the transformer ratio and the input (mains) voltage range, generally due to voltage peaks and / or overvoltages.
  • the body diodes inherent in a Mosfet are significantly slower in Mosfets with reverse voltages of 150 to 200 V than in Mosfets with only 50 V reverse voltages; more precisely, the blocking delay times are at least 200 ns in the first case and at least 80 ns in the second case.
  • conventional rectifier diodes with a blocking voltage of 200 V achieve blocking delay times of 35 ns.
  • the resulting short-circuit current magnetizes the stray inductance of the transformer and generates a high-energy overvoltage pulse after the commutation process, which is either stored in a special voltage-limiting network or in the winding capacities of the transformer windings and converted into heat when the primary transistor or the primary transistors are switched on.
  • the control of secondary-side synchronous rectifiers uses a secondary-side digital signal processor to control the synchronous switch or switches, the control pulses required for the signal processor being derived from the secondary voltage of the transformer.
  • a switching converter of the type specified at the outset in which, according to the invention, a common control for the primary and the secondary side is provided with a digital signal processor which, derived from a common clock generator, both the switching pulses for the at least one primary switch and that for the at least one synchronous switch.
  • the invention shows particular advantages if the at least one secondary-side synchronous switch is designed as a MOSFET, since the presence of the body diodes can be taken into account particularly well here.
  • a current sensor is provided in the primary circuit for supplying information to the control circuit.
  • control circuit is set up to control the secondary switches close in front of the primary switches. This enables voltage-free switching, protects the controlled switches from dangerous overvoltages and allows the use of switches with lower dielectric strength.
  • control circuit is set up to control the primary and secondary switches in the sense of energy recovery.
  • control circuit is set up to control the primary and secondary switches in the sense of an alternation of the power between the primary and the secondary side in order to maintain auxiliary supply voltages. This enables a supply of the control circuit or other auxiliary circuits to be guaranteed, in particular when idling, which is always a critical operating state in the case of switching converters.
  • control circuit is set up to store the delay times between its switching commands and the switching of the respective controlled switches and to take them into account in the control sequence.
  • control circuit is at a single potential level, the primary and / or secondary switches being controlled separately, the control circuit can be constructed more simply. For example, if several processors are used, no opto-bus is required to communicate with them.
  • FIG. 1 is a simplified circuit diagram of a first embodiment of a switching converter according to the invention
  • FIG. 3 shows a simplified representation of the basic circuit diagram of a variant of the invention designed as a flyback converter
  • FIG. 4 shows a basic circuit diagram of a variant of the invention in push-pull circuit
  • Fig. 5 in a block diagram, a possibility of floating control of the circuit breaker
  • Fig. 6 is a logic flow diagram of the switch control.
  • an input DC voltage UE which is here connected to a capacitor CZK, is fed symmetrically to the primary winding WP of a transformer UET via two controlled primary switches SP1, SP2.
  • the input DC voltage UA for example in the case of switching power supplies, can be an intermediate circuit voltage obtained by rectifying a 230/400 V mains voltage.
  • the controlled primary switches SP1, SP2 are Mosfets with integrated body diodes, the double and symmetrical arrangement of these switches halving the required blocking voltage values - compared to the use of only one primary switch.
  • two demagnetizing diodes D1, D2 are provided, which bridge the path WP-SPl or WP-SP2.
  • a primary sensor resistor Rp or another current sensor is arranged in the primary circuit, which provides information about the primary current profile.
  • two controlled synchronous switches SSI, SS2 are provided, namely a first synchronous switch SSI after the secondary winding WS in the series branch and a second synchronous switch SS2 subsequently in the transverse branch.
  • the first synchronous switch SSI which could also be in the positive branch, works as a synchronous rectifier
  • the second controlled switch as a freewheeling switch.
  • a series inductor LS, followed by a capacitor Cs, on which the output voltage UA is applied, complete the flux converter. If the leakage inductance of the transformer is not too great, it can also be demagnetized via the winding capacitance and the demagnetizing diodes D1, D2 can be omitted. In this case, a switch-on time longer than 50% of the period is possible.
  • a series resistor Rs is provided as a current sensor in the negative branch of the secondary side. If necessary, the current sensor could also be on the primary side.
  • a control circuit AST is provided for controlling all controlled switches, which core contains a digital processor DSP, but also the driver stages required for direct control of the switches, etc.
  • the control circuit also includes the actual values of the input current IE, the output current I A and the output voltage UA supplied to be compared with stored or predetermined setpoints.
  • the duty cycle nis the pulse width modulated control of the primary switch SPl, SP2 determined. This duty cycle always remains less than 1: 1 because of the time required for the demagnetization.
  • the voltage supply of the control circuit AST is not shown in detail, it can take place from the intermediate circuit voltage or during operation via an auxiliary winding of the transformer. A number of variants are known to the person skilled in the art for this.
  • processor DSP is not necessarily to be understood as a physical unity, but that, for example, several microprocessors which are connected via a common data bus can implement such a digital processor.
  • the individual lines of FIG. 2 contain a complete period of activation, the activation signals for the controlled switches SP1, SP2 (primary) and SSI, SS2 (secondary) being shown in the first four lines, whereas the fifth line shows that approximate course of the magnetizing current i m . Marked and essential points in time for the course of the activation within a period are denoted by tl to ⁇ 7.
  • the freewheeling current driven by the series inductor LS is divided between the synchronous switches SSI and SS2.
  • a complete transfer of the entire freewheeling current to the synchronous switch SS2 then takes place during the period (t2 - tl).
  • the current commutates by switching off the MOS channel because of the high forward voltage of the body diode of the synchronous switch SS2 and because of the low-resistance secondary winding WS to the already switched on synchronous switch SSI.
  • the primary switch SP2 switches off, as a result of which the magnetizing current and the current in the primary leakage inductance are short-circuited via the primary switch SP1 and the diode Dl. Therefore, the voltage on all windings collapses to almost zero volts, with the currents remaining upright.
  • the freewheeling synchronous switch SS2 is switched on and only to ensure that the current can commutate. Because of the primary short circuit, the secondary winding WS of the transformer prevents the current from being passed on via the rectifier synchronous switch SSI and the current commutates to the freewheeling synchronous switch SS4.
  • the primary switch SPl is also switched off and the end magnetization of the transformer UET takes place via the demagnetizing diodes Dl and D2, this end magnetization having to be completed before the time tl of the next period.
  • the switching times primary and secondary can in principle be selected completely independently of one another.
  • This option will of course be used in such a way that as far as possible no unwanted short circuits or overvoltages occur during the entire switching sequence.
  • the “step-by-step” switching of the switches, as shown in FIG. 2, can also be implemented without problems thanks to the invention.
  • Fig. 2 relates to a stationary operating state, but it must be clear that the switching times or the delay or the shifting of the switching times can be dynamically adapted to different operating conditions, e.g. fluctuations in the input voltage or load fluctuations and / or temperature fluctuations etc.
  • the control circuit can be implemented using microprocessors, the applicant achieving good results, for example, with the following microprocessors: Texas Instruments, TMS 320LF2406A, 40 Mips / 40 MHz / 2.5 k RAM / 32 k Flash, 16 PWM channels, 16 ADC or Motorola DSP56F803, 64 k-Flash / 4 k-RAM, 6 PWM channels 8 ACD.
  • the entire drive circuit AST is drawn as a single block, but it should be clear to the person skilled in the art that there is also a division here different blocks can be made without changing the overall concept of independent control.
  • a digital signal processor DSP of the control circuit supplies the control pulses for a controlled switch via a driver TR1 to the galvanically isolating transformer TRF.
  • An auxiliary supply HVS can supply the driver TR1.
  • a box SIG for the signal and a box ESP for an energy store there is a separation of signal and energy, represented by a box SIG for the signal and a box ESP for an energy store.
  • Another driver TR2 is now supplied with the signal on the one hand and the required energy on the other hand and the driver controls a controlled switch GES.
  • the invention enables energy to be fed back from the secondary side to the primary side without additional hardware expenditure by suitably changing the control pulses of the switches.
  • the secondary synchronous switch SS2 is switched on, which results in a negative current through the inductance LS.
  • this current is conducted through the secondary winding WS of the transformer UET.
  • the capacitor CZK is recharged via the body diodes of the uncontrolled primary switches SP1 and SP2, the secondary inductance LS or choke acting as a step-up converter.
  • Such a regeneration makes it possible, for example, to maintain a primary and / or secondary auxiliary supply by feeding energy back and forth.
  • the transformer is always activated and additional auxiliary windings, not shown here, but already mentioned above, continue to be supplied. This is particularly interesting when the engine is idling, when all the pulses are de facto stopped when the output voltage is reached and no load is connected.
  • the aforementioned feedback can also be provided, for example, for a targeted discharge of a battery provided on the secondary side or for supplying the intermediate circuit (input voltage UE) in an emergency.
  • FIG. 3 shows that the invention can also be applied to flyback converters. Comparable parts or sizes are given the same reference numerals as in FIG. 1.
  • the control circuit AST again receives information about the primary current IE and about the output current IA or the output voltage UA. Of course, other information, e.g. via the temperature, are also fed to the control circuit AST and this circuit also allows dynamic adaptation to operating conditions. Since there are no overvoltages in a flyback converter as in a forward converter, the main advantage of the invention lies in the possibility of compensating for the delay times. Energy recovery is also possible with a flyback converter.
  • the transformer UET here has a primary winding WP with center tap and two secondary windings WS1 and WS2.
  • the upper or lower half of the primary winding WP can be switched from the positive pole of the input voltage UE to ground via primary switches SPA, SPB.
  • controlled synchronous switches SSa and SSb can be used for two-way rectification, with another synchronous switch SSQ being used here as a freewheeling switch.
  • This switch which, like all other switches, can also be designed as a MOSFET, keeps the freewheeling current of the secondary inductance LS away from the transformer, so that it cannot heat it up.
  • the freewheeling synchronous switch SSQ requires a lower blocking voltage than the rectifier synchronous switches SSA and SSB, since it only has to block the blocking voltage of one of the two transformer windings WS1 or WS2 and it can therefore also be designed with a lower impedance. This also reduces the copper losses of the transformer or transformer, namely by around a third if the Freewheeling current through the synchronous switch SSQ.
  • the individual primary and secondary-side current and voltage sensors are not shown in FIG. 4, via which information about the actual state is supplied to the control circuit AST.
  • a variant of the invention in which a separate freewheeling synchronous switch SSQ, as in FIG. 4, is not required, can be implemented if the two secondary synchronous switches SSA and SSB are specifically controlled for freewheeling.
  • the freewheeling current then flows entirely through the secondary windings WS1 or WS2 of the transformer UET, but produces lower losses overall in the switches SSA and SSB, since there is a current distribution when the switches SSA and SSB are switched on, and accordingly a reduction in the power dissipation.
  • a start-up sequence for the primary transistors is defined and then the essential parameters, in particular the switching times, are transferred for a stable steady state.
  • the controlled period sequence then takes place, for example as shown in FIG. 2.
  • a setpoint / actual value comparison which can affect in particular the output voltage and the output current, but also the temperature, follows and the parameters can be changed accordingly.
  • the I-Limit which intervenes in the controlled period, denotes the defined limit for the primary current.
  • the auxiliary supplies are set up using a separate power supply unit or series regulator or auxiliary starting resistors.
  • the processor starts in the second phase, i.e. of his program, possibly with a self-test.
  • the third phase includes the control of the primary transistors.
  • the secondary transistors (switches) can only be activated later, since the rectification takes place via the body diodes first, if there are any. This enables a simpler program flow and the requirements for the performance of the processors (the processor) can be lower.
  • the fourth phase a stable operating state with a stable output voltage is reached. Now the secondary switches (Mosfets) are also controlled and the losses are reduced.
  • An important advantage that the invention offers is that the delay times of each individual control circuit can be taken into account to ensure optimal operation. For example, these delays in a test run when calibrating the assembly using the microprocessor . be measured yourself, and then considered in the program.
  • the level of the input voltage UE also has an influence on the switching speeds of the primary transistors, since the reaction of the drain-gate capacitance places a higher load on the gate control when the input voltage is higher and reduced the switching speed. Thus, the level of the input voltage can be taken into account when adjusting the circuit or taken into account during operation.
  • the delay times between the control circuit and the respective controlled switch can be taken into account.
  • These delay times are expediently stored in the control circuit for each of the individual branches - according to FIG. 1, for example four branches.
  • the delay times for each branch are generally different, which is due to the inevitable component tolerances as well as the tolerances, for example the gate capacitance in Mosfets.
  • the control or the digital signal processor can calculate and save the difference between a transmitted switching command and the actually implemented switching command via a separate input.
  • the digital processor DSP of the control circuit AST can also calculate the switch-on times exclusively digitally, in which case there are no currently generally common ramp generators that are only started by the processor. This solution offers a lot of flexibility, but the processor has to be clocked sufficiently quickly so that the necessary level of control can be achieved. In a practical exemplary embodiment with a switching power supply clock frequency of 50 kHz, the processor has 25ns steps.

Abstract

L'invention concerne un convertisseur de commutation comportant un translateur (UET), qui présente au moins un enroulement primaire (WP) et au moins un enroulement secondaire (WS), ainsi qu'au moins un commutateur primaire (SP1, SP2) régulé, par l'intermédiaire duquel une tension continue d'entrée (UE) peut être appliquée, périodiquement et avec un facteur d'utilisation des impulsions prédéfinissable et/ou une fréquence prédéfinissable, à l'enroulement primaire (au moins au nombre de un), de même qu'au moins un commutateur synchrone (SS1, SS2) régulé, associé à l'enroulement secondaire (au moins au nombre de un), en vue d'un redressement synchrone. Un circuit d'attaque (AST) commun côté primaire et côté secondaire est muni d'un processeur numérique (DSP) qui, dérivé d'un générateur de rythme d'horloge (CLK) commun, produit aussi bien les impulsions de commutation pour le commutateur primaire (SP1, SP2) (au moins au nombre de un) que celles requises pour le commutateur synchrone (SS1, SS2) (au moins au nombre de un).
EP03735143A 2002-08-12 2003-06-23 Convertisseur de commutation Withdrawn EP1529336A1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
AT0121802A AT413908B (de) 2002-08-12 2002-08-12 Schaltwandler
AT12182002 2002-08-12
PCT/AT2003/000175 WO2004015850A1 (fr) 2002-08-12 2003-06-23 Convertisseur de commutation

Publications (1)

Publication Number Publication Date
EP1529336A1 true EP1529336A1 (fr) 2005-05-11

Family

ID=31499793

Family Applications (1)

Application Number Title Priority Date Filing Date
EP03735143A Withdrawn EP1529336A1 (fr) 2002-08-12 2003-06-23 Convertisseur de commutation

Country Status (5)

Country Link
US (1) US20050152158A1 (fr)
EP (1) EP1529336A1 (fr)
CN (1) CN100389536C (fr)
AT (1) AT413908B (fr)
WO (1) WO2004015850A1 (fr)

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Also Published As

Publication number Publication date
CN1675821A (zh) 2005-09-28
CN100389536C (zh) 2008-05-21
ATA12182002A (de) 2005-10-15
US20050152158A1 (en) 2005-07-14
WO2004015850A1 (fr) 2004-02-19
AT413908B (de) 2006-07-15

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