EP1275203A1 - Circuit pour reduire les pertes de commutation de soupapes electroniques - Google Patents

Circuit pour reduire les pertes de commutation de soupapes electroniques

Info

Publication number
EP1275203A1
EP1275203A1 EP01923373A EP01923373A EP1275203A1 EP 1275203 A1 EP1275203 A1 EP 1275203A1 EP 01923373 A EP01923373 A EP 01923373A EP 01923373 A EP01923373 A EP 01923373A EP 1275203 A1 EP1275203 A1 EP 1275203A1
Authority
EP
European Patent Office
Prior art keywords
electronic
valve
losses
saturation
switch
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP01923373A
Other languages
German (de)
English (en)
Inventor
Wolfgang Croce
Günther Danhofer
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Individual
Original Assignee
Individual
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Individual filed Critical Individual
Publication of EP1275203A1 publication Critical patent/EP1275203A1/fr
Withdrawn legal-status Critical Current

Links

Classifications

    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03K—PULSE TECHNIQUE
    • H03K17/00—Electronic switching or gating, i.e. not by contact-making and –breaking
    • H03K17/08—Modifications for protecting switching circuit against overcurrent or overvoltage
    • H03K17/081—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit
    • H03K17/0814—Modifications for protecting switching circuit against overcurrent or overvoltage without feedback from the output circuit to the control circuit by measures taken in the output circuit

Definitions

  • the application relates to a circuit for reducing the switching losses of electronic valves, a saturation coil for reducing the switching losses being arranged in series with the electronic valve.
  • Controlled and uncontrolled semiconductor components are subsumed under the term electronic valves.
  • the controlled semiconductor components are controlled either by the electrical current supplied to an electrode or by the electrical potential applied to such an electrode. These include, for example, bipolar and unipolar transistors, thyristors or comparable electronic components. Diodes in which the current is a function of the voltage are, for example, uncontrolled electronic valves.
  • coils are connected in series with the transistor.
  • the inrush current can be delayed by appropriate dimensioning of the coil, as a result of which the power loss, characterized by the integral of the product of current and voltage, can be reduced.
  • a capacitor can be used in parallel with the transistor to reduce the voltage steepness.
  • the maximum operating frequency of the electronic valve is greatly reduced by the inductance or capacitance.
  • the power loss that normally occurs in the transistor is also destroyed in another component, for example in the coil or the capacitor, with damping resistors connected in series, as a result of which there is in fact only a displacement, but not a real reduction in the power loss.
  • Such saturation coils or step chokes for reducing the switch-on losses of electronic valves are known for example from DE 35 42 751 AI, DE 33 34 794 AI or DE 28 29 840 AI.
  • thyristors When using thyristors as electronic valves, it is known, for example from the document "Power Electronics: Fundamentals and Applications” by Rainer Jäger, VDE Verlag Berlin 1980, pages 165-181, to arrange a further thyristor in parallel via a capacitor in order to quench the thyristor.
  • a swinging circuit which is arranged parallel to the auxiliary thyristor, serves to ensure a periodic function of the thyristor.
  • the capacitor is recharged via this oscillating circuit, which consists of an inductor and diode in series, for example.
  • the arrangement does not reduce the switching losses of the thyristor.
  • valve relief In order to reduce both the switch-on and switch-off losses, compromises are usually made between valve relief and the maximum operating frequency, since it has so far not been possible to combine the circuits for reducing the switch-on losses and the switch-off losses with a reasonably high operating frequency.
  • US Pat. No. 5,341,004 A discloses a semiconductor circuit with reduced switching losses, in which a second semiconductor element, which is of the same type as the first semiconductor element, is applied in parallel to the semiconductor element, for example the transistor.
  • the second semiconductor element has a higher saturation voltage and a shorter fall time than the first semiconductor element. Because the faster semiconductor element during the switch-off phase the current takes over, the turn-off losses of the first semiconductor element can be reduced in accordance with the shortened switching time.
  • the object of the invention is to achieve the most effective possible reduction of both the switch-on and switch-off losses in electronic valves.
  • the disadvantages of known systems are to be avoided or at least reduced.
  • the maximum frequency of the electronic valve should not be significantly reduced by the circuit according to the invention and the circuit according to the invention should be as simple as possible and therefore inexpensive.
  • the object of the invention is achieved in that an electronic auxiliary valve is arranged parallel to the electronic valve and a series circuit of at least one inductor and a diode for discharging the capacitor is arranged parallel to the electronic valve, the electronic auxiliary valve being activated before the electronic valve is switched off , so that the auxiliary valve takes over the current flowing through the electronic valve and thus the power loss of the electronic valve is minimized during the switch-off process.
  • the known saturation coil connected in series with the electronic valve has an inductance which is variable as a function of time or current, which is as large as possible when the electronic valve is switched on and as small as possible after the switch-on process, so that the current is opposite the voltage of the electronic valve is delayed during the switch-on process and the power loss of the electronic valve is minimized during the switch-on process.
  • This inductance ensures that the current is delayed so much during a switch-on process that the power loss occurring in the electronic valve, characterized by the integral of the product of the voltage and the current, is almost negligible, while the inductance decreases so strongly after the switch-on process , so that there is no significant limitation of the maximum operating frequency of the electronic valve.
  • the coil can be arranged anywhere in the current path of the electronic valve.
  • the electronic auxiliary valve which is arranged parallel to the electronic valve via a capacitor, becomes controlled before the electronic valve is switched off, so that the circuit branch takes over the current flowing through the electronic valve. This also minimizes the power loss of the electronic valve during the switch-off process.
  • a series connection of at least one inductor and one diode for discharging the capacitor is provided in parallel with the auxiliary valve.
  • a saturation coil is arranged in series with the electronic auxiliary valve to reduce the switch-on losses of the auxiliary valve, the total switching losses can be reduced further.
  • the non-linearity of the inductance of the coil is achieved in that it is formed by a choke with a magnetic core, and in that the choke is dimensioned such that it saturates immediately after the electronic valve or the electronic auxiliary valve is switched on goes.
  • the choke loses its inductive resistance in saturation, since all elementary magnets of the core material are magnetized.
  • the choke does not limit the effective operating frequency. Since the choke hardly stores any more energy in the magnetic field in saturation, the losses and overvoltages generated and their energy content are very low and can be fed back into the supply by suitable circuits, for example.
  • the circuit according to the invention for reducing the switch-on losses can be adapted exactly to the respective application.
  • a microcontroller is provided for controlling the electronic valves and electronic auxiliary valves. This allows the circuit to be sentences are adjusted.
  • 1 is a schematic circuit consisting of a transistor as an electronic valve
  • FIG. 3 shows the circuit according to FIG. 1 with a saturation choke to reduce the switch-on losses
  • FIG. 6 shows an embodiment variant of the circuit according to the invention for the combined reduction of the switch-on and switch-off losses of transistors
  • Fig. 1 shows a transistor T as an electronic valve.
  • the transistor T switches a voltage U 0 to a load, represented by a series connection of a load resistor R L and a load inductance L L.
  • a corresponding base current I B is applied to the base of the transistor T.
  • the time profiles of the base current I B , the collector-emitter voltage U CE , the collector current I c and the resulting power loss P v during a switching on and off process of the transistor are shown in FIGS. 2a to 2d.
  • the courses are only schematic representations.
  • the collector current I c gradually increases to its maximum value after a certain switch-on delay time t d .
  • the collector-emitter voltage U CE gradually drops to a minimum value which depends on the transistor type and the collector current I c .
  • the collector-emitter voltage U CE gradually rises again during the so-called storage time t s and the collector current I c then drops to a negligible residual current.
  • Fig. 3 shows a simplified circuit of an electronic valve in the form of a transistor x with a saturation inductor L x in series. It is irrelevant at which point the inductance L x is interposed. With suitable dimensioning of the saturation choke L x , the switch-on losses can be almost completely eliminated, so that only the passage losses and the switch-off losses are decisive for the heat balance of the transistor T x or the electronic valve, and the switching frequency is neither due to thermal losses nor due to insufficient current rise and waste time is limited.
  • the collector current I c increases as quickly as possible. This is achieved through use a saturation choke h x with a magnetic core, which is dimensioned so that it saturates immediately after the collector-emitter voltage U CE drops and thus has a very low inductance. At this point in time, the product of the collector-emitter voltage U CE and collector current I c no longer makes any significant contribution to the switch-on power loss. With this measure, the start-up losses can be reduced in such a way that they are negligible compared to the forward losses.
  • 5a shows the base current I B of the transistor T lt, which represents the switch-on process of this controlled semiconductor.
  • 5b shows the corresponding time profile of the current I (t) through the saturation inductor L x and in FIG. 5c the inductance L (t) of the saturation inductor L x as a function of the time t during the switch-on process.
  • the current rises very slowly due to the relatively high inductance of the saturation choke x .
  • the area of the core saturation is characterized in that the magnetic flux ⁇ or the induction B cannot be significantly increased despite the increase in the current in the saturation choke L x .
  • the inductive resistance of the winding drops, as a result of which only the undesirable ohmic component of the resistance limits the current in the winding.
  • the inductance of the saturation inductor L x therefore drops to a minimum value L min . This is mainly determined by the number of turns and the core material of the saturation choke L x .
  • the current I (t) now increases more rapidly to its maximum value I max limited by the load.
  • the dimensioning of the choke L x is preferably carried out by suitable selection of the magnetic core material, the number of turns and the core volume. These parameters influence not only the point in time t s at which the inductance L x goes into saturation, but also the behavior of how the transition to saturation takes place, that is to say, for example, the steepness of the current rise in the area of saturation of the saturation choke h 1 .
  • FIG. 6 shows a circuit according to the invention for combining th reduction in turn-on and turn-off losses of a transistor T x .
  • an auxiliary transistor T 2 with a further saturation inductor L 2 is connected via a capacitor C in parallel to the transistor 1 X and the saturation inductor L x connected in series.
  • the saturation inductor L 2 minimizes the turn-on losses of the auxiliary transistor T 2 in the same way as the saturation inductor L : minimizes the turn-on losses of the main transistor T 1 .
  • the parallel to the auxiliary transistor T 2 and the saturable reactor L 2 connected diode D x and inductance L 3 is used to reverse the polarity of the capacitor C according to any one switching cycle, so that the starting conditions for a renewed switching cycle to be created.
  • a diode D 2 is used parallel to the output (load R L and L L ), which enables the demagnetization of the inductance L L , so that there are no impermissibly high voltage peaks when switching off.
  • the mode of operation of the circuit according to FIG. 6 is explained in more detail on the basis of the time profiles according to FIGS. 7a to 7h.
  • the switch-on process of the main transistor T x corresponds to that which has already been shown and explained in FIGS. 4a to 4d.
  • the auxiliary transistor T 2 Before the switch-off process, the auxiliary transistor T 2 is switched through by a corresponding base current I B2 .
  • the collector current I c2 also increases due to the inductor L 2 with a delay.
  • the secondary branch formed by transistor T 2 finally takes over the current, so that after reaching the maximum of collector current I C2, main transistor T x no longer carries collector current I C1 and can be switched off by base current I B1 . Since the collector current I cl of the transistor x has already dropped to its minimum at this point in time, the turn-off power loss of the transistor T x is reduced to a minimum.
  • the current I c2 drops automatically due to the charge on the capacitor C.
  • the negative collector-emitter chip voltage U CE2 after the switching on of the transistor T x stems from the swinging over of the capacitor C via the diode D x and the inductance L 3 .
  • the switching losses according to the invention are reduced by combating the cause, namely the simultaneous occurrence of a current and a voltage.
  • the wiring according to the invention is characterized by particular simplicity and particular effectiveness. As a result, all circuits which contain electronic valves or switches can be made significantly smaller or deliver a higher output power with the same volume.
  • circuits according to the invention offer particular advantages when used in devices in which very high currents and / or voltages and therefore also very high power losses occur. These include, for example, welding devices in which very high currents usually occur or ballasts for gas discharge lamps.

Landscapes

  • Electronic Switches (AREA)

Abstract

L'invention concerne un circuit permettant de réduire les pertes de commutation de soupapes électroniques, dans lequel une bobine de saturation (2) destinée à réduire les pertes de mise en service est montée en série par rapport à la soupape électronique (1). Afin de réduire le plus efficacement possible, tant les pertes de mise en service que les pertes de mise hors service, il est prévu de monter parallèlement à la soupape électronique (1), une soupape auxiliaire électronique (3) par l'intermédiaire d'un condensateur (4) et de coupler en série au moins une résistance inductive (6) et une diode (7) pour soulager le condensateur (4). La soupape auxiliaire électronique (3) est lancée avant le processus de mise hors service de la soupape électronique (1), de manière que ladite soupape auxiliaire (3) absorbe le courant traversant la soupape électronique (1) et que la puissance de perte de la soupape électronique (1) se trouve de ce fait minimisée pendant le processus de mise hors service. Une bobine de saturation (5) est également avantageusement montée en série par rapport à la soupape auxiliaire (3) afin d'en réduire les pertes de mise en service.
EP01923373A 2000-04-12 2001-04-12 Circuit pour reduire les pertes de commutation de soupapes electroniques Withdrawn EP1275203A1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
AT6362000 2000-04-12
AT6362000 2000-04-12
PCT/AT2001/000106 WO2001080425A1 (fr) 2000-04-12 2001-04-12 Circuit pour reduire les pertes de commutation de soupapes electroniques

Publications (1)

Publication Number Publication Date
EP1275203A1 true EP1275203A1 (fr) 2003-01-15

Family

ID=3677908

Family Applications (1)

Application Number Title Priority Date Filing Date
EP01923373A Withdrawn EP1275203A1 (fr) 2000-04-12 2001-04-12 Circuit pour reduire les pertes de commutation de soupapes electroniques

Country Status (3)

Country Link
EP (1) EP1275203A1 (fr)
AU (1) AU2001250144A1 (fr)
WO (1) WO2001080425A1 (fr)

Families Citing this family (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE10156963A1 (de) * 2001-11-20 2003-06-05 Fritz Frey Schaltungsanordnung zum zuverlässigen Schalten von Stromkreisen
CN103326345B (zh) * 2013-07-08 2015-04-22 东南大学 一种直流过压保护电路

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CH682611A5 (de) * 1991-04-16 1993-10-15 Hasler Ag Ascom Schaltentlastungsnetzwerk für einen Schalter und Verwendung desselben.
US5543704A (en) * 1994-06-08 1996-08-06 Telefonaktiebolaget Lm Ericsson Pulse width modulated DC-to-DC boost converter
DE19546663A1 (de) * 1995-12-14 1997-06-19 Euroatlas Ges Fuer Leistungsel Spannungswandler
US5914587A (en) * 1997-08-05 1999-06-22 Lucent Technologies Inc. Circuit for reducing switching losses of a power converter and method of operation thereof
US5991174A (en) * 1998-08-28 1999-11-23 Lucent Technologies Inc. Snubber circuit for a rectifier, method of operation thereof and power converter employing the same
US6028418A (en) * 1999-02-11 2000-02-22 Delta Electronics, Inc. Boost converter with minimum-component-count active snubber

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
See references of WO0180425A1 *

Also Published As

Publication number Publication date
AU2001250144A1 (en) 2001-10-30
WO2001080425A1 (fr) 2001-10-25

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