EP1104587A2

EP1104587A2 - Wide band planar radiator

Info

Publication number: EP1104587A2
Application number: EP98917080A
Authority: EP
Inventors: Lutz Rothe; Walter Gerhard
Original assignee: Pates Technology Pantentverwertungsgesellschaft fur Satelliten- und Moderne Informationstechnologien Mbh
Current assignee: Pates Technology Pantentverwertungsgesellschaft fur Satelliten- und Moderne Informationstechnologien Mbh
Priority date: 1997-03-25
Filing date: 1998-03-25
Publication date: 2001-06-06
Anticipated expiration: 2018-03-25
Also published as: CA2284643A1; JP2001524276A; WO1998026642A2; IL131994A0; ATE247870T1; ES2209128T3; AU7041498A; WO1998026642A3; IL131994A; EP1104587B1; DE59809361D1; KR20010005719A; DE19712510A1; US6456241B1

Abstract

The present radiator pertains to a planar array antenna for sending or receiving linear polarized waves, with two radiator levels each comprising radiator elements mounted in lines and columns, while the elements of each radiator level are coupled on a central point so as to be equal in phase and amplitude. Both radiator levels receive and transmit mutually perpendicular polarized waves, and each radiator element has shades (6) and a linear excitrated stripline (16, 161, 16a, 16b). Said striplines (16, 161, 16a 16b) are linked in pairs to the branch ends (15, 31) of the coupling networks (1, 2), and the striplines (16, 161, 16a 16b) of each pair are mounted on the axis or arranged in an axially parallel configuration; the free ends of both striplines (15, 161, 16a, 16b) are connected through at least one connection line (32, 33, 34, 36) to a brunch end (15, 31), and a 180° phase difference between both radiator elements (6,16) is obtained by using at least one connection line (32, 33, 34) of a stripline (16, 161, 16a, 16b).

Description

Broadband planar spotlights

The invention relates to a planar antenna for receiving and transmitting linearly polarized waves, with two radiator planes arranged parallel to one another, each having a plurality of radiator elements arranged in rows and columns, the radiator elements of each radiator plane being coupled in phase and amplitude to a central point in each case via a coupling network , and the two radiator planes receive or radiate orthogonally polarized waves.

The planar antenna is designed as a radiator system for the reception of extremely high-frequency electromagnetic radiation fields on the basis of a planar solution concept, by means of which directional information transmission paths, preferably for the area of satellite-based data, audio and video transmission, can be operated. Here, the invention relates primarily to the design of the individual radiators and their network-side coupling.

The field of application of the invention also includes stationary and mobile telephone or information transmission on the basis of satellite-based message transmission and the sector of terrestrial information transmission on the basis of defined point-to-point connections. In particular, the area of satellite-based analog and digital signal transmission

CONFIRMATION COPY transmission, preferably within the spectral range between 10.70 GHz and 12.75 GHz, and the range of terrestrial point-to-point transmission, preferably within the spectral range between 10.00 GHz and 10.40 GHz, targeted application focuses.

Currently known planar emitter solutions for the reception of high-frequency electromagnetic radiation fields are based on the electromagnetic excitation of diaphragm fields with rectangular, square, circular or Romanesque diaphragm borders, the electromagnetic supply of which is carried out by means of strip lines with a dimensionally defined dimension.

The mutual arrangement of the exciting strip conductors or excited apertures and the respective design of the aperture contour determine the characteristics of the electromagnetic radiation field that can be generated in their combination. The known arrangements are based on the generation of circularly polarized electromagnetic radiation fields by means of diaphragm groups excited in phase, the individual diaphragms being excited in each case by means of a pair of strip conductors with a dimensionally defined dimension with a mutual spatial and temporal offset of 90 °, or else on the generation of linearly polarized electromagnetic radiation fields by means of diaphragm groups excited in phase, the individual diaphragms in each case being carried out by means of a strip conductor which is dimensionally defined on the geometry side and whose geometric arrangement determines the direction of oscillation of the electric field vector. Known solutions for the design of the radiator elements are also based on the use of geometrically defined dimensioned, consisting of one or more identical or unequal surface elements and galvanically or field-supported coupled conductor surfaces with square,

- 1- Rectangular, circular or trapezoidal surface borders, which lead to the excitation of the diaphragm fields, the polarization being determined via the location of the signal coupling.

Any other solutions used are based on the configuration of surface resonators in microstrip or coplanar technology with square, rectangular or circular surface boundaries. Both galvanic and field-based versions of the signal coupling are known. Other known solutions are based on microstrip configurations in ring or frame design with resonant geometric ring or frame length. The known solutions of the excitation networks for the case of the group arrangement are based on the parallel feeding of the radiator elements or on the parallel feeding of series-fed radiator sub-groups. Here, microstrip, slot line, triplate or coplanar technologies are used to implement the coupling networks.

As is known, the generation of two orthogonal polarizations is based on the arrangement of the radiator elements which is stuck along the surface normal of the diaphragms or surface resonators. Known planar directional emitter arrangements with high directivity are configured exclusively as narrow-band systems or, in the case of satellite-based information transmission, as single-band systems. The signals are coupled in and out via a waveguide with a capacitive probe, the waveguide geometry representing the propagation condition of the field type of the highest cutoff wavelength.

The aim of the invention is to configure planar transmission and reception modules, by means of which directional information, both direct and transponder-based, Transmission lines are primarily conceivable within the framework of the mobile terrestrial telephone or information transmission sector as well as satellite-based communication lines.

It is therefore an object of the present invention to provide a planar antenna whose geometric dimensions are as small as possible, the antenna being as broad as possible in the spectral range with a high area efficiency and a high directivity.

This object is achieved according to the invention by a planar antenna with the features of claim 1. Further advantageous configurations result from the features of the subclaims.

The planar antenna according to the invention advantageously has square diaphragms which, compared to round diaphragms, have a much higher broadband capability and a greater polarization purity. However, square diaphragms have the disadvantage of increased electromagnetic coupling and the mutual influencing of neighboring radiator elements. In addition, square panels require more space, which has a disadvantageous effect on the implementation of the dining network. This is due to the fact that only the strip conductors of the coupling network which excite the apertures may protrude into the aperture space and not the coupling network which connects the stimulating strip conductors to the coupling point. A square panel with rounded corners is therefore used as the optimum between electrical broadband and the required geometric space. Square or rectangular panels with other conceivable corner or side deformations are also conceivable. The single radiator is excited via a conductor piece protruding into the panel. The shape of the conductor, the shape of the edges of the diaphragms, and the position of the conductor in relation to the diaphragm determine the base point impedance of the radiator element “diaphragm line”. The radiator elements are connected in an impedance-correct manner, with the same amplitude and phase, by means of a likewise planar supply or coupling network and to a common summation point (coupling point). A parallel supply between the individual radiators is usually used here. However, this is not sensibly possible with single radiators with a square diaphragm shape due to the lack of space. Due to the need for an impedance-correct, low-reflection single radiator coupling and necessary impedance transformations Corresponding conductor widths that largely preclude the practical implementation options. In the prior art, therefore, at least two feed lines must be implemented between two screens, which leads to considerable mecha niche and electrical difficulties and will make practical implementation almost impossible.

This basic problem is solved in the present invention with a new serial feed technology between two adjacent radiator elements. The serial feed technology makes it possible to design the entire feed network in a mechanically simplified manner and at the same time to solve the space problem when feeding square diaphragms. In addition, the electrical properties of the feed line are considerably improved because there are no feed lines running parallel between the diaphragms and, consequently, no electromagnetic coupling phenomena which adversely affect the overall functionality can occur.

y ~ The diaphragms are supplied by line sections which are arranged alternately in the plane of the electrical polarization (E plane). This means that all radiator elements are always aligned and polarized in opposite directions by 180 °. In order to ensure that all elements are supplied in phase, a phase diversion between two adjacent diaphragms creates a 180 ° phase difference. This supply also has the advantage that excited propagable parasitic waves, which arise due to unbalances when the diaphragm is excited by the triplate feed line, are largely extinguished by the serial supply and their negative influence on the electrical functioning is considerably reduced. The advantageous combination of a square diaphragm with rounded corners and serial supply leads to very good electrical parameters with regard to the polarization purity, insulation, the forward / reverse ratio and the area efficiency.

The exciting strip conductors serve to excite a field or vibration type within the diaphragm, which is determined both by the aperture geometry or contour and by the geometrical position and geometry of the exciting strip conductor. This means that the formation of the resulting field or radiation type of the diaphragm by superimposing the source or excitation condition determined by the arrangement and geometry of the strip conductor and the propagation or existence condition determined by the diaphragm contour and geometry is determined. Via the targeted generation of a defined impedance profile within the aperture space by means of the arrangement and geometry-side dimensioning of the exciting strip conductor, the field type generation is used to determine the polarization state of the aperture field, so that in the case of the same aperture contour, both the thogonal linear polarizations as well as the orthogonal circular polarizations are generated. In the case of the same excitation elements, that is to say the same stimulating stripline, the formation and existence conditions of both the orthogonal linear polarization and the orthogonal one are determined by the specific generation of defined blind elements within the aperture space by means of the contour and geometry dimensioning of the aperture circular polarization generated. The linear polarization can be converted into a circular polarization by means of an additional polarizer.

In order to maintain the broadband capability of the individual radiator and the feed network, a frequency wideband coupling between the common feed point of the antenna and the subsequent electronics (LNC) is necessary. For this purpose, the planar antenna according to the invention has an adapted, low-reflection and frequency-broadband transition from a coaxial line to a triplate line. The difficulty with this type of coupling is the realization of a high-frequency ground connection between the coaxial outer conductor (ground) and the two ground lines of a triplate line with rear coupling. This problem was solved by using a hollow profile segment. Here, the good ground connection between the hollow profile segment, the aperture masks and the coaxial coupling and uncoupling is crucial. The “hollow profile” or “tunnel” formed is selected so that the antenna signal power can be coupled out with as little reflection as possible. The outer shape of the hollow profile segment is insignificant for the electrical properties and is determined from a manufacturing point of view. Any number of mechanical hollow profile segment shapes are thus conceivable.

- V The subject matter of the invention and additional embodiments thereof are explained in more detail below with reference to figures.

Show it:

Figure 1 is a perspective sectional drawing through the planar antenna according to the invention;

Figure 2 and 3: the coupling networks of the planar antenna;

FIG. 4: a conductive layer with screens arranged in a matrix;

FIG. 5: two adjacent diaphragms with the strip conductors which excite them and which project into the diaphragm space in a symmetrical manner;

FIG. 6: two adjacent diaphragms with stimulating strip conductors which do not engage in the center-symmetrically in the diaphragm space;

FIG. 7: superimposition of the two coupling networks including representation of the aperture spaces;

Figures 8 to 10: exemplary aperture shapes;

FIGS. 11 and 12: cross-sectional representation through the coupling points between the coaxial waveguide and the triplate network;

Figure 13: top view of a coupling point; FIG. 14: a spacer ring for forming the hollow profile segment;

Figure 15: Guide bush.

FIG. 1 shows a perspective detail drawing from the planar antenna according to the invention, in which the three conductive layers (diaphragm masks) 3, 4 and 5 to the coupling networks 1 and 2 and the base plate 12 are arranged parallel to one another. The diaphragms 6 of the conductive layers 3, 4, 5 are each arranged one above the other and together form the diaphragm spaces which are excited by the coupling networks shown in FIGS. 2 and 3 and in particular by the strip-shaped stimulating strip conductors 16a and 16b. The base plate 12 is located at a distance of approximately λ / 4 from the conductive layer 4 and serves to shield the radiation emitted in the direction of the base plate 12 and to reflect it. The spaces between the conductive layers 3, 4 and 5 and the base plate 12 and the coupling networks 1 and 2 are filled by means of dielectric layers 7, 8, 9, 10 and 11, the dielectric layers being produced from foils or mats and placed and positioned between the individual layers. With their diaphragms 6, the conductive layers 3 and 4 together with the coupling network 1 form nx m radiator elements. The conductive layers 4 and 5 with their diaphragms 6, together with the coupling network 2, likewise form nx m radiator elements. As can be seen from FIGS. 2 and 3, all the stimulating strip conductors 16a and 16b are coupled in phase and amplitude homogeneous fashion to a central coupling point 17 and 22 within the network level via the coupling networks. Every coupling network exists from trunk branches 13a and 13b to which further branches 13a, 13b, 14a, 14b are connected. The last branch of the network before the stimulating strip conductors are reached is referred to below as the branch. As can be seen in FIG. 5, the first exciting strip line 16 is connected to this branch 15, 31 via a short connecting line 36. A U-shaped connecting line 32, 33, 34 is also connected with one leg 32 to the branch 15, 31, the second exciting strip line 16 being connected at right angles to the other leg 34 via a further short connecting conductor 35. The two exciting strip conductors 16 connected to the branch 15, 31 together form a group of two. The stripline 16a of the coupling network 1, and the stripline 16b of the coupling network 2, which are each on a line, together form a row of a coupling network. The strip conductors, which are arranged parallel to one another, each form a column. As shown in FIG. 6, it is also possible that the strip conductors 16 'forming a group of two are not arranged on a line, but rather axially parallel to one another. This determines the excitation or impedance of the planar antenna.

The U-shaped connecting conductor 32, 33, 34 is dimensioned in its geometric length and coupling profile-side arrangement such that between the first and second, third and fourth, fifth and sixth etc. line aperture taking into account the mutual aperture coupling in each case in the plane of the electrical Field vector of the state of the opposite phase is generated.

The connecting cable used for the 180 ° phase shift

32, 33, 34 need not be U-shaped, but can have any other shape and form. The

- to - However, U-form has great advantages in terms of the space required.

The exciting strip conductors 16a, 16b are each arranged centrally symmetrically (FIG. 5) or asymmetrically (FIG. 6), preferably centrally symmetrically to the one edge 6b of the diaphragms 6. The strip conductors 16a, 16b run perpendicular to one another. This results in the possibility of generating decoupled orthogonal linear polarization or the possibility of generating coupled and phase-shifted orthogonal polarization or circular polarization in the opposite direction of rotation of the field vector.

As can be seen from FIG. 7, the individual exciting strip conductors 16a, 16b of the coupling networks 1 and 2 are arranged orthogonally to one another, so that two waves orthogonally polarized to one another can be transmitted or received by means of the planar antenna according to the invention.

FIGS. 8 to 10 show different apertures. FIG. 8 shows a square diaphragm 6 with straight edges 6b, which are connected to one another by means of circular arc segments 6c. FIG. 9 shows a likewise square diaphragm 6, the corners 6c being chamfered.

A further possibility of varying or setting the broadband nature of the planar antenna, among other things, is shown in FIG. Here the edges 6b '' are not straight, but are pressed inwards in a circular, elliptical or hyperbolic shape.

The screens 6 of the individual conductive layers 3, 4 and 5 are each arranged in such a way that the Intersections of their lines of symmetry lie one above the other. As can be seen from FIG. 4, the diaphragms 6 of a plane are arranged at the same distance from one another. However, it is also possible to arrange the diaphragms of a plane at non-uniform distances from one another. The diaphragms can also be arranged offset from one another in columns or rows.

The dielectric layers 7, 8, 9, 10 and 11 can have the same or different susceptibility profiles. The individual layers can be configured either homogeneously or from more than one partial layer with the same or different, preferably the same, layer height and the same or different, preferably identical, dielectric susceptibility profiles. The coupling network is either guided or stabilized mechanically using a low-dielectric layer, preferably a low-dielectric film with a minimal dielectric loss angle. The configuration of the coupling networks including the stimulating strip conductors is carried out by means of additive techniques or subtractive methods, preferably subtractive methods, preferably PTFE or PET compositions, polyethylene co-positions, poly-4-methylpentene or poly-4-methylhexene being used as structure supports .

As can be seen from the figures, each coupling network has 1 and 2 trunk branches 13a, 13b (FIGS. 2 and 3) and 51 (FIG. 13), which each connect one half of the coupling network to the coupling point. Arranged between the trunk branches 51 is a straight strip section 50, which is galva- centrically centered with the inner conductor 42 of a coaxial waveguide, which is used to connect the planar antenna to the downstream low-noise converter (LNC). nisch connected. The inner conductor 42, which penetrates through the conductor track 50, is preferably galvanically connected to the latter by means of a solder connection. The strip-shaped conductor section 50 is bordered by two projections 43a of a spacer ring 43 at the same distance in each case. The projections 43a and 43a 'connect the conductive layers 3 and 4 or 4 and 5 to one another, so that a hollow profile segment is formed. This hollow profile segment is preferably rectangular, but can also be circular or elliptical. The length of the stripline 50 is determined in each case from the required impedance and the line conditions. As shown in FIG. 11, an outer conductor part 40 is arranged on the base plate 12, which protrudes with its one projection 40a through the base plate in the direction of the low-noise converter. This outer conductor part 40 can optionally be screwed to the base plate 12. For this purpose, an external thread on the outer conductor part 40a in the area of the base plate 12 is necessary, which in turn must have a corresponding internal thread. The outer conductor 40 bears against the base plate 12 with its collar 40b. This collar 40b has a square or hexagonal shape so that it can cooperate by means of a wrench. In the direction of the conductive layers 3, 4, 5, the collar 40b is adjoined by a particularly cylindrical part 40c, which forms the support surface for the spacer ring 43 with its end face. Another cylindrical projection 40d with a smaller diameter adjoins the projection 40c forming the collar. This projection 40d is encompassed by the spacer ring 43 and continues to reach through the conductive layer 5 and is flush with its surface. The outer conductor part 40, together with the inner conductor 42 and the socket 41, which is made of non-conductive material, forms a coaxial waveguide for connecting the downstream low-noise Converters. The projection 40a which extends through the base plate 12 has an external thread for fastening the low-noise converter. The thickness of the base plate 43b of the spacer ring 43 together with the length of the cylindrical part 40c and the length of the collar 40b together corresponds to the distance between the base plate and the conductive layer 5. Additional spacer sleeves 45 keep the base plate 12 and the conductive layer 5 at a distance. The conductive layers 4 and 5 are pressed or held together by means of screws 47. For this purpose, corresponding bores or recesses 46, 30 are provided in the conductive layers 4 and 5. Network level 2 also has a corresponding bore 24.

FIG. 12 shows the coupling between the coaxial waveguide and the Tπplate waveguide of the network 1. For this purpose, the spacer ring 43 ^λ , which is made of conductive material, connects the two conductive layers 3, 4 and also penetrates through the network level 1. By means of spacer bushings 45 and associated screws 47, the conductive layers 3 and 4 are pressurized against one another. The conductive outer conductor part 40 connects the base plate 12 with the spacer ring 43 so that the base plate 12 together with the conductive layers 3, 4 are at the same potential. All parts of FIG. 12 correspond in function to those of FIG. 11. Functional parts are therefore given the same, but deleted, reference numerals.

Relevant dimensions of the planar antenna for receiving waves in the frequency range between approx. 10 GHz and 13 GHz are listed below.

The distance between the base plate 12 and the conductive layer 5 is 4 mm and is determined by the spacers 45 as well as the guide bushes 54 according to FIG. 15 and the outer conductor 40 together with the spacer ring 43. The space between the base plate 12 and the conductive layer 5 is filled with a foam mat, the ε _{r of} which is approximately equal to 1. A polyethylene foam film with a thickness of 1 mm is located between a conductive layer 3, 4, 5 and the respectively adjacent coupling network 1 or 2. The conductive layers consist of aluminum sheets with a thickness of 0.5 mm. Between the conductive layers 3, 4, 5 there is a coupling network 1 or 2, which is arranged on an optional glass fiber reinforced PTFE film (TLY) or PET film, the relative dielectric constant of 2.2 and the thickness of 127 μm .

The spacer ring 43 has an outer diameter of 12 mm. The inner diameter of the axial bore 43c has a diameter of 5 mm. The groove 43d has a width of 6 mm. The width of the trunk branches 51 according to FIG. 13 is 2.1 mm, the width of the stripline 50 is 1.2 mm. In the area of the galvanic soldered connection between the inner conductor 42 and the strip conductor 50, the strip conductor 50 is made thickened, in particular by means of segments of a circle whose radius is 0.85 mm. The height of the base plate 43b of the spacer ring 43 is 2 mm. The height of the projections 43a is 2.625 mm. The panels have a width and a length of 16 mm each. The corners are rounded, whereby the rounding corresponds to a segment of a circle with a radius of 5 mm. The centers of the panels 6 are each 21.5 mm apart.

The exciting strip conductors 16a for the horizontal plane have a length of 6 mm and a width of 1.5 mm. The distance between the two legs of the U-shaped connecting conductor 33 is 2.3 mm. The radius of the circular section is 1.15 mm. The distance from the edge 6b of a panel to the center line of the nearest leg 32, 34 is 1.6 mm. The length of the branch 31a is 5 mm. The geometry of the radiation elements for the vertical plane differs only slightly from that of the radiator elements for the horizontal plane. The aperture shape is the same. The length of the stimulating stripline 16b is 6 mm. However, the width of the stimulating strip line 16b is 1 mm.

It goes without saying that the stated sizes are only valid for a certain frequency band and for appropriately selected materials. Depending on the required frequency spectrum of the planar antenna, the geometries must be chosen differently.

Reference numerals:

1.2 coupling networks with exciting strip conductors 3,4,5 conductive layers with diaphragms arranged in a matrix 6

6.6 \ 6 ^{, λ} apertures

6a space between the panels

6b, 6b ^λ , 6b ^Xλ edges of the screen 6c, 6c ^λ rounded or beveled corners of the screen

7,8,9,10,11 dielectric layers

12 base plate

13a, 14a, 13b, 14b branches of the coupling network

13a ^λ , 13b, 50 trunk branch, galvanically connected with inner conductor

15, 15a, 15b,

31, 31a, 31b branch to which the exciting strip conductors 16, 16 16a, 16b connect

16.16 \

16a, 16b stimulating strip conductors

17.22 coupling point; galvanic connection point between inner conductor and trunk branch 18.24 holes / recess for screws 47.47 ^x

19a, 19b, 25 holes for guide bush 54

20.23 Cutouts for the projections 43a, 43a of the spacer ring 43, 43 which penetrate the coupling network 21 Cutout for the outer conductor part 40 ^λ Bore for the cylindrical part 40c of the outer conductor part 40 'Bores for the spacer bushings 45 ^λ Bore for the cylindrical part 40d of the outer conductor part 40 Bore for the projections 43a of the spacer ring which penetrate the coupling network 2 43 bores, 34 legs of the U-shaped connecting line, 33a, 33b U-shaped connecting cable, 36 short connecting cables to the stimulating ones

Strip conductors, 40 ^v outer conductor part a, 40a the base plate 12 through part b, 40b ^λ plan on the base plate 12 part of the outer conductor part c, 40c ^x the collar forming part against which the spacer ring 43,43 abuts d, 40d ^λ further collar of the Outer conductor, which reaches through the conductive layer and ends flat with it, 40e external thread for fastening coaxial

Waveguides or a low-noise converter, 41 insulation socket between inner conductor 42.42 ^v and outer conductor 40.40 ^λ , 42 inner conductor, 43 ^Λ spacer ring a, 43a ^x projections penetrating through the conductive layer and the coupling network; Educate the

Side walls of the groove 43d b base plate of the spacer ring 43 c axial bore

- / ό> ~ d The groove forming the hollow profile segment, 44 'soldered connection between inner conductor 42, 42' and trunk branch of the coupling network, 45 'spacer, in particular rivet bushing, made of conductive or non-conductive material a, 45a' section of the spacer 45, 45 'b driven into the base plate, 45b 'internal thread of the spacer 45,45', 4 6 'hole or recess for the penetrating conductive screw 47,47', 47 'screw, made of conductive or non-conductive material a, 47a' external thread of the screw 47 b, 47b 'Head of screw 47, 48' spacer straight strip-shaped conductor; Center-symmetrical to the edges of the groove 43d of the spacer ring 43 formed by the projections 43a. Stem branches of the coupling network. Guide bush. Section of the guide bush with an enlarged diameter for adjusting the distance between the base plate and the conductive layer 5. Blind bore with internal thread. Contact surface on base plate. 12 Contact surface on conductive layer. 5

- / <* -

Claims

claims

1. Planar antenna for receiving and transmitting linearly polarized waves, with two radiator planes arranged parallel to one another, each with several radiator elements arranged in rows and columns, the radiator elements of each radiator plane being coupled in phase and amplitude to a central point in each case via a coupling network , and the two radiator planes receive or radiate orthogonally polarized waves, characterized in that - each radiator element has diaphragms (6) and a rectilinearly stimulating strip conductor (16, 16 ^λ , 16a, 16b), and

- That the exciting stripline (16, 16, 16a, 16b) each in groups of two at the ends of the branches

(15,31) of the coupling networks (1,2) are connected, and

- That the strip conductors (16, 16, 16a, 16b) of each group of two are arranged on an axis or axially parallel to one another, the facing ends of the two strip conductors (16, 16 16a, 16b) each having at least one connecting line

(32,33,34,35,36) are connected to one end of a branch (15,31), and

that a phase difference of 180 degrees between the two radiator elements (6, 16) is generated by means of at least one connecting line (32, 33, 34) of a strip line (16, 16 \ 16a, 16b).

-2o-

2. Planar antenna according to claim 1, so that the connecting lines differ in length by half a wavelength from one another.

3. planar antenna according to claim 1 or 2, since you r ch marked that the longer of the two connecting lines has a U-shape with two parallel legs (32,34), the end of one leg (32) to the branch (15, 31) of the coupling network (1, 2) and a short strip conductor (35) adjoins the end of the other leg (34) at right angles, on which the exciting strip conductor (16, 16 ^λ , 16a, 16b ) connects.

4. planar antenna according to one of claims 1 to 3, since you r ch ge kennzei chn et that parallel to the surface at a certain distance from each coupling network (1,2) a conductive layer (3,4,5) arranged with diaphragms (6) , the diaphragms (6) each being arranged above a strip conductor (16, 16 ^λ , 16a, 16b).

5. planar antenna according to claim 4, since you r ch ge characteristic that between the conductive layers (3,4,5) and the coupling networks (1,2) each have at least one dielectric layer (7,8,9,10) is arranged, the thickness of which determines the distance between the respective conductive layer (3, 4, 5) and the respective coupling network (1, 2).

6. Planar antenna according to one of the preceding claims, since th e r ch g e k e n n z e i ch n e t that the coupling network (1,2) and the exciting strip line (16, 16 16a, 16b) are applied to a particularly glass fiber reinforced PTFE or PET film.

-JLi-

7. Planar antenna according to one of the preceding claims, so that the exciting strip conductors (16, 16 ^Λ , 16a, 16b) of a line are arranged on a line or parallel to one another, whereby these strip conductors (16, 16 ^λ , 16a, 16b) are connected alternately with their first and with their second narrow end to the coupling network (1, 2).

8. Planar antenna according to one of the preceding claims, that the waveguides of the planar antenna are designed in triplate technology.

9. planar antenna according to one of the preceding claims, that each coupling network (1, 2) has an input or output coupling point

(17,22), the coupling points (17,22) being designed as waveguide transitions between triplate technology and coaxial coupling in and coupling out.

10. Planar antenna according to one of the preceding claims, since you r ch g e k e n n z e i ch n e t that the apertures

(6) are rectangular, in particular square, with or without rounded or bevelled corners (6c, 6c ^λ ), the radius of the rounded corners or the degree of the bevel determining, among other things, the frequency bandwidth and input impedance.

11. planar antenna according to one of the preceding claims, since you r ch gekennzei net that the contour of the diaphragm (6) has a number of n straight sides (6b, 6b, 6 ^{Λ x} ), which are interconnected by arches.

-

12. Planar antenna according to one of the preceding claims, since it is known that the borders of the diaphragms (6) are composed of a number of n circular, elliptical or hyperbolic segments.

13. Planar antenna according to one of the preceding claims, so that a stimulating strip line (16, 16, 16a, 16b) projects into the aperture space, the strip line (16, 16, 16a, 16b) being perpendicular to the boundary side is arranged, via which it protrudes into the aperture space.

14. Planar antenna according to one of the preceding claims, since you mark the net that the exciting strip conductors (16, 16, 16a, 16b) of two diaphragms (6), which are adjacent in rows, alternate from the respectively opposite edges (6b, 6b, 6b ^{λ λ} ) are arranged leading into the aperture space.

15. planar antenna according to claim 13 or 14, since you r ch gekennzei ch net that the rectilinear strip conductor (16, 16 ^λ , 16a, 16b) is formed within the aperture space from a plurality of rectilinear strip conductor sections of the same or different section length and the same or different section width.

16. Planar antenna according to one of claims 13 to 15, so that the section-shaped strip conductor is formed from conductor sections coupled galvanically or by means of a gap of defined gap width.

17. planar antenna according to one of the preceding claims 13 to 16, dadu r ch gekennzei ch net that the exciting strip conductor (16, 16, 16a, 16b) is arranged in the center symmetrically or offset to the boundary side of the respective aperture space.

18. Planar antenna according to one of the preceding claims, characterized in that the central coupling point (17.22) is designed such that the inner conductor (42, 42) of a coaxial waveguide, by means of which the signals from the planar antenna to Low-Noise-Converter (LNC) are coupled in or out, with which the strip conductor section of the coupling network (1, 2) forming the trunk branch (51) is galvanically connected, the strip conductor section (51) being in the area of the galvanic connection to the inner conductor ( 42.42 ^x ) leads straight and center-symmetrically through a conductive, profiled, hollow profile segment.

19. A planar antenna according to claim 18, so that the hollow profile segment is formed by a conductive connection between the diaphragms (6) including the coupling network (1, 2) and the conductive layers themselves.

20. planar antenna according to claim 19, since you r ch ge kennzei ch net that a spacer ring (43, 43 ^v ), which forms the hollow profile segment, with projections (43a, 43a) of a defined length formed on its first flat side, the two conductive layers (3, 4; 4, 5) conductively connects to one another, and the spacer ring (43,43) on a collar (40c, 40c ^Λ) of forming the outer conductor of the coaxial waveguide portion (40, 40 ') with its second flat side is supported, the projections (43a, 43a) penetrating one conductive layer (4, 5) and the coupling network (1, 2) and abutting the other conductive layer (3, 4).

21 planar antenna according to claim 20, dadu rchgekennzei ch net that the spacer ring (43.43 ^λ ) engages around a collar (40c, 40c) of the outer conductor (40.40 ^λ ) adjacent cylindrical projection (40d, 40d) and the cylindrical projection (40d, 40d ^λ ) passes through a conductive layer (4,5) and ends flush with its surface.

22. Planar antenna according to one of claims 20 or 21, so that the spacer ring (43, 43) is a disk with an axial bore (43c), one flat side of which is a groove (43d) with central symmetry, the depth of the length addition corresponds to the thickness of one conductive layer (4, 5) and the distance between the two conductive layers (3, 4; 4, 5).

23. A planar antenna according to one of claims 20 to 22, as you r ch ch gekennzei net, that the part forming the training has senleiter (40,40 ^λ) has a further collar (40b, 40b) provided on a conductive Gundplatte (12 ) is present.

24. planar antenna according to one of claims 20 to 23, since you r ch marked that the part forming the outer conductor (40.40 ^Λ ) has an axial bore, m a non-conductive bushing (41.41 ^Λ ) made of PTFE in particular, in which the inner conductor (42, 42) is arranged, the one end of the socket abutting the underside of the coupling network (1, 2).

25. Planar antenna according to one of the preceding claims, since you mark the net that the base plate (12) and the diaphragms (6) have conductive layers (3, 4, 5) by means of in particular conductive spacers, in particular rivet bushings, which m the base plate (12) are driven in, are kept at a distance, the spacers (45, 45) having an internal thread (45b, 45b) into which screws (47, 47) engage, with each of the screws (47, 47 ^Λ ) its head is pressurized with a conductive layer (3, 4) against the spacer ring (43, 43).

26. planar antenna for receiving and transmitting linearly polarized waves only one polarization plane according to one of the preceding claims, since you ch chennzei net that the planar antenna has only one radiator level with only one coupling network (2) and only two apertures (6) each has conductive layers (4,5).

27. Planar antenna according to one of the preceding claims, since it is known that circular polarization can be received or transmitted by means of a polarizer which is arranged above the planar antenna in the radiation space.

-αt-