EP0647373B1 - Dispositif et procede d'accord d'un filtre melangeur - Google Patents

Dispositif et procede d'accord d'un filtre melangeur Download PDF

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Publication number
EP0647373B1
EP0647373B1 EP94902794A EP94902794A EP0647373B1 EP 0647373 B1 EP0647373 B1 EP 0647373B1 EP 94902794 A EP94902794 A EP 94902794A EP 94902794 A EP94902794 A EP 94902794A EP 0647373 B1 EP0647373 B1 EP 0647373B1
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EP
European Patent Office
Prior art keywords
combiner
frequency
power
filter
sample
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired - Lifetime
Application number
EP94902794A
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German (de)
English (en)
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EP0647373A1 (fr
Inventor
Pekka Heikkilä
Eero Koukkari
Seppo Nousiainen
Juha Vasanoja
Martti Kainulainen
Jukka KYLLÖNEN
Teuvo Haukipuro
Esa Niemitalo
Harri Tikka
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Nokia Oyj
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Nokia Telecommunications Oy
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    • H—ELECTRICITY
    • H03—ELECTRONIC CIRCUITRY
    • H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS
    • H03H7/00—Multiple-port networks comprising only passive electrical elements as network components
    • H03H7/46—Networks for connecting several sources or loads, working on different frequencies or frequency bands, to a common load or source
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
    • H01P1/00—Auxiliary devices
    • H01P1/20—Frequency-selective devices, e.g. filters
    • H01P1/213—Frequency-selective devices, e.g. filters combining or separating two or more different frequencies

Definitions

  • the invention relates to a device for adjusting a combiner filter, comprising means for receiving a first sample signal proportional to forward RF power to the combiner filter and a second sample signal proportional to RF power reflected from the combiner filter; a first frequency-selective detector means for detecting the magnitude of the forward power by means of said first sample signal; a second frequency-selective detector means for detecting the magnitude of the reflected power by means of said second sample signal; a control means for adjusting the centre frequency of the combiner filter in response to the detection results of the detector means.
  • One known way to connect several radio transmitters to the same antenna or antenna line is to connect each radio transmitter through a separate bandpass filter having its centre frequency tuned to the transmitting frequency of the radio transmitter.
  • bandpass filters are called combiner filters.
  • the function of the combiner filter is to feed the transmitting signal of the respective radio transmitter to the antenna with the smallest possible losses and prevent the leakage of transmitting signals of different frequencies from other radio transmitters, from the direction of the antenna, to this particular radio transmitter as efficiently as possible.
  • combiner bandpass filters are tuned fixedly to the transmitting frequencies of the radio transmitters. So it has not been possible to change the transmitting frequency of the radio transmitter without simultaneously changing the combiner filter or its tuning.
  • the frequencies of radio transmitters can be changed simply and rapidly.
  • One such case is the base station of a cellular mobile radio system to which predetermined transmitting and receiving channels have been assigned.
  • the channel allocation of the system can be altered, if desired, by varying the transmitting and receiving frequencies of the base stations, the channel capacity of the system can be utilized in a flexible and efficient way in varying conditions. Therefore combiner filters have been developed in which the centre frequency changes automatically with the transmitting frequency.
  • the adjustment of known automatically tunable combiner filters is based on measuring RF power reflected from the input of the filter or RF power passing through the combiner filter, and on locking to a minimum/maximum value of the measured power.
  • a problem with this adjustment method is, however, the low adjusting accuracy and the narrow dynamic range.
  • the frequency selectivity of the entire adjusting system relies on the combiner filter, power components of other radio transmitters leaking through the combiner filter to its input cause the minimum reflection suppression value of the reflection suppression measurement at the filter input to be about 7 dB, which results in a narrow dynamic range for the measurement.
  • the measuring dynamics of the maximum power value also remains low for the same reasons as above.
  • the automatically tunable combiner filter based on this prior art adjustment method does not allow variation in the relative power levels between the radio transmitters, that is, the "mutual dynamics" is almost 0 dB, as a change in the power level of one transmitter affects immediately the power measurement in the adjustment circuits of the combiner filters of the other radio transmitters, thus causing adjustment error.
  • Finnish Patent Application 912 255 discloses an adjusting arrangement where the frequency selectivity of the measurement of the RF power passing through or reflected has been increased by mixing the RF measuring signal of the same frequency, i.e. a transmitting-frequency signal, so that a substantially zero-frequency signal, i.e. a DC signal, is obtained, which has a level proportional to the RF power reflected from the input or to the RF power passing through the filter.
  • Power components leaking from the transmitting frequencies of other radio transmitters appear in the mixing result e.g. at a frequency of 300 kHz or at higher frequencies, which are filtered off in the lowpass filtration following the mixing.
  • the invention provides a measuring signal the level of which depends merely on the transmitting-frequency RF power component to be measured, whereas the measuring signal is not affected by the transmitting signals of other radio transmitters.
  • One object of the invention is a device by means of which a plurality of combiner filters are tuned jointly.
  • said receiving means comprise at least two first inputs for the first sample signals of at least two different combiner filters
  • the measuring signals of a number of different combiner filters are multiplexed to the same detector means. Multiplexing simplifies considerably the measuring and adjusting electronics of the tuning and adjusting means of combiner filters, especially with a high number of combiner filters. Other advantages include the more advantageous price, a smaller requirement of service and smaller size and lower weight.
  • the multiplexing of measuring signals is used primarily to select the sample signals of the forward and reflected power of one and the same combiner filter to be tuned for the measuring electronics.
  • One advantage of the multiplexing structure according to the invention is, however, that the controls of the first and the second selector means are independent of each other, which also allows isolation measurement between different channels.
  • the sample signal of the forward power of one combiner filter and the sample signal of the reflected power of another combiner filter are thereby connected to the measuring electronics. When both sample signals undergo frequency-selective detection at the same frequency, the degree of isolation between the radio channels will be determined.
  • a preferred embodiment of the invention includes a method for performing isolation measurement on radio transmitters using the device of the invention, the radio transmitter being isolated by combiner filters.
  • the method is characterized in that it comprises the steps of:
  • radio transmitters Tx1...Txn having transmitting frequencies f 1 ...f n are connected through bandpass filters 1 1 , 1 2 ,...1 n tuned to the respective frequencies to a common summing point P1 and further through an antenna line to a common transmitting antenna ANT.
  • a radio-frequency (RF) signal applied to the transmitting antenna ANT comprises the frequencies f 1 ...f n of all the transmitters.
  • the transmitting frequencies f 1 ...f n are within the range 920-960 MHz, for instance.
  • Such bandpass filters connecting several transmitters to a common antenna are generally referred to as combiner filters.
  • the combiner filter allows the transmitting signal of its own transmitter to pass to the antenna line with losses as small as possible, while it at the same time prevents efficiently the entrance of the transmitting signals of different frequencies from other transmitters to its own transmitter.
  • the invention will be described below in connection with combiner filters, in which it can be particularly advantageously applied, but the invention can also be applied in filters intended for other purposes when frequency selective power measurement is required in the frequency adjustment.
  • FIG. 2 showing an arrangement according to the invention for adjusting combiner filters will now be referred to.
  • the arrangement comprises combiner blocks 1 1 , 1 2, ...,1 n , of which only block 1 1 , selection blocks 21 and 22, detection block 23, and control block 24 are shown for the sake of clarity.
  • the tuning of the combiner filter is based on the measurement of a radio-frequency transmitting signal to determine the forward power Pf passing to an individual combiner filter and the power Pr reflected from the filter.
  • the power of the forward signal to the combiner filter and that of the signal reflected from the combiner filter are compared with each other, and the centre frequency of the filter is adjusted such that the proportion of the power reflected from the filter to the transmitter power is at minimum.
  • the proportion of the power transmitted to the antenna is thus as large as possible.
  • the tuning of the combiner filter is performed by a stepper motor adjuster, which is programmed to be controlled by the control unit 24 in response to the measuring signal data concerning the forward and reflected power.
  • Each combiner block 1 1 , 1 2 ,...,1 n contains a combiner filter 10 adjusted by a stepper motor. After the filters 10 the transmitter lines are summed electrically by transmission lines of a predetermined length and applied to the antenna line. All transmitter branches comprise circulator means 11 between the transmitters and the combiner filters 10 so as to reduce the connecting of the transmitters from the antenna line to other transmitters. The circulator means 11 also derive radio-frequency samples required for the adjusting procedure from the forward power passing to the combiner filter (sample signals Pf1... Pfn) and from the power reflected from it (sample signals Pr1...Prn).
  • the combiner filter blocks have a common adjusting equipment by means of which the combiner blocks are tuned one by one. Therefore the radio-frequency measuring signals Pf1...Pfn and Pr1...Prn from the circulator means 11 of the combiner blocks have to be selected for further processing. Selections are made in the selection block 22 for the forward power Pf and in the selection block 21 for the reflected power Pr. In the selection block 22 the signal of the combiner filter to be tuned next is selected by switches S1-Sn on the basis of control provided over the four-line control bus 22A of the control unit 24. Correspondingly, in the selection block 21, the signal Pr of the combiner filter to be tuned next is selected by switches S1-Sn (e.g.
  • the selected signals Pf and Pr are applied to mixers 220 and 210, respectively, by means of which the radio-frequency signals to be measured are mixed to a zero intermediate frequency.
  • Local oscillator signals LO needed in the mixing are obtained from a synthesizer 230 provided in the detection block 23 and operating at the centre frequency of the transmitter channel to be tuned next.
  • the synthesizer 230 obtains its channel control data from the control block via a bus 24A.
  • the mixing forms the RF input signals Pf and Pr into zero-intermediate-frequency measuring signals IFF and IFR, in which the spectral components caused by the channel to be measured are at a frequency below 150 kHz and the levels of which are proportional to the levels of the radio-frequency signals Pf and Pr to be measured.
  • the mixing allows frequency-selective power measurement.
  • the low-frequency spectral components caused by the transmitting signals of other transmitters connected to the combiner system occur at frequencies above 500 kHz, and they can be filtered off by means of a lowpass filter 211 and 221 provided at the output of each selection block, respectively.
  • the filtered intermediate-frequency signals IFR and IFF are applied to the detection block 23.
  • the function of the detection block 23 is to detect the magnitude of the forward power to the combiner filter to be tuned next and that of the power reflected from the combiner filter from the intermediate-frequency signals IFF and IFR obtained from selector cards.
  • the detection block 23 may have a structure such as shown in Figure 2, for instance, where the forward power measuring branch from the input IFF to the output UF2 and the reflected power measuring branch from the input IFR to the output UR2 are mutually identical in signal processing. These measuring branches are used for the continuous fine-adjustment of the combiner filter.
  • the measuring branch of the detection block from the input IRF to the output UR1 is used when the combiner is taken into use, whereby the output signal of the transmitter is a test signal with a transmission of equal power in each time slot.
  • the output signals UF2, UR1 and UR2 from the detection block 23 are applied to the control block 24, where the A/D conversion is performed and the tuning state of the combiner to be adjusted next is calculated from the output signals.
  • the control unit 24 has a dedicated control output for each combiner filter 10 for controlling the stepper motor.
  • the multiplexing of measuring signals is used primarily to select the sample signals of the forward and reflected power of one and the same combiner filter to be tuned for the measuring electronics.
  • One advantage of the multiplexing structure according to the invention is, however, that the controls of the first and the second selector means are independent of each other, which also allows isolation measuring between different channels. In such a case the sample signal of the forward power of one combiner filter and the sample signal of the reflected power of another combiner filter are connected to the measuring electronics. When both sample signals undergo frequency-selective detection at the same frequency, the degree of isolation between the radio channels will be determined.
  • f 1 -frequency leakages caused by the transmitter Tx1 ( Figure 1), having a radio channel at the frequency f 1 , in the radio channels of the adjacent transmitters Tx2...Txn will be explained.
  • the function of the combiner filter is to prevent or minimize the leakages of transmitting signals of different frequencies from other transmitters in the direction of the antenna ANT to its own transmitter, no efficient isolation is obtained between the transmitters Tx1..Txn with small channel spacings.
  • the combiner filter 1 2 has a finite suppression on the stop band.
  • a portion of the transmitting signal of the transmitter Tx1 is able to pass through the combiner filter 10 of the transmitter Tx2 in the direction of the transmitter Tx2 to an isolator 11.
  • This "reflected" signal can be measured in a manner similar to the measuring of the Tx2 transmitting signal portion reflected from the combiner filter 10 in tuning measurement.
  • Isolation measuring takes place by a measuring circuitry shown in Figure 2 in the following way.
  • the synthesizer 230 is commanded to the channel f 1 of the transmitter Tx1, and the forward power selection block 22 selects a sample signal P f1 of the forward power of the transmitter Tx1 for down-conversion by the mixer 220.
  • the reflected power selection block 21 selects a sample signal P r of the reflected power of an adjacent transmitter under examination, e.g. Tx2, for down-conversion by the mixer 210.
  • Down-conversion makes the measuring process frequency-selective, that is, the signal of the channel f 1 can be extracted from both of the selected sample signals for detection.
  • the detection block 23 forms detection results UR2 and UF2, respectively, from which, after the A/D conversion, the control block 24 calculates the proportion of the power leaked from the transmitter Txl in the direction of the transmitter under examination, e.g. Tx2.
  • the switches S1-Sn of the selection blocks 21 and 22 can be realized e.g. by using RF relays as switches or by using switches and transmission lines of a predetermined length.
  • a problem with relay selections, however, is the large mechanical size and high price.
  • Multiplexing switching arrangements containing transmission lines of a predetermined length in practice, electrically multiples of a quarter wave), in turn, are large in size when made from conventional printed circuit board materials.
  • the selection blocks 21 and 22 are realized by a circuit shown in Figure 3, comprising RF signal inputs RF1...RFN for the sample signals P f1 ...P fn or P r1 ...P rn , respectively.
  • Each input RF1...RFN is connected by a respective diode switch D1...Dn to a summing transmission line 31 operating as a radio-frequency switching and transmission means connected to the output 32 of the selection circuit.
  • One switch diode D1...Dn at a time is caused to conduct so that the selected diode allows the passage of the signal to be measured from the selected input to the summing transmission line 31.
  • the signal On the transmission line 31 the signal is divided into two portions equal in size, which start to propagate to the opposite ends of the transmission line 31. Both ends of the transmission line exhibit a load corresponding with the specific impedance of the transmission line (e.g. 50 Ohm), so that no significant amount of power is reflected from the end of the transmission line.
  • the specific impedance of the transmission line e.g. 50 Ohm
  • the diodes D1...Dn which are not switched to conduct appear in the direction of the transmission line as low capacitances.
  • the stray capacitance of this particular diode can be compensated by an LC circuit (not shown) connected in parallel with the diode.
  • An alternative way to compensate for the stray capacitance is to use the diode switches D1...Dn to form part of the capacitive portion of the transmission line 31, in which case the stray capacitance can be compensated by the layout design of the printed circuit board. This way, however, requires that the diode switches D1...Dn can be positioned with small spacings as compared with the wave length of the sample signal to be switched.
  • the control of the switch diodes D1...Dn is realized by DC or DC voltage generators (not shown), which apply a forward current control to control inputs SEL1...SELn for opening the switch diode D1...Dn or a reverse voltage control for closing the switch diode D1...Dn.
  • the controls SEL are connected via coils L1...Ln so that the coil feeding at the frequency of the sample signal to be connected will not load the transmission line.
  • the switching current applied to the transmission line 31 through the switch diode has to be transferred away from the transmission line 31 without loading it.
  • Capacitors C1...Cn and Cs1 and Cs2 are coupling capacitors.

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  • Transmitters (AREA)
  • Networks Using Active Elements (AREA)
  • Filters And Equalizers (AREA)
  • Measurement Of Resistance Or Impedance (AREA)
  • Monitoring And Testing Of Transmission In General (AREA)
  • Channel Selection Circuits, Automatic Tuning Circuits (AREA)
  • Input Circuits Of Receivers And Coupling Of Receivers And Audio Equipment (AREA)
  • Radar Systems Or Details Thereof (AREA)

Claims (9)

  1. Dispositif pour régler un filtre mélangeur, comprenant :
    des moyens pour recevoir un premier signal d'échantillon (Pf) proportionnel à la puissance RF directe appliquée au filtre mélangeur (10), et un deuxième signal d'échantillon (Pr) proportionnel à la puissance RF réfléchie par le filtre mélangeur ;
    un premier moyen de détection sélectif en fréquence (220, 233B) pour détecter la valeur de la puissance directe au moyen du premier signal d'échantillon (Pf) ;
    un deuxième moyen de détection sélectif en fréquence (210, 233A) pour détecter la valeur de la puissance réfléchie au moyen du deuxième signal d'échantillon (Pr) ;
    un moyen de commande (24) pour régler la fréquence centrale du filtre mélangeur en réponse aux résultats des moyens de détection ;
    caractérisé en ce que les moyens de réception comprennent :
    au moins deux premières entrées pour les premiers signaux d'échantillon (Pf) d'au moins deux filtres mélangeurs différents ;
    un premier moyen de sélection (22) pour connecter le signal choisi parmi les premiers signaux d'échantillon (Pr) sélectivement aux premiers moyens de détection (220, 233B) ;
    au moins deux deuxièmes entrées pour les deuxièmes signaux d'échantillon (Pr) des deux filtres mélangeurs différents;
    un deuxième moyen de sélection (21) pour connecter le signal choisi parmi les deuxièmes signaux d'échantillon (Pr) sélectivement aux deuxièmes moyens de détection (210, 233A).
  2. Dispositif selon la revendication 1,
    caractérisé en ce que les moyens de sélection (21, 22) réagissent au moyen de commande (24) pour sélectionner alternativement les couples de premiers et deuxièmes signaux d'échantillon des filtres mélangeurs.
  3. Dispositif selon la revendication 1 ou 2,
    caractérisé en ce que les commandes du premier et du deuxième moyen de sélection (21, 22) sont indépendantes l'une de l'autre.
  4. Dispositif selon la revendication 3,
    caractérisé en ce que le dispositif présente un état de mesure dans lequel le premier moyen de sélection (21) sélectionne le premier signal d'échantillon du filtre mélangeur à accorder, et le deuxième moyen de sélection (22) sélectionne le deuxième signal d'échantillon du filtre mélangeur à accorder, en vue de la détection et du calcul d'un coefficient de réflexion.
  5. Dispositif selon l'une quelconque des revendications précédentes,
    caractérisé en ce que le dispositif présente un état de mesure de l'interférence dans lequel le premier moyen de sélection (21) sélectionne le premier signal d'échantillon du filtre mélangeur à accorder, et le deuxième moyen de sélection (22) sélectionne le deuxième signal d'un autre filtre mélangeur.
  6. Dispositif selon l'une quelconque des revendications précédentes,
    caractérisé en ce que les premier et deuxième moyens de détection sélectifs en fréquence comprennent tous les deux des moyens mélangeurs (210, 220) pour la transposition par abaissement de fréquence des signaux d'échantillon RF avant la détection.
  7. Dispositif selon l'une quelconque des revendications précédentes,
    caractérisé en ce que les deux moyens de sélection comprennent :
    au moins deux entrées RF (RF1, RFn), et une sortie RF (32) ;
    une ligne sommatrice d'émission (31) connectée à la sortie (32) des moyens de sélection ;
    une diode de commutation (D1-Dn) connectée entre la ligne sommatrice d'émission (31) et chaque entrée RF ;
    des moyens pour commander sélectivement l'une des diodes de commutation à la fois pour les rendre conductrices en vue de commuter les signaux RF des entrées RF vers la ligne sommatrice d'émission.
  8. Procédé pour effectuer des mesures d'isolation sur des émetteurs radio en utilisant le dispositif de la revendication 1, les émetteurs radio étant isolés par des filtres mélangeurs,
    caractérisé en ce que le procédé comprend :
    la détection sélective en fréquence, en utilisant le premier moyen de détection (220, 233B), de la puissance d'un signal RF direct avec une première fréquence arrivant à une entrée d'un premier filtre mélangeur (I1) accordé à la première fréquence ;
    la détection sélective en fréquence, en utilisant le deuxième moyen de détection (210, 233A), de la puissance d'une composante de signal RF avec la première fréquence s'échappant de la sortie d'un deuxième filtre mélangeur (l2) accordé à une deuxième fréquence, vers une entrée de celui-ci ;
    la détermination (24), au moyen des résultats de détection (UR1, UR2, UF2), de la proportion de puissance directe s'échappant vers un autre émetteur.
  9. Procédé selon la revendication 8,
    caractérisé en ce que la détection sélective en fréquence comprend la transposition par abaissement de fréquence (210, 220) des signaux RF avant la détection.
EP94902794A 1992-12-30 1993-12-29 Dispositif et procede d'accord d'un filtre melangeur Expired - Lifetime EP0647373B1 (fr)

Applications Claiming Priority (3)

Application Number Priority Date Filing Date Title
FI925956 1992-12-30
FI925956A FI94690C (fi) 1992-12-30 1992-12-30 Laite kompainerisuodattimen virittämiseksi ja menetelmä erotusmittauksen suorittamiseksi
PCT/FI1993/000567 WO1994016497A1 (fr) 1992-12-30 1993-12-29 Dispositif et procede d'accord d'un filtre melangeur

Publications (2)

Publication Number Publication Date
EP0647373A1 EP0647373A1 (fr) 1995-04-12
EP0647373B1 true EP0647373B1 (fr) 1998-08-26

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US (1) US5525940A (fr)
EP (1) EP0647373B1 (fr)
JP (1) JP3078839B2 (fr)
AT (1) ATE170346T1 (fr)
AU (1) AU674375B2 (fr)
DE (1) DE69320636T2 (fr)
FI (1) FI94690C (fr)
NO (1) NO306889B1 (fr)
WO (1) WO1994016497A1 (fr)

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JP2728018B2 (ja) * 1995-04-18 1998-03-18 日本電気株式会社 送信回路
FI107766B (fi) * 1998-01-28 2001-09-28 Nokia Networks Oy Viritysmenetelmä ja lähetinvastaanotinyksikkö
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US7327406B2 (en) * 2001-10-16 2008-02-05 Rfstream Corporation Methods and apparatus for implementing a receiver on a monolithic integrated circuit
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JP2005536080A (ja) * 2002-05-29 2005-11-24 株式会社ＲｆＳｔｒｅａｍ 画像除去２次フィルタ
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US20050012676A1 (en) * 2003-07-16 2005-01-20 Mccarthy Robert Daniel N-port signal divider/combiner
US6940365B2 (en) * 2003-07-18 2005-09-06 Rfstream Corporation Methods and apparatus for an improved discrete LC filter
US7446631B2 (en) * 2005-03-11 2008-11-04 Rf Stream Corporation Radio frequency inductive-capacitive filter circuit topology
CN101138160A (zh) * 2005-03-11 2008-03-05 Rf信息公司 宽带调谐电路
US7358795B2 (en) * 2005-03-11 2008-04-15 Rfstream Corporation MOSFET temperature compensation current source
DE102009018648B4 (de) * 2009-04-23 2018-11-29 Snaptrack, Inc. Frontendmodul mit Antennentuner
US9136815B2 (en) 2012-06-13 2015-09-15 Nokia Technologies Oy Methods and apparatuses for implementing variable bandwidth RF tracking filters for reconfigurable multi-standard radios
US9136825B2 (en) * 2012-06-13 2015-09-15 Nokia Technologies Oy Method and device for implementing tracking filters and RF front end of software defined radios
US9407482B2 (en) 2013-11-11 2016-08-02 Nokia Technologies Oy Tunable RF N-path filter

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Publication number Publication date
FI94690B (fi) 1995-06-30
ATE170346T1 (de) 1998-09-15
NO943192D0 (no) 1994-08-29
NO943192L (no) 1994-10-28
JP3078839B2 (ja) 2000-08-21
AU5701394A (en) 1994-08-15
EP0647373A1 (fr) 1995-04-12
FI925956A0 (fi) 1992-12-30
US5525940A (en) 1996-06-11
AU674375B2 (en) 1996-12-19
DE69320636T2 (de) 1999-02-11
JPH07504557A (ja) 1995-05-18
FI925956A (fi) 1994-07-01
NO306889B1 (no) 2000-01-03
DE69320636D1 (de) 1998-10-01
FI94690C (fi) 1995-10-10
WO1994016497A1 (fr) 1994-07-21

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