EP0439240A2 - Ballast électronique - Google Patents

Ballast électronique Download PDF

Info

Publication number
EP0439240A2
EP0439240A2 EP91250009A EP91250009A EP0439240A2 EP 0439240 A2 EP0439240 A2 EP 0439240A2 EP 91250009 A EP91250009 A EP 91250009A EP 91250009 A EP91250009 A EP 91250009A EP 0439240 A2 EP0439240 A2 EP 0439240A2
Authority
EP
European Patent Office
Prior art keywords
voltage
circuit
electronic ballast
transistor
control circuit
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP91250009A
Other languages
German (de)
English (en)
Other versions
EP0439240B1 (fr
EP0439240A3 (en
Inventor
Dieter Dipl.-Ing. Albert
Peter Prof. Dr.-Ing. Marx
Burkhard Prof. Dr.-Ing. Karstädt
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Semperlux GmbH
Original Assignee
Semperlux GmbH
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Priority claimed from DE19904001549 external-priority patent/DE4001549A1/de
Application filed by Semperlux GmbH filed Critical Semperlux GmbH
Publication of EP0439240A2 publication Critical patent/EP0439240A2/fr
Publication of EP0439240A3 publication Critical patent/EP0439240A3/de
Application granted granted Critical
Publication of EP0439240B1 publication Critical patent/EP0439240B1/fr
Anticipated expiration legal-status Critical
Expired - Lifetime legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/2825—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage
    • H05B41/2828—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage using control circuits for the switching elements

Definitions

  • the invention relates to an electronic ballast for low-pressure discharge lamps supplied from direct and alternating voltage networks according to the preamble of the main claim.
  • an electronic ballast which has an inverter in a half-bridge circuit which feeds at least one lamp, a capacitive reactance connected in parallel with the lamp and an inductive resistor connected in series with the lamp and capacitive reactance.
  • the power transistors of the inverter in the half-bridge circuit are controlled digitally by a control circuit having two control circuits, two control voltages offset by a half-period, between which there is a pulse gap, being generated.
  • the DC voltage is supplied via an isolating transformer with two galvanically isolated ones Secondary windings.
  • a circuit known as a step-up converter is used, which essentially consists of a memory inductor with two windings, a switching transistor, a diode, a charging capacitor and a sine control unit.
  • the invention has for its object to provide a dimmable electronic ballast for low-pressure discharge lamps with good efficiency, which is suitable for both DC and AC operation.
  • the step-up choke of the harmonic filter has an additional auxiliary winding, which is connected to a rectifier circuit and the capacitor of the DC voltage supply circuit for the digital drive circuit, the capacitor constantly charged and stabilized to the necessary supply voltage for the control circuit.
  • the DC voltage supply circuit connected to the harmonic filter has a first transistor which becomes conductive immediately after the supply voltage of the electronic ballast is switched on and charges the capacitor to the supply voltage of the control circuit, wherein the first transistor is blocked by a blocking circuit after charging the capacitor. In this way, the voltage required for supplying the control circuit is made available immediately after starting, both in direct voltage and alternating voltage operation.
  • the inductive reactance of the at least one lamp has two auxiliary windings which are electrically isolated from one another and are each connected to the electrodes of the lamp. This measure improves the dimming behavior compared to that of the prior art, since there the lamp electrodes were not sufficiently heated.
  • the circuit arrangement shown in FIG. 1 for an electronic ballast for low-pressure discharge lamps, in which the lamps are supplied with a high-frequency current in order to achieve a better luminous efficiency consists of an inverter 1 in a half-bridge circuit, a control circuit 2 for controlling the inverter, and a DC voltage supply circuit 3 , which supplies the supply voltage for the control circuit 2, and a harmonic filter 4, which limits the mains current harmonics.
  • the harmonic filter 4 designed as a step-up converter or step-up converter essentially consists of a step-up converter choke L3 with two windings N2, N3, each of which is connected to the connections of a bridge rectifier D5-D8, the other terminals 5, 6 of which are connected to a mains voltage or an HF -Filter lie, from a semiconductor switch designed as a switching transistor T3, a diode D9 connected to both the winding N3 of the step-up converter choke L3 and to the drain of the switching transistor T3 and a charging capacitor C5 connected to the diode D9, which is connected to ground and has a charging voltage of U Br has.
  • the switching transistor T3 is controlled via its gate connection by control logic IC2, which receives information regarding the input voltage
  • the step-up converter enables the continuous transformation of a DC input voltage
  • the control logic is designed such that a low harmonic, almost sinusoidal current is taken from the power supply network, wherein the power factor is almost 1 and a regulated DC voltage is available at the output.
  • the DC voltage supply circuit 3 has a trained as a self-locking N-channel MOS-FET transistor T4, the drain connection via a resistor R4 for current limitation to the terminal U Br and its source connection is connected to a capacitor C3, one designed as a Z diode Stabilizing diode D11 is connected to the gate terminal of transistor T4 and to the collector of a transistor T5, which is connected to terminal U Br via a resistor R5.
  • the emitter of the transistor T5, the Zener diode D11 and the capacitor C3 are connected to ground with their other connections.
  • the base of transistor T5 is connected via a resistor R6 to the connection between bridge rectifier D5-D8 and winding N3, and a parallel RC element C4, R7 is located parallel to the base-emitter path.
  • the capacitor C3 supplies at its terminal U V the DC voltage for supplying the control circuit 2.
  • the step-up converter choke L3 has an additional auxiliary winding N1, which is connected to the terminal U V via a resistor R3 and a bridge arm of the bridge rectifier D1 to D4 a further Z diode D10 is connected in parallel with the capacitor C3.
  • the control circuit 2 consists of an integrated pulse width modulation component IC1 and an integrated high-voltage half-bridge driver HVIC, which is explained in more detail below.
  • the PWM module IC1 eg IP 3535 A
  • the control circuit 2 is connected to the inverter 1, which has two half-bridge transistors T1, T2 in a known manner and the capacitive voltage divider C1, C2 in the second bridge branch.
  • the lamp arrangement 8, which is described in more detail below, lies in the bridge diagonal. With regard to the structure and function of the inverter, reference is also made to DE-OS 38 05 159.
  • the diodes D1 to D4 of the bridge circuit, the winding N3 of the step-up converter choke L3 and the diode D9 of the charging capacitor C5 reach approximately the peak value of the Mains voltage charged.
  • the charging voltage U Br at the charging capacitor C5 causes a positive voltage of 15 V to develop at the gate of the transistor T4 via the resistor R5 and the Zener diode D11, as a result of which the transistor T4 becomes conductive and the capacitor C3 switches to the voltage U V , namely about +15 V is charged. Since the transistor T4 is designed as a self-blocking N-channel MOS field-effect transistor, it blocks again immediately, because the voltage at the source and gate is approximately the same.
  • the transistor T4 If the transistor T4 has become conductive, the second transistor T5 is still blocked since the Capacitor C4 of the RC element is uncharged. After a time constant determined by the dimensioning of the resistors R6, R7 and C4, the transistor T5 becomes conductive and thereby blocks the transistor T4.
  • the capacitor C4 discharges through the resistor R7, the time constant of this RC element C4, R7 being selected such that the transistor T5 is ready to start again within one second after the mains voltage has been switched off is, ie is in the non-conductive state. This enables the electronic ballast to be switched on again quickly.
  • other connection options for the resistor R6 and the RC element R7, C4 are also conceivable, which ensure a controlled charging and discharging of the capacitor 4.
  • the arrangement described serves as a starting circuit so that a safe start is made possible when operating on direct or alternating voltage networks.
  • control circuit If the control circuit is supplied with the voltage U V via the start circuit just described, it starts to work and, as will be described further below, supplies two signals arranged offset to one another at its outputs. At the same time, the control circuit supplies 2 trigger signals to the control logic IC2, which switches the transistor T3, as a result of which the actual current flowing through the choke L3 (or N3) is superimposed by a high-frequency ripple current. This applies to both AC and DC voltage supply at terminals 5,6.
  • the capacitor C3 is charged during operation, specifically via the auxiliary winding N1, the resistor R3 and the bridge circuit D1 to D4.
  • the alternating voltage generated on the auxiliary winding N1 is rectified in two-way fashion via the resistor R3 with the bridge circuit D1 to D4.
  • the voltage on the capacitor C3 is stabilized to approximately 15 V using the Zener diode D10.
  • the pulse width modulation module, PWM module, IC1 essentially consists of a square-wave generator with a variable pulse duty factor and a downstream logic circuit, which is designed in such a way that at the outputs two pulses offset in time are supplied, a pulse gap being provided between the pulses, by which it is prevented that the downstream half-bridge transistors T1, T2 become conductive at the same time.
  • the pulse duty factor of the PWM module IC1 is changed by applying a DC voltage of variable size to the dimming input 7, i.e. the pulse gap between the two output signals of the PWM module IC1 is changed.
  • the output signals of the PWM module IC1 go to the high-voltage half-bridge driver HVIC, the structure and function of which is explained in more detail with reference to the circuit diagram in FIG. 3.
  • the integrated high-voltage bridge driver HVIC a so-called bootstrap circuit is used, which can be externally connected or integrated in different bridge drivers currently on the market.
  • the driver Tr2 is connected to the supply voltage U V
  • the driver Tr1 requires a supply voltage which takes into account that the load point between two transistors T1, T2 fluctuates between the voltages of approximately U Br and approximately OV.
  • the bootstrap circuit is provided, which consists of the diode D12, the protective resistor R8 connected in series and the capacitor C7, the capacitor C7 being connected on the one hand to the load point and on the other hand to the resistor R8, which is connected to the charging voltage U Br lies.
  • the diode D12 is connected to the supply voltage U V.
  • capacitor C7 can charge to approximately U V since the load point is approximately at ground.
  • T2 blocks and then conducts T1
  • the load point is approximately at U Br
  • a voltage of approximately U Br + U V is present at the capacitor, which results in a floating supply voltage for driver Tr1.
  • the switching signal for the transistor 1 supplied by the PWM module IC1 must also be adapted to the level differences between the voltage U Br and approximately OV.
  • the voltage level shift circuit S which is located between the signal output of the PWM module IC1 and the input of the driver Tr1, is used for this purpose. This level shift is used in the commercial HVICs Realized in different ways, for example the switching signal can be modulated or superimposed on a pulse signal with the level of U Br .
  • FIG. 5 shows a circuit in which the bootstrap circuit D12, R8 and C7 as in FIG. 3 are also used.
  • an optocoupler OC is provided which controls the driver Tr3 for the transistor T1 using potential isolation.
  • the driver Tr4 receives the switching signal directly from the PWM module IC1.
  • the voltage U Br which is halved by the capacitors, is present at the capacitors C1, C2 of the inverter 1.
  • the transistors T1, T2 are mutually switched to the conductive or the blocked state, and the circuit of the discharge lamps is driven with a high-frequency square-wave voltage.
  • this discharge lamp circuit 8 consists of at least one discharge lamp LL, to which a capacitor C is connected in parallel, the parallel connection being in series with an inductance L. Of course, several such arrangements can be provided in parallel.
  • an attenuator is connected in parallel with the lamp electrodes a resistor R and a diode D, the resistor R being an ohmic or complex resistor or another resistor or a combination.
  • This damping element improves the dimming behavior of the discharge lamp LL, since so-called "running layers", ie visually disturbing instabilities of the arc discharge, are avoided with lamps dimmed very far, ie below 10% of the maximum brightness.
  • FIG. 2 shows a further exemplary embodiment, the harmonic filter 4 and the DC voltage supply circuit 3 according to FIG. 1 being omitted for the sake of simplicity.
  • the discharge lamp circuit 8 consists of two fluorescent lamps LL1 and LL2 with correspondingly connected capacitors C7, C8 and the attenuator R, D and the inductors L1 and L2 connected in series.
  • two auxiliary windings L1 'and L1 ", as well as L2' and L2", which are galvanically separated from one another, are provided.
  • the auxiliary windings L1 'and L1 "or L2', L2" are connected to the two electrodes of each fluorescent lamp LL1, LL2, whereby an improvement in the heating of the electrodes is achieved. These measures therefore sufficiently heat the electrodes even when dimming.
  • the capacitors C1, C2 according to FIG. 1 are replaced by capacitors C. each lying in series with the lamp and the inductors.
  • the pulse duty factor of the PWM module IC1 is usually changed via a variable DC voltage at the dimming input 7.
  • the disadvantage here is that there is no electrical isolation between the dimmer or brightness controller and the lamp. 2, therefore, an optocoupler IC3 with a downstream low-pass filter R1, C6 is used, the light-emitting diode of the optocoupler being led via a resistor R2 to the terminals 9, 10 of the electronic ballast EVG1 for connection to the dimmer transmitter.
  • the external dimmer is also provided as a PWM module 11, whose duty cycle is changed for brightness control.
  • the pulse signals supplied by the PWM module 11 are transmitted by the optocoupler IC3 and smoothed by the low-pass filter R1, C6, so that a variable DC voltage is again present at the dimming input.
  • several electronic ballasts EVGn can be dimmed by the PWM module 11 by connecting the terminals 9, 10 in parallel.
  • rectifier bridges can be provided in the ballasts, which are connected to the terminals 9, 10.
  • the external dimmer 11 can also be used with an integrated PWM control module for brightness control, wherein, as indicated in FIG. 2, several electronic ballasts can also be dimmed by connecting the terminals 9, 10 in parallel.

Landscapes

  • Circuit Arrangements For Discharge Lamps (AREA)
  • Discharge-Lamp Control Circuits And Pulse- Feed Circuits (AREA)
  • Mechanical Treatment Of Semiconductor (AREA)
  • Glass Compositions (AREA)
  • Furan Compounds (AREA)
  • Organic Insulating Materials (AREA)
  • Discharge Heating (AREA)
  • Non-Silver Salt Photosensitive Materials And Non-Silver Salt Photography (AREA)
EP91250009A 1990-01-20 1991-01-17 Ballast électronique Expired - Lifetime EP0439240B1 (fr)

Applications Claiming Priority (4)

Application Number Priority Date Filing Date Title
DE19904001549 DE4001549A1 (de) 1990-01-20 1990-01-20 Elektronisches vorschaltgeraet zum betrieb von entladungslampen
DE4001549 1990-01-20
DE4018865 1990-06-13
DE4018865A DE4018865A1 (de) 1990-01-20 1990-06-13 Elektronisches vorschaltgeraet zum betrieb von entladungslampen

Publications (3)

Publication Number Publication Date
EP0439240A2 true EP0439240A2 (fr) 1991-07-31
EP0439240A3 EP0439240A3 (en) 1992-08-19
EP0439240B1 EP0439240B1 (fr) 1995-06-21

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ID=25889237

Family Applications (1)

Application Number Title Priority Date Filing Date
EP91250009A Expired - Lifetime EP0439240B1 (fr) 1990-01-20 1991-01-17 Ballast électronique

Country Status (3)

Country Link
EP (1) EP0439240B1 (fr)
AT (1) ATE124202T1 (fr)
DE (2) DE4018865A1 (fr)

Cited By (17)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0535911A1 (fr) * 1991-09-30 1993-04-07 Toshiba Lighting & Technology Corporation Circuit d'alimentation pour une lampe à décharge
EP0564895A1 (fr) * 1992-04-06 1993-10-13 Starkstrom-Elektronik Ag Ballast électronique pour lampes à décharge basse-pression
DE4328306A1 (de) * 1993-08-23 1994-03-17 Spindler Bernhard Dipl Ing Schaltungsanordnung zur Einstellung und Regelung des Betriebszustandes von Niederdruckentladungslampen im Hochfrequenz- und Niederfrequenzbetrieb
EP0620700A1 (fr) * 1993-04-15 1994-10-19 Heinrich Korte Ballast électronique
DE4426258A1 (de) * 1993-07-27 1995-02-02 Matsushita Electric Works Ltd Umrichter
DE4406000A1 (de) * 1994-02-24 1995-08-31 Hilite Lighting And Electronic Dimmerschaltung für Gasentladungslampen mit elektronischen Vorschaltgeräten
DE29605087U1 (de) * 1996-03-19 1996-08-08 Trilux Lenze Gmbh & Co Kg Leuchtstofflampen-Vorschaltgerät mit Hochsetzsteller
DE29609839U1 (de) * 1996-06-04 1996-08-22 Trilux Lenze Gmbh & Co Kg Leuchtstofflampen-Vorschaltgerät
DE19543419A1 (de) * 1995-11-21 1997-05-22 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Verfahren und Schaltungsanordnung zum Betreiben von Kaltkathoden-Glimmleuchtstofflampen
EP0808086A1 (fr) * 1996-05-13 1997-11-19 General Electric Company Ballast en demi-pont pour lampes à décharge, attaqué par un circuit intégré à haute tension
EP1231821A1 (fr) * 2001-02-09 2002-08-14 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Ballast pour lampes électriques
EP1280388A1 (fr) * 2001-07-16 2003-01-29 TridonicAtco GmbH & Co. KG Ballast électronique avec un mode de préchauffage
EP1309229A2 (fr) 1997-05-16 2003-05-07 Denso Corporation Appareil haute-tension pour lampe à décharge
WO2008128575A1 (fr) * 2007-04-23 2008-10-30 Osram Gesellschaft mit beschränkter Haftung Circuiterie permettant de faire fonctionner au moins une lampe à décharge et procédé de production d'une tension auxiliaire
DE102007058982A1 (de) * 2007-12-07 2009-06-10 Tridonicatco Gmbh & Co. Kg Betriebsgerätsschnittstelle zur Spannungsversorgung
WO2012143906A2 (fr) 2011-04-22 2012-10-26 Koninklijke Philips Electronics N.V. Circuit d'alimentation électrique pour convertisseur pfc
EP2854484A1 (fr) * 2013-09-27 2015-04-01 Toshiba Lighting & Technology Corporation Circuit d'alimentation électrique et luminaire

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0059064B1 (fr) * 1981-02-21 1985-10-02 THORN EMI plc Circuit de démarrage et d'exploitation de lampes
EP0318110A1 (fr) * 1987-11-27 1989-05-31 Koninklijke Philips Electronics N.V. Circuit onduleur en pont
DE3913033A1 (de) * 1988-04-20 1989-11-16 Zumtobel Ag Vorschaltgeraet fuer eine gasentladungslampe
WO1990011005A1 (fr) * 1989-03-10 1990-09-20 Harel Jean Claude Dispositif electronique de demarrage et d'alimentation pour tubes fluorescents a electrodes prechauffables

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0059064B1 (fr) * 1981-02-21 1985-10-02 THORN EMI plc Circuit de démarrage et d'exploitation de lampes
EP0318110A1 (fr) * 1987-11-27 1989-05-31 Koninklijke Philips Electronics N.V. Circuit onduleur en pont
DE3913033A1 (de) * 1988-04-20 1989-11-16 Zumtobel Ag Vorschaltgeraet fuer eine gasentladungslampe
WO1990011005A1 (fr) * 1989-03-10 1990-09-20 Harel Jean Claude Dispositif electronique de demarrage et d'alimentation pour tubes fluorescents a electrodes prechauffables

Cited By (28)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0535911A1 (fr) * 1991-09-30 1993-04-07 Toshiba Lighting & Technology Corporation Circuit d'alimentation pour une lampe à décharge
US5334915A (en) * 1991-09-30 1994-08-02 Toshiba Lighting & Technology Corporation Operating circuit arrangement for a discharge lamp
EP0564895A1 (fr) * 1992-04-06 1993-10-13 Starkstrom-Elektronik Ag Ballast électronique pour lampes à décharge basse-pression
EP0620700A1 (fr) * 1993-04-15 1994-10-19 Heinrich Korte Ballast électronique
DE4426258A1 (de) * 1993-07-27 1995-02-02 Matsushita Electric Works Ltd Umrichter
DE4426258B4 (de) * 1993-07-27 2004-10-21 Matsushita Electric Works, Ltd., Kadoma Umrichter
DE4328306A1 (de) * 1993-08-23 1994-03-17 Spindler Bernhard Dipl Ing Schaltungsanordnung zur Einstellung und Regelung des Betriebszustandes von Niederdruckentladungslampen im Hochfrequenz- und Niederfrequenzbetrieb
DE4406000A1 (de) * 1994-02-24 1995-08-31 Hilite Lighting And Electronic Dimmerschaltung für Gasentladungslampen mit elektronischen Vorschaltgeräten
US5500573A (en) * 1994-02-24 1996-03-19 Hilite Lighting And Electronics Ltd. Dimmer circuit for gas discharge lamps having electronic ballasts
US5900700A (en) * 1995-11-21 1999-05-04 Patent-Treuhand-Gesellschaft Fur Elektrische Gluhlampen Mbh Process and circuit arrangement for operating cold cathode discharge lamps
DE19543419A1 (de) * 1995-11-21 1997-05-22 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Verfahren und Schaltungsanordnung zum Betreiben von Kaltkathoden-Glimmleuchtstofflampen
DE29605087U1 (de) * 1996-03-19 1996-08-08 Trilux Lenze Gmbh & Co Kg Leuchtstofflampen-Vorschaltgerät mit Hochsetzsteller
EP0808086A1 (fr) * 1996-05-13 1997-11-19 General Electric Company Ballast en demi-pont pour lampes à décharge, attaqué par un circuit intégré à haute tension
DE29609839U1 (de) * 1996-06-04 1996-08-22 Trilux Lenze Gmbh & Co Kg Leuchtstofflampen-Vorschaltgerät
EP1309229A3 (fr) * 1997-05-16 2011-06-22 Denso Corporation Appareil haute-tension pour lampe à décharge
EP1309229A2 (fr) 1997-05-16 2003-05-07 Denso Corporation Appareil haute-tension pour lampe à décharge
EP1231821A1 (fr) * 2001-02-09 2002-08-14 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH Ballast pour lampes électriques
AU780599B2 (en) * 2001-02-09 2005-04-07 Osram Ag Ballast for operating electric lamps
EP1280388A1 (fr) * 2001-07-16 2003-01-29 TridonicAtco GmbH & Co. KG Ballast électronique avec un mode de préchauffage
WO2008128575A1 (fr) * 2007-04-23 2008-10-30 Osram Gesellschaft mit beschränkter Haftung Circuiterie permettant de faire fonctionner au moins une lampe à décharge et procédé de production d'une tension auxiliaire
CN101658074B (zh) * 2007-04-23 2013-11-20 奥斯兰姆有限公司 驱动至少一个放电灯的电路装置和产生辅助电压的方法
KR101387051B1 (ko) * 2007-04-23 2014-04-18 오스람 게엠베하 적어도 하나의 방전 램프를 동작시키기 위한 회로 어레인지먼트 그리고 보조 전압을 생성하기 위한 방법
DE102007058982A1 (de) * 2007-12-07 2009-06-10 Tridonicatco Gmbh & Co. Kg Betriebsgerätsschnittstelle zur Spannungsversorgung
WO2012143906A2 (fr) 2011-04-22 2012-10-26 Koninklijke Philips Electronics N.V. Circuit d'alimentation électrique pour convertisseur pfc
WO2012143906A3 (fr) * 2011-04-22 2012-12-13 Koninklijke Philips Electronics N.V. Circuit d'alimentation électrique pour convertisseur pfc
US9379626B2 (en) 2011-04-22 2016-06-28 Koninklijke Philips Electronics N.V. Power supply circuit for a PFC converter
EP2854484A1 (fr) * 2013-09-27 2015-04-01 Toshiba Lighting & Technology Corporation Circuit d'alimentation électrique et luminaire
JP2015070698A (ja) * 2013-09-27 2015-04-13 東芝ライテック株式会社 電源回路及び照明装置

Also Published As

Publication number Publication date
EP0439240B1 (fr) 1995-06-21
EP0439240A3 (en) 1992-08-19
ATE124202T1 (de) 1995-07-15
DE59105746D1 (de) 1995-07-27
DE4018865A1 (de) 1991-12-19

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