EP0144556B1 - Blindleistungskompensator zur Kompensation einer Blindstromkomponente in einem Wechselspannungsnetz - Google Patents

Blindleistungskompensator zur Kompensation einer Blindstromkomponente in einem Wechselspannungsnetz Download PDF

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Publication number
EP0144556B1
EP0144556B1 EP84110650A EP84110650A EP0144556B1 EP 0144556 B1 EP0144556 B1 EP 0144556B1 EP 84110650 A EP84110650 A EP 84110650A EP 84110650 A EP84110650 A EP 84110650A EP 0144556 B1 EP0144556 B1 EP 0144556B1
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EP
European Patent Office
Prior art keywords
current
voltage
reactive
alternating
phase
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired
Application number
EP84110650A
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German (de)
English (en)
French (fr)
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EP0144556A1 (de
Inventor
Herbert Dr. Stemmler
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BBC Brown Boveri AG Switzerland
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BBC Brown Boveri AG Switzerland
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Publication date
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Priority to AT84110650T priority Critical patent/ATE35489T1/de
Publication of EP0144556A1 publication Critical patent/EP0144556A1/de
Application granted granted Critical
Publication of EP0144556B1 publication Critical patent/EP0144556B1/de
Expired legal-status Critical Current

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for AC mains or AC distribution networks
    • H02J3/18—Arrangements for adjusting, eliminating or compensating reactive power in networks
    • H02J3/1821—Arrangements for adjusting, eliminating or compensating reactive power in networks using shunt compensators
    • H02J3/1835—Arrangements for adjusting, eliminating or compensating reactive power in networks using shunt compensators with stepless control
    • H02J3/1842—Arrangements for adjusting, eliminating or compensating reactive power in networks using shunt compensators with stepless control wherein at least one reactive element is actively controlled by a bridge converter, e.g. active filters
    • H02J3/185—Arrangements for adjusting, eliminating or compensating reactive power in networks using shunt compensators with stepless control wherein at least one reactive element is actively controlled by a bridge converter, e.g. active filters wherein such reactive element is purely inductive, e.g. superconductive magnetic energy storage systems [SMES]
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/20—Active power filtering [APF]

Definitions

  • the invention relates to a reactive power compensator for compensating a reactive current component in an AC network according to the preamble of patent claim 1.
  • Combinations of switched capacitor batteries (TSC: thyristor switched capacitor) and controllable inductors (TCR: thyristor controlled reactance) are usually used as reactive power compensators these days.
  • the capacity of the capacitor bank is dimensioned according to the maximum inductive reactive power that occurs at the consumer. Since the capacitor bank can only be switched on and off in stages, the reactive power range between the stages is opened up by the controllable inductance (DE-OS-1 932 272). With this type of reactive power compensation, the effort for the capacitor bank to be installed increases with increasing reactive power of the consumer, so that with high reactive power, considerable costs for the compensator must be expected.
  • the invention relates to a prior art of reactive current compensators, as is known from IEEE Transactions, Volume IECI-23, No. 2, May 1976, pp. 162-166.
  • a pulse-width-modulated compensation current is generated by a regulated, thyristor-equipped, force-commutated inverter as a reactive current source with an input-side filter capacitor and an output-side DC choke.
  • the pulse frequency of the inverter is in the range of 1 kHz - 2.5 kHz.
  • the compensation current is not only dependent on the fundamental oscillation of the reactive current component due to a phase shift in the consumer circuit, but also on harmonic reactive currents.
  • Load current and mains voltage are multiplied to form the instantaneous value of the reactive power as a control signal for the thyristors of the inverter.
  • the product signal is then integrated during a half oscillation of the mains frequency and, after buffering in a sample and hold circuit during the half oscillation following the integration, multiplied by the mains voltage.
  • the load current is subtracted from this product.
  • the response time of a half-oscillation of the mains frequency is for fast load changes, such as z. B. occur in melting furnaces, not always sufficient.
  • the invention solves the problem of designing a reactive power compensator for compensating a reactive current component in an AC network in such a way that it ensures adequate compensation and at the same time a low harmonic component in the reactive current even with faster load changes.
  • An advantage of the invention is the shorter response time and the resulting larger area of application of the reactive power compensator. No integration over a certain period of time is required to form the control voltage.
  • the reactive current compensator according to the invention is in the compensation of reactive currents in three-phase three-phase networks, and therefore a three-phase converter bridge is used within the compensator, the following description in connection with an exemplary embodiment is limited to the simpler case of a single-phase AC network for the sake of clarity.
  • the person skilled in the art can easily carry out the implementation of the invention in the case of the three-phase network.
  • a consumer 5 is connected to an AC voltage network 18 with a sinusoidal mains voltage U N , through which a likewise sinusoidal consumer current I flows.
  • the consumer current I is not in phase with the mains voltage U N as required.
  • a current measuring device 6 and a voltage measuring device 7 are provided in the feed lines to the consumer 5 and parallel to the consumer 5. Both measuring devices are known measuring transducers, as are usually used for monitoring supply networks and are familiar to any person skilled in the art.
  • a converter bridge circuit with positively commutated converter valves 1, ..., 4, an AC voltage input 19 and a direct current output 20.
  • the positively commutated converter valves 1, ..., 4 are arranged in the individual bridge branches so that the DC output 20 results in a specified current direction for the current flowing there.
  • the type of converter bridge circuit is therefore also referred to as an I-converter.
  • the AC voltage input 19 is connected to the AC voltage network 18, while the DC output 20 is terminated by a smoothing choke 10. Parallel to the AC voltage input 19 there is also a capacitor 9 for protecting the converter valves 1,..., 4 during the forced commutation.
  • the positively commutated converter valves, 1, ..., 4 are converter valves that can be switched on or off either as independent components or by means of suitable additional circuitry (commutation circuits) regardless of the input voltage at the bridge.
  • the use of switch-off thyristors (GTO: gate turn off) is particularly advantageous here because these thyristors enable a simplified construction of the reactive power compensator due to the unnecessary additional wiring.
  • the positively commutated converter valves 1,..., 4 are connected via their control inputs to a control unit 11, which emits suitable pulses for switching the valves on and off according to a predetermined schedule.
  • This schedule is determined by a sequence of logic pulses, which arrive at the pulse inputs A and B of the control unit 11 from a pulse length modulator 12 and a polarity detector 22.
  • the polarity detector 22 determines the polarity of a sinusoidal control voltage U s at its input and outputs a signal corresponding to logic "1" at U s > 0 and a signal corresponding to logic "0" at U s ⁇ 0.
  • the control voltage U s is also the modulation voltage for the pulse length modulator 12, the pulse frequency f of which is predetermined by a pulse frequency generator 17.
  • the pulse length modulator 12 one of the circuits known from the technology of pulse length modulation can be used, in which e.g. B. a sawtooth signal generated in the pulse frequency generator 17 of the pulse frequency f is added to the modulation voltage and the sum signal is given to a limit value detector, at whose output the length-modulated pulses appear at a suitably set limit value.
  • a sawtooth signal generated in the pulse frequency generator 17 of the pulse frequency f is added to the modulation voltage and the sum signal is given to a limit value detector, at whose output the length-modulated pulses appear at a suitably set limit value.
  • the control voltage U s is the product of a multiplication process in which, in a first multiplier 13, an amplified reference voltage a.
  • U R is multiplied by a multiplication factor H which, depending on the phase position of the consumer current I, takes positive or negative values.
  • the multiplication factor M is the product of a further multiplication process in which an inverted reference voltage - b - U R is multiplied by the output signal of the current measuring device 6 in a second multiplier 16 and the product is reduced to its DC voltage component in a downstream low-pass filter 14.
  • the amplified reference voltage a. U R and the inverted reference voltage -b ⁇ U R are derived via an amplifier 21 or an inverting amplifier 15 from a common reference voltage U R , which is generated from the output signal of the voltage measuring device 7 by a 90 ° phase shift in a phase shifter 8.
  • the amplifiers 15 and 21 allow separate setting of the reference voltages a ⁇ U R and -b. U R to values for different processing the signals are suitable. However, the amplifier 21 can also be omitted.
  • the mode of operation of the reactive power compensator is clear from the shape and the time sequence of the various signals and signal voltages that occur in the circuit according to FIG. 1. To explain this, it is assumed that the consumer 5 takes inductive reactive power from the AC network 18, ie the consumer current I lags the mains voltage U N by a phase angle 0 ° ⁇ ⁇ 90 °. The corresponding current and voltage pointers are shown in the vector diagram of FIG. 2. The pointer of the consumer current 1 is rotated clockwise by the phase angle ⁇ with respect to the pointer of the rush voltage U N. The consumer current I can be broken down vectorially into an active current component I w and a reactive current component I B , which is to be compensated for by the reactive power compensator.
  • the reactive current component I B is parallel to the vector of the sinusoidal reference voltage U R, which is delayed by 90 ° by the phase shifter 8 against the mains voltage U N.
  • the vector of the reactive current component I B is parallel to the inverted reference voltage -b. UR.
  • FIGS. 3a and 3b The time course of the voltages and currents is shown in FIGS. 3a and 3b.
  • 3a shows the rush voltage U N over time t, the consumer current I lagging by ⁇ and the reference voltage U R lagging by 90 °.
  • the consumer current I is plotted again in FIG. 3 b on the same scale, together with its reactive current component I B and the control voltage U S required for the pulse length modulator 12.
  • the control voltage U s is always shifted in phase with respect to the reactive current component I B by 180 °, and therefore in phase with a compensation current .DELTA.l to be generated from the power factor corrector and the reactive current component I B just compensated.
  • the reactive current component I B since both the reference voltage U R and the amplified reference voltage a ⁇ U R have an amplitude that is constant over time and lag behind the mains voltage U N in a phase-locked manner by 90 °, the reactive current component I B, however, generally has both its amplitude and its phase position between capacitive (+90 °) and inductive (-90 °) changes, a corresponding tracking of the control voltage U s is effected in that the amplified reference voltage aU R is multiplied by the multiplication factor M, which is variable in its amount and its sign.
  • M which is variable in its amount and its sign.
  • inductive reactive current component I B a negative sign of M generates the necessary phase shift of 180 ° of the control voltage U s compared to a.
  • U R and I B With a capacitive reactive current component, a positive sign of M leaves the phase unchanged, since the necessary 180 ° shift is already between I B and a. U R is present.
  • a multiplication factor M proportional to this DC signal input from (5) has exactly the desired properties: it is negative with an inductive reactive current component (- (p), positive with a capacitive reactive current component (+ ⁇ ), and it is proportional to the amplitude I ° B of the reactive current component I B
  • the proportionality constant can be set in a suitable manner by the transmission factor of the current measuring device 6 and the inverting amplifier 15.
  • the converter bridge circuit In accordance with the control voltage U s given by M and a ⁇ U R , the converter bridge circuit generates the compensation current ⁇ l in the form of sinusoidally length-modulated rectangular pulses, as shown in FIG. 3c.
  • the associated sequence of the control for the positively commutated converter valves 1,..., 4 is shown below in FIG. 3d, the hatched areas in each case denoting the period in which the corresponding converter valve is switched through.
  • the two converter valves 1 and 4 switched through simultaneously, so that from this point in time according to the determination from FIG. 1, a positive compensation current ⁇ l flows at the AC voltage input 19 and at the same time through the smoothing choke 10.
  • the converter valve 1 is switched off and the converter valve 2 is switched through, while the converter valve 4 remains conductive.
  • the compensation current ⁇ l is zero until the converter valve 1 is switched through again.
  • the switched-over converter valves 2 and 4 form a free-running branch for the smoothing inductor 10, which drives a direct current of unchanged size via this free-running branch due to the stored energy.
  • This interplay of ⁇ l pulses and free-running times is repeated with the pulse frequency f and changing duty cycles within the time interval t 3 - t 2 , in which the compensation current ⁇ l is positive.
  • FIG. 3a-d illustrate the control sequence for an inductive reactive current component I B.
  • I B In the case of a capacitive reactive current component, I B , U s and I are out of phase by 180 °.
  • the positive ⁇ l pulses then fall in the time interval t 2 -t j , so that the control times of the converter valves are also interchanged accordingly.
  • suitable logic pulses from the pulse length modulator 12 and the polarity detector 22 are required at the pulse inputs A and B of the control unit. These logic pulses are shown in the top two rows of FIG. 4.
  • the sequence of logic pulses emitted by the polarity detector 22 changes from logic "1" to logic "0” or vice versa each time the polarity of the control voltage U s changes at times t 1 t 2 and t 3 .
  • the sequence emitted by the pulse length modulator 12 consists of nothing but positive, sinusoidally length-modulated logic pulses. This can e.g. B. can be achieved by first supplying the control voltage U s in the pulse length modulator 12 to a full-wave rectifier and only then using it for the actual pulse length modulation.
  • FIG. 6 A suitable circuit structure of the control unit 11, which ensures the necessary logic operations, is shown in FIG. 6.
  • the logic pulses of the pulse inputs A and B reach an XOR gate (exclusive OR; exclusive OR) 26, the output of which leads on the one hand directly via a pulse converter 23 to the control input of the converter valve 2 and on the other hand via a first inverter 24 and an identical pulse converter 23 with the Control input of the converter valve 1 is connected.
  • Two further lines lead from the pulse input A via a second inverter 25 and a pulse converter 23 or directly via a pulse converter 23 to the converter valves 3 and 4.
  • the pulse converters 23 are constructed identically for all outputs and generate from the logic pulses. e.g. B. by differentiation, suitable control pulses for the positively commutated converter valves 1, ..., 4.
  • the control pulses are such that when switching from logic "0" to logic “1” the assigned converter valve is switched through, while when switching from logic "1" to logic “0” the converter valve is deleted.
  • the circuit design of the pulse converter 23 depends on the ignition and shutdown properties of the converter valves used and is known to the person skilled in the art.
  • the invention results in a reactive power compensator, which enables fast, steady and flexible regulation of the reactive current components occurring in an AC voltage network with little design effort.
  • the size of the smoothing choke 10 and the capacitor 9 can be chosen to be smaller the higher the pulse frequency f. It is therefore advantageous to set this pulse frequency substantially higher than the frequency of the mains voltage U N , but in particular greater than 10 kHz. In this way, e.g. B. in turn-off thyristors, taking advantage of the possible switching frequencies, the effort in the passive components kept low.
  • a further reduction in the harmonic content in the compensation current Al can thereby be achieved 7, that a plurality of converter bridge circuits 27, 28 are connected in parallel to the AC voltage network 18 and clocked in an offset manner, as shown in FIG.
  • the AC voltage network is indicated in this case as a three-phase network.
  • the converter valves of each converter bridge circuit 27, 28 are arranged in a three-phase full bridge, as is indicated in the dashed boxes in FIG. 7.
  • the individual converter bridge circuits 27 and 28 are also constructed identically with regard to the control according to FIG. 1, but it must be taken into account that instead of the single-phase mains voltage U N from FIG. 1, the three concatenated voltages of the three-phase network are now taken for themselves can be used for control.
  • Each of the converter bridge circuits 27 and 28 supplies an associated compensation current ⁇ l 1 or A1 2 to the AC network 18.
  • the superimposition of the two compensation currents ⁇ l 1 and A1 2 then results in the resulting compensation current ⁇ l.
  • a pulse frequency generator 17 and 17 ' is assigned to both converter bridge circuits 27, 28, respectively. Both pulse frequency generators 17 and 17 'preferably generate the same pulse frequency f. While in both converter bridge circuits 27 and 28 all other voltages used for control are in phase, there is a phase difference in the form of a displacement angle ⁇ (FIG. 8) between the pulse trains of the pulse frequency generators 17, 17 '. This is achieved by a synchronization line 29 which connects the two pulse frequency generators 17 and 17 'and synchronizes taking into account the offset angle ⁇ .
  • the pulse trains of the compensation currents ⁇ l 1 and ⁇ l 2 of the two converter bridge circuits 27 and 28 are then also offset according to FIG. 8 by the offset angle ⁇ , for example 36 °.

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Control Of Electrical Variables (AREA)
  • Supply And Distribution Of Alternating Current (AREA)
  • Optical Communication System (AREA)
EP84110650A 1983-10-12 1984-09-07 Blindleistungskompensator zur Kompensation einer Blindstromkomponente in einem Wechselspannungsnetz Expired EP0144556B1 (de)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT84110650T ATE35489T1 (de) 1983-10-12 1984-09-07 Blindleistungskompensator zur kompensation einer blindstromkomponente in einem wechselspannungsnetz.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
CH5548/83 1983-10-12
CH554883 1983-10-12

Publications (2)

Publication Number Publication Date
EP0144556A1 EP0144556A1 (de) 1985-06-19
EP0144556B1 true EP0144556B1 (de) 1988-06-29

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EP84110650A Expired EP0144556B1 (de) 1983-10-12 1984-09-07 Blindleistungskompensator zur Kompensation einer Blindstromkomponente in einem Wechselspannungsnetz

Country Status (8)

Country Link
US (1) US4647837A (enrdf_load_stackoverflow)
EP (1) EP0144556B1 (enrdf_load_stackoverflow)
JP (1) JPS6098830A (enrdf_load_stackoverflow)
AT (1) ATE35489T1 (enrdf_load_stackoverflow)
AU (1) AU575589B2 (enrdf_load_stackoverflow)
CA (1) CA1230643A (enrdf_load_stackoverflow)
DE (1) DE3472509D1 (enrdf_load_stackoverflow)
IN (1) IN161960B (enrdf_load_stackoverflow)

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JPH0655009B2 (ja) * 1987-11-16 1994-07-20 三菱電機株式会社 アクテイブフイルタの制御装置
JPH01310418A (ja) * 1988-06-08 1989-12-14 Aretsukusu Denshi Kogyo Kk 自動力率制御装置
JP2760646B2 (ja) * 1990-09-18 1998-06-04 株式会社東芝 電力変換装置の電流指令値演算装置
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DE69905453T2 (de) 1999-07-02 2003-10-23 Magnetek S.P.A., Terranuova Bracciolini Stromversorgungseinrichtung für einen elektrischen Motor und dazugehörige Steuerungsmethode
BR0013946A (pt) * 1999-09-13 2002-05-28 Aloys Wobben Processo para a regulagem de potência reativa em uma rede elétrica, e, aparelho para a geração de energia elétrica em uma rede elétrica
RU2183897C1 (ru) * 2000-11-02 2002-06-20 Агунов Александр Викторович Способ генерирования компенсационного тока в питающую сеть
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FI113306B (fi) * 2002-08-27 2004-03-31 Vacon Oyj Loistotehon kompensointi taajuusmuuttajalla
EP1604440B1 (en) * 2003-03-14 2016-06-15 ABB Technology AG Electronic circuit breaker
CN100505505C (zh) * 2005-12-14 2009-06-24 东芝三菱电机产业系统株式会社 电力变换设备
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CN100541225C (zh) * 2006-12-27 2009-09-16 梁一桥 谐波电流和感性无功功率发生装置
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IT1402466B1 (it) * 2010-11-05 2013-09-13 Raw Power S R L Dispositivo per eliminare una componente continua di corrente circolante in una rete elettrica monofase
FR2979493B1 (fr) * 2011-08-25 2013-09-13 Converteam Technology Ltd Compensateur d'energie reactive comprenant n onduleurs en parallele, n bancs de condensateur(s) et des moyens de connexion des bancs au travers de composants electriques passifs
UA101888C2 (ru) 2011-10-19 2013-05-13 Юрий Николаевич Самойленко Способ компенсации реактивной мощности в сети питания переменного тока
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Also Published As

Publication number Publication date
AU3352084A (en) 1985-04-18
AU575589B2 (en) 1988-08-04
DE3472509D1 (en) 1988-08-04
CA1230643A (en) 1987-12-22
US4647837A (en) 1987-03-03
EP0144556A1 (de) 1985-06-19
JPS6098830A (ja) 1985-06-01
IN161960B (enrdf_load_stackoverflow) 1988-03-05
ATE35489T1 (de) 1988-07-15

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