EP0121917A1 - Dispositif électronique pour faire fonctionner des lampes à fluorescence - Google Patents

Dispositif électronique pour faire fonctionner des lampes à fluorescence Download PDF

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Publication number
EP0121917A1
EP0121917A1 EP84103849A EP84103849A EP0121917A1 EP 0121917 A1 EP0121917 A1 EP 0121917A1 EP 84103849 A EP84103849 A EP 84103849A EP 84103849 A EP84103849 A EP 84103849A EP 0121917 A1 EP0121917 A1 EP 0121917A1
Authority
EP
European Patent Office
Prior art keywords
current
working
electronic
circuit
voltage
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Withdrawn
Application number
EP84103849A
Other languages
German (de)
English (en)
Inventor
Fred Dr. Ing. Hasemann
Ferdinand Dipl.-Ing. Mertens
Norbert Dipl.-Ing. Wittig
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Trilux GmbH and Co KG
Original Assignee
Trilux Lenze GmbH and Co KG
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Trilux Lenze GmbH and Co KG filed Critical Trilux Lenze GmbH and Co KG
Publication of EP0121917A1 publication Critical patent/EP0121917A1/fr
Withdrawn legal-status Critical Current

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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters
    • H05B41/282—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices
    • H05B41/2825—Circuit arrangements in which the lamp is fed by power derived from dc by means of a converter, e.g. by high-voltage dc using static converters with semiconductor devices by means of a bridge converter in the final stage

Definitions

  • the invention relates to an electronic ballast for fluorescent lamps, with a push-pull switch arrangement connected to a DC voltage, consisting of two electronic switches connected in series, a working resonant circuit connected to the connection point of the electronic switches, at least one fluorescent lamp whose supply voltage is derived from the voltage drop of the inductance or the capacitance. and with a control circuit that switches the electronic switches depending on the current in the working circuit.
  • Electronic ballasts are known for the operation of fluorescent lamps (DE-OS 29 41 822), which a working resonant circuit from the series connection of a Have inductance and a capacitance.
  • the fluorescent lamp is connected in parallel to the capacitance of the series resonant circuit at which high voltages occur.
  • the working oscillating circuit is triggered by a push-pull switch arrangement comprising two transistors connected in series, which are controlled in opposite directions to one another depending on the current in the working oscillating circuit, so that one end of the working oscillating circuit is alternately connected to positive and negative potential.
  • the push-pull switch arrangement is controlled in such a way that the transistors are respectively opened in the correct half-wave of the oscillating current in order to support and excite the oscillation, but this activation takes place with a delay in which the oscillating current has already reached a considerable size.
  • the transistor that is controlled in the blocking state must switch off a current of considerable size.
  • switching losses are particularly important for heating a transistor or another electronic switch.
  • the transistors require extensive cooling plates because of the high switching losses. The life of these transistors is limited due to the strong heating.
  • the invention has for its object an electronic ballast of the aforementioned. To create a way in which the power loss is reduced.
  • control circuit is designed such that the switching of the electronic switches takes place in the vicinity of the zero crossings of the current of the working resonant circuit.
  • both electronic switches of the push-pull switch arrangement are practically de-energized at the time of the switchover, so that the switchover takes place with almost no power loss.
  • the electronic switches have almost no switch-on and switch-off losses and remain cold.
  • the current that flows through the respective conductive electronic switch does not cause much heat loss due to the low forward resistance.
  • transistors with relatively low power and without cooling devices can be used as electronic switches. This simplifies the electronic and mechanical components of the device. Due to the low load on the electronic switches, their lifespan is increased.
  • Switching the push-pull switch arrangement in the vicinity of the zero crossing of the oscillating current means at the same time that at the time of switching both at the Inductance and the capacitance of the working oscillating circuit each have the maximum voltage present.
  • the switchover therefore takes place at the point in time at which the voltage of the fluorescent lamp also assumes its maximum value. It has been found that the fluorescent lamp is ignited even at lower supply voltages if the switchover time is selected in the manner according to the invention. Fluorescent lamps can be ignited with a DC supply voltage of approx. 30 volts if the switchover takes place at the maximum voltage. With previous ballasts, a higher operating voltage is required for ignition. As a result of the low ignition voltage, the lamp can also be switched on in the more dimmed state.
  • ballast according to the invention can be used unchanged in connection with different types of fluorescent lamps.
  • Argon lamps have a different ignition and operating behavior than krypton lamps.
  • the ignition voltage is approximately 350 volts and the operating current consumption is approximately 350 mA.
  • the ignition voltage for krypton lamps is approximately 850 volts and the operating current consumption is approximately 450 mA.
  • the working circuit is damped more because of the lower resistance.
  • a ballast which is designed to supply a krypton lamp which has a power of 50 W if it is designed in the manner according to the invention, can also supply an argon lamp in unchanged form, but then a power of about 60 W. Through this additional The ballast is not overloaded in the case of an argon lamp.
  • the push-pull switch arrangement is preferably switched over in a phase angle range of ⁇ 10 °, based on the zero crossing of the current of the working resonant circuit, and in particular in a phase angle range of -5 °.
  • an inductive transformer is connected to the work resonant circuit, the primary winding connected in series, whose two oppositely excited Sekundärwicklun - gen each one of the electronic switches control so that the blocking of the previously conducting switch before the zero crossing of the current and the opening of the previously blocked switch takes place after the zero crossing of the current.
  • a switching interval is achieved, so that it is excluded that both electronic switches are in the conductive state at the same time.
  • the fact that the one transistor is blocked and the other transistor is turned on on both sides of the zero current crossing means that the current values during the switching operations are approximately the same and both are very small.
  • the electronic switches are field effect transistors of the same type and that each of the secondary windings is connected at one end to the source connection and at the other end to the control connection of the associated field effect transistor and that the secondary windings are wound or switched in phase opposition to one another. Since field effect transistors have an extremely high input resistance at the control connection, the secondary windings are not loaded by the field effect transistors, so that only a negligibly small current flows in them. The control voltage at each field effect transistor is thus in phase with the oscillating current, ie with the current in the primary winding of the transformer.
  • phase shifter networks which are connected between the secondary coils of the transformers and the control connections of the electronic switches.
  • An electronic ballast in which the switches are switched near the zero crossings has a very low power loss, while almost all of the input power is transferred to the lamp.
  • the lamp resistance must meet certain conditions so that the working circuit is capable of oscillating at all.
  • the capacitance or the inductance of the working oscillating circuit is the primary winding a transformer is connected in parallel, the secondary winding of which is connected to the electrodes of the fluorescent lamp.
  • L is the inductance of the working resonant circuit, C the capacitance, R the lamp resistance and f the resonant frequency of the resonant circuit
  • the condition must be met without using a transformer be fulfilled so that the vibration is maintained. This means that must be so that the pressure under the root does not become negative or zero.
  • the resonant circuit elements L and C can be determined with a predetermined resistance R and a predetermined mains alternating voltage as well as a predetermined lamp power. With a mains voltage of 220 volts and a nominal lamp output of 50 watts, this means that taking into account the mains voltage tolerances of - 10%, the lamp resistance R must be greater than 474 ohms.
  • the fluorescent lamps used in practice generally have a lower resistance during nominal operation.
  • the lamp resistance is transformed by the transformer to a value R ', which must be greater than 474 ohms.
  • the value R ' should not be greater than approx. 1000 ohms in order not to make the ignition of the lamp too difficult by the step-down voltage.
  • R ' is preferably in the range from 600 to 700 ohms and in particular in the vicinity of 700 ohms.
  • the supply circuit shown in Fig. 1 has a low-pass filter 10, the input terminals of which are connected to an AC voltage of e.g. 220 V and 50 Hz.
  • the low-pass filter 10 consists, in a known manner, of at least one choke 11 and one transverse capacitor 12.
  • a full-wave rectifier 13 is connected to the output of the low-pass filter, the output terminals of which are connected to a smoothing capacitor 14.
  • a DC voltage U arises at the smoothing capacitor 14 and is supplied to the circuit according to FIG. 2, FIG. 3 or FIG. 5 as an input voltage.
  • the voltage U is applied to the push-pull switch arrangement 15, 16, which consists of two series-connected transistors 15 and 16 of the same type - in the present case npn transistors.
  • the push-pull switch arrangement 15, 16 which consists of two series-connected transistors 15 and 16 of the same type - in the present case npn transistors.
  • the series circuit of the primary coil 18 of the Ubertragers 19 the inductance 20 and the K is apazi- ty 21 connected.
  • the inductance 20 forms, together with the capacitance 21, the working resonant circuit.
  • the fluorescent lamp 22 is connected in parallel with the capacitor 21. One end of the capacitor 21 and the fluorescent lamp 22 is connected via a capacitor 23 to the positive pole of the supply voltage U g .
  • Transistors 15 and 16 are switched in push-pull mode, ie if transistor 15 is conductive, transistor 16 is blocked and if transistor 16 is conductive transistor 15 is blocked. However, overlap the blocking phases of both transistors change slightly, as will be explained below.
  • Transistors 15 and 16 are controlled via two secondary windings 24, 25 of transformer 19. Secondary winding 24, which is inductively coupled to primary winding 18 via a ferrite core, is connected to a control circuit 26, the output of which is connected to the base of transistor 15 is.
  • the second secondary coil 25, which is also inductively coupled to the primary coil 18 of the transmitter 19 via a ferrite core, is connected to a control circuit 27, the output of which is connected to the base of the transistor 16.
  • the two secondary coils 24 and 25 are excited in opposite directions to one another by the primary coil 18, which is indicated by the points shown. For example, the secondary coils 24 and 25 are wound in opposite directions to one another.
  • the control circuits 26 and 27 control the transistors 15 and 16 so that the transistor 15 connecting the connection point 17 to the positive pole of the supply voltage U becomes conductive when the current in the primary coil 18 is at the beginning of the positive half-wave and is blocked when this current is at the end of the positive half wave.
  • the transistor 16, which connects the connection point 17 to the negative pole of the supply voltage U g becomes conductive when the current in the primary coil 18 is at the beginning of the negative half-wave and blocked when this current is at the end of this negative half-wave.
  • I the oscillating current which flows through the working oscillating circuit 21 and thus also through the primary winding 18 of the transformer 19. This oscillating current is almost sinusoidal.
  • the previously conductive transistor 15 Shortly before the zero crossing 28 from the positive to the negative half-wave, the previously conductive transistor 15 is blocked at time t 1 . A short time after the zero crossing 28 of the oscillating current I, the previously blocked transistor 16 becomes conductive at the time t 2 . Between the two times t 1 and t 2 , both transistors 15 and 16 are blocked.
  • the transistor 16 is blocked again at the time t 3 shortly before the positive zero crossing 29 and shortly after the positive zero crossing 29 the transistor 15 becomes conductive at the time t 4 .
  • FIG. 4 also shows the time profiles of the voltage U L at the inductor 20 and the voltage U c at the capacitor 21. These voltages are 90 ° out of phase with the current I and 180 ° out of phase with respect to each other. It can be seen that at the times of the zero crossings 28, 29 of the oscillating current I, the voltages U L and U c each assume their maximum value. Since the voltage U c is also present on the fluorescent lamp 22, the voltage on the fluorescent lamp has approximately the maximum value at the switching times t 1 to t 4 .
  • FIG. 3 differs from that of FIG. 2 only in that field-effect transistors 35, 36 are used as electronic switches, and in that the control switching devices 26 and 27 are omitted.
  • the field effect transistor 35 is connected with its source connection to the connection point 17 and with its drain connection to the positive pole of the supply voltage U g.
  • the field effect transistor 36 is connected with its source connection to the negative pole of the supply voltage U g and with its drain connection with the connection point 17.
  • One end of the secondary winding 24 is connected to the connection point 17 and the other end to the control connection of the field effect transistor 35.
  • One end of the secondary winding 25 is connected to the control connection of the field effect transistor 36 and the other end to the negative pole of the supply voltage U g .
  • FIG. 5 corresponds to that of FIG. 3, so that only the differences are explained below.
  • the fluorescent lamp 22 is not connected in parallel directly to the capacitance 21 of the working resonant circuit 20, 21, but rather via a transformer 39.
  • the primary winding of the transformer 39 is connected with its two ends to the electrodes of the capacitor 21, that is to say connected to the latter in parallel.
  • the electrodes of the fluorescent lamp 22, the heating circuits of which are not shown in the present case, are connected to the ends of the secondary winding 38 of the transformer 39.
  • the resistance of the fluorescent lamp 22 is according to the formula transformed to the primary side, where R is the lamp resistance, w1 the number of turns of the primary winding 37 and w 2 the number of turns of the secondary winding 38. The number of turns is such that the condition is satisfied.
  • L is the
  • the secondary winding 38 has an additional tap 40 which is used when connecting a krypton lamp.
  • the entire secondary winding 38 is used in the argon lamp.
  • the transformer 39 in FIG. 5 it is possible to evaluate the direct voltage generated from the mains voltage in full, i.e. without a voltage-reducing choke, and the entire available voltage by the push-pull switch arrangement 35, 36 which is switched in the zero current crossings becomes practically lossless and without phase gates in a DC voltage and at the same time achieve that the fluorescent lamp consumes exactly the intended nominal power.
  • the fluorescent lamp is therefore not overloaded and the energy losses of the ballast are reduced to the absolutely necessary level.

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  • Circuit Arrangements For Discharge Lamps (AREA)
EP84103849A 1983-04-08 1984-04-06 Dispositif électronique pour faire fonctionner des lampes à fluorescence Withdrawn EP0121917A1 (fr)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3312574 1983-04-08
DE19833312574 DE3312574A1 (de) 1983-04-08 1983-04-08 Elektronisches vorschaltgeraet fuer leuchtstofflampen

Publications (1)

Publication Number Publication Date
EP0121917A1 true EP0121917A1 (fr) 1984-10-17

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Family Applications (1)

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EP84103849A Withdrawn EP0121917A1 (fr) 1983-04-08 1984-04-06 Dispositif électronique pour faire fonctionner des lampes à fluorescence

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EP (1) EP0121917A1 (fr)
DE (1) DE3312574A1 (fr)

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
EP0361748A1 (fr) * 1988-09-26 1990-04-04 General Electric Company Circuit de contrôle de puissance pour lampes de décharge et procédé pour leur fonctionnement
EP0361706A1 (fr) * 1988-09-08 1990-04-04 Hayashibara, Ken Dispositif d'éclairage
EP0391679A1 (fr) * 1989-04-04 1990-10-10 Aktiebolaget Electrolux Circuit oscillateur
US4996462A (en) * 1988-07-27 1991-02-26 Siemens Aktiengesellschaft Electronic ballast for fluoroscent lamps
EP0659037A2 (fr) * 1993-12-15 1995-06-21 General Electric Company Ballast avec indicateur de son fonctionnement pour lampe à décharge
US5434880A (en) * 1992-07-11 1995-07-18 Lumonics Ltd. Laser system

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB9013819D0 (en) * 1990-06-21 1990-08-15 Nada Electronics Ltd Resonant inverter
DE19608655A1 (de) * 1996-03-06 1997-09-11 Bosch Gmbh Robert Leistungssteuerung einer mit Wechselstrom betriebenen Hochdruckgasentladungslampe, insbesondere für Kraftfahrzeuge
DE19608657A1 (de) * 1996-03-06 1997-09-11 Bosch Gmbh Robert Schaltung zum Betrieb einer Hochdruckgasentladungslampe

Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2061037A (en) * 1979-10-16 1981-05-07 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for driving low pressure discharge
GB2080652A (en) * 1980-07-21 1982-02-03 Philips Nv Oscillator for supplying an electrodeless discharge lamp
WO1983000271A1 (fr) * 1981-07-06 1983-01-20 Zelina, William, B. Ballast inverseur pour lampe fluorescente alimentee par le reseau

Patent Citations (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2061037A (en) * 1979-10-16 1981-05-07 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for driving low pressure discharge
GB2080652A (en) * 1980-07-21 1982-02-03 Philips Nv Oscillator for supplying an electrodeless discharge lamp
WO1983000271A1 (fr) * 1981-07-06 1983-01-20 Zelina, William, B. Ballast inverseur pour lampe fluorescente alimentee par le reseau

Cited By (9)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US4996462A (en) * 1988-07-27 1991-02-26 Siemens Aktiengesellschaft Electronic ballast for fluoroscent lamps
EP0361706A1 (fr) * 1988-09-08 1990-04-04 Hayashibara, Ken Dispositif d'éclairage
EP0361748A1 (fr) * 1988-09-26 1990-04-04 General Electric Company Circuit de contrôle de puissance pour lampes de décharge et procédé pour leur fonctionnement
EP0391679A1 (fr) * 1989-04-04 1990-10-10 Aktiebolaget Electrolux Circuit oscillateur
US5043680A (en) * 1989-04-04 1991-08-27 Aktiebolaget Electrolux Resonant converter oscillator usable for powering a magnetron
AU626399B2 (en) * 1989-04-04 1992-07-30 Aktiebolaget Electrolux Oscillator circuit
US5434880A (en) * 1992-07-11 1995-07-18 Lumonics Ltd. Laser system
EP0659037A2 (fr) * 1993-12-15 1995-06-21 General Electric Company Ballast avec indicateur de son fonctionnement pour lampe à décharge
EP0659037A3 (fr) * 1993-12-15 1997-03-26 Gen Electric Ballast avec indicateur de son fonctionnement pour lampe à décharge.

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Publication number Publication date
DE3312574A1 (de) 1984-10-18

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Inventor name: WITTIG, NORBERT, DIPL.-ING.

Inventor name: HASEMANN, FRED, DR. ING.

Inventor name: MERTENS, FERDINAND, DIPL.-ING.