CN217469895U - Double-frequency Doherty power amplifier based on left-hand and right-hand composite line structure - Google Patents
Double-frequency Doherty power amplifier based on left-hand and right-hand composite line structure Download PDFInfo
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Abstract
The utility model discloses a dual-frenquency Doherty power amplifier based on right-hand man composite line structure, divide ware, carrier power amplification module, peak power amplification module and close way impedance match network including the dual-frenquency merit, utilize right-hand man composite line theory to have found the dual-frenquency merit and divided ware and dual-frenquency impedance inverter. The double-frequency power divider realizes power distribution of any two frequency bands, and can expand the bandwidth of two working frequency bands while only using a first-level Wilkinson power divider structure; the impedance inverter utilizing the left-right hand transmission line theory can randomly select two working frequency bands without changing the overall structure, and meanwhile, the bandwidths of the two working frequency bands can be expanded to a certain extent.
Description
Technical Field
The utility model belongs to the microwave radio frequency communication field specifically is a radio frequency power amplifier, especially relates to dual-frenquency Doherty power amplifier based on left and right hands composite line structure.
Background
The radio frequency power amplifier is a key component of a radio frequency communication front end, 5G communication has the characteristics of complex modulation, large bandwidth and high signal peak-to-average ratio, and higher requirements are put forward on the bandwidth and the efficiency of the power amplifier. The Doherty power amplifier adopting the load modulation technology has the excellent characteristics of high back-off efficiency and good linearity. The purpose of expanding the bandwidth is achieved by researching a concurrent double-frequency impedance inverter to replace an 1/4 wavelength line which limits the working bandwidth in the Doherty power amplifier. Due to the advantages of small occupied space, low power consumption and the like, the multiband radio frequency power amplifier receives wide attention in recent years. The earliest multi-frequency amplifiers were implemented primarily by installing multiple amplifiers in different frequency bands and using single pole multi-throw switches or using a specially designed broadband load network to cover the entire frequency band. With the miniaturization and cost reduction of devices, the high cost, the overlarge size and the low working efficiency of the devices are more and more difficult to meet the requirements of related industries; the latter is rather difficult to achieve high efficiency over a wide band.
In view of the difficulties in the prior art, it is necessary to research to implement a simple dual-frequency structure to replace the conventional 1/4 wavelength line, and on the basis of the structure, a dual-frequency Doherty power amplifier with guaranteed back-off efficiency is proposed and can operate in the 5G band.
SUMMERY OF THE UTILITY MODEL
In order to overcome the technical defect who exists among the prior art, the utility model provides a dual-frenquency Doherty power amplifier based on right-hand and left-hand composite line structure adopts the dual-frenquency merit of right-hand and left-hand composite transmission line structure to divide the ware equally using, the dual-frenquency input/output matching network that T type microstrip structure and series connection microstrip line constitute, the way output matching network extension bandwidth that multistage step microstrip line is established ties, the dual-frenquency impedance inverter realization that right-hand and left-hand transmission line structure constitutes about the complex can guarantee to roll back efficiency and sufficient saturation efficiency in 5G working frequency channel.
In order to solve the technical problem existing in the prior art, the technical scheme of the utility model as follows:
the double-frequency Doherty power amplifier based on the left-hand and right-hand composite line structures comprises a double-frequency power divider, a carrier power amplification module, a peak power amplification module, a double-frequency impedance inverter and a combined output matching network.
The input end of the double-frequency power divider is connected with the radio-frequency signal output end, and the output end of the double-frequency power divider is respectively connected with the input ends of the carrier power amplification module and the peak power amplification module.
The carrier power amplification module comprises a carrier input matching/biasing network, a carrier power amplifier, a carrier output matching/biasing network and a double-frequency impedance inverter.
The peak power amplification module comprises a peak power amplifier phase compensation line, a peak input matching/biasing network, a peak power amplifier and a peak output matching/biasing network.
The combined output matching network comprises a three-step impedance matching microstrip line.
As a preferable technical scheme, the dual-frequency power divider is composed of microstrips TL 1-TL 15, arc microstrip lines Curve 1-Curve 4, capacitors C1-C6 and resistors R1, wherein one end of the microstrip line TL1 is used as a port 1, and the other end of the microstrip line TL1 is connected with one ends of TL2 and TL 3. Microstrip lines TL14, TL15 have one end as port 2 and port 3, and the other end connected to one end of TL12, TL13, respectively. The microstrip line TL2, the arc microstrip line Curve1, the microstrip line TL5, the capacitor C1, the capacitor C2, the capacitor C3, the microstrip line TL10, the arc microstrip line Curve3 and the microstrip line TL12 are sequentially connected in series to form one path of the power divider, and the microstrip line TL3, the arc microstrip line Curve2, the microstrip line TL14, the capacitor C4, the capacitor C5, the capacitor C6, the microstrip line TL11, the arc microstrip line Curve4 and the microstrip line TL13 are sequentially connected in series to form the other path of the power divider. Short-circuit stub microstrip lines TL6 and TL7 are loaded between capacitors C1 and C2 and between C2 and C3 respectively to form a left-right hand composite line structure, and short-circuit stub microstrip lines TL8 and TL9 are loaded between capacitors C4 and C5 and between C5 and C6 respectively to form a left-right hand composite line structure. Series resistors R1 are connected between microstrip lines TL12 and TL13 in series to balance current, so that a double-frequency Wilkinson power divider based on a left-hand and right-hand composite line is formed, and the working frequency band is 3.3-3.6GHz and 4.8-5.0 GHz; the percentage of the components is 1: 1.
as an optimal technical scheme, the input and output matching network adopts a structure of connecting a T-shaped structure and a step microstrip line in series to perform dual-frequency impedance matching, and the bandwidths of two working frequency bands are expanded to a certain extent.
As a preferred technical solution, the carrier input matching/biasing network is the same as the peak input matching/biasing network, and the carrier output is matched to 2R opt Matching the peak output to R opt 。
Wherein R is opt The optimal load resistance values of the carrier amplifier and the peak amplifier under the bias condition of B class are obtained.
As a preferable technical scheme, the impedance inverter adopts a left-right hand composite line structure to replace a traditional 50 omega, 1/4 wavelength line. The left-hand and right-hand compound line structure is formed by sequentially connecting a microstrip line TL16, a capacitor C7, a capacitor C8, a capacitor C9 and a microstrip line TL19 in series, the connecting part of the capacitor C7 and the capacitor C8 and the connecting part of the capacitor C8 and the capacitor C9 are respectively connected with a short-circuit stub microstrip line TL17 and a short-circuit stub microstrip TL18 in parallel, and the propagation constant and the characteristic impedance of the left-hand and right-hand compound line are respectively as follows:
wherein, L' R 、C' R 、L' L 、C' L Respectively distributed inductance and capacitance in unit length; and omega is an operating frequency point. If a composite right and left handed transmission line is used instead of the 1/4 wavelength impedance transformation line, it is necessary to satisfy:
β CRLH (ω＝ω 1 )＝β 1 (4)
wherein Z is t Characteristic impedance of a conventional 1/4 wavelength impedance inverter; omega 1 Is the first working frequency point; beta is a 1 The phase shift corresponding to the first working frequency point.
The formula and the characteristic impedance which meet the conditions form three independent equations which contain four variables, so that the equation has a degree of freedom, the equation is possible to meet the working condition of a second working frequency point, and the parameters of the left-hand and right-hand composite transmission line are as follows:
wherein, ω is 1 、ω 2 Two frequency points for work, beta 1 、β 2 Which are respectively the phase shifts corresponding to the two working frequency points. The above parameters are ideal and uniform composite right-left hand transmission lines, but in practical application, the LC ladder network is usually used to construct the composite right-left hand transmission lines, so the parameters of the actual right-left hand transmission lines are as follows:
wherein N is the number of LC trapezoidal structure units, phi 1 、φ 2 Of N structural unitsThe total phase shift.
As a preferred technical solution, the combining output matching network is formed by multiple sections of series-connected step microstrip lines, and the output bandwidth of the combining output matching network is expanded to a certain extent.
Compared with the prior art, the utility model discloses following technological effect has:
1. the utility model discloses a function that the dual-frenquency of 3.3 ~ 3.6GHz, 4.8 ~ 5.0GHz is sent out is replaced to 1/4 wavelength line in the traditional Doherty power amplifier peak power amplifier module by the right-hand man composite transmission line, 1/4 wavelength line in the ware is divided to the right-hand man composite transmission line replacement tradition Wilkinson merit about the adoption, realizes dual-frenquency power partition, and the step microstrip line of multistage series connection can improve the bandwidth of two 5G working frequency ranges to a certain extent.
2. The utility model discloses can use in the power amplifier module of 5G basic station, realize the concurrent function of two 5G frequency channels, reduce holistic cost, can be fine be applied to in the fifth generation mobile communication system.
Drawings
Fig. 1 is a block diagram of a conventional Doherty power amplifier module.
Fig. 2 is a schematic block diagram of the dual-frequency Doherty power amplifier based on the left-hand and right-hand composite line structure of the present invention.
Fig. 3 is a schematic structural diagram of the dual-band power divider of the present invention.
Fig. 4 is the small signal simulation result of the dual-frequency power divider of the present invention.
Fig. 5 is a simplified equivalent circuit model of the left-right hand transmission line under the ideal balance condition of the present invention.
Fig. 6 is a schematic structural diagram of the dual-frequency impedance inverter of the present invention.
Fig. 7 is a diagram showing simulation results of S parameters of the dual-frequency impedance inverter of the present invention.
Fig. 8 the utility model provides a big signal characteristic simulation result sketch map of dual-frenquency Doherty power amplifier based on left and right hands combined line structure.
Detailed Description
The following are specific embodiments of the present invention and the accompanying drawings are used to further describe the technical solution of the present invention, but the present invention is not limited to these embodiments.
Referring to fig. 2, it is shown that the embodiment of the utility model provides a schematic block diagram of dual-frenquency Doherty power amplifier based on right-hand and left-hand composite line structure, include that the dual-frenquency merit based on right-hand and left-hand transmission line divides ware, carrier power amplification module, peak power amplification module, dual-frenquency impedance inverter, closes way output matching network. Compared with the traditional Doherty structure shown in FIG. 1, the utility model discloses replace the 1/4 wavelength microstrip line in traditional Wilkinson power divider and impedance inverter with the right-hand and left-hand composite transmission line. The carrier power amplification module comprises a carrier input matching/biasing network, a carrier power amplifier, a carrier output matching/biasing network and a double-frequency impedance inverter; the peak power amplification module comprises a peak power amplifier phase compensation line, a peak input matching/biasing network, a peak power amplifier and a peak output matching/biasing network; the combined output matching network comprises a three-step impedance matching microstrip line. The double-frequency power divider realizes power distribution of any two frequency bands, and can expand the bandwidth of two working frequency bands while only using a first-level Wilkinson power divider structure; the impedance inverter based on the left-right hand transmission line theory can randomly select two working frequency bands on the basis of not changing the whole structure, and meanwhile, the bandwidths of the two working frequency bands can be expanded to a certain extent. Because the output end of the carrier power amplifier is provided with the double-frequency resistance anti-reversion line, in order to ensure that the carrier power amplifier and the peak power amplifier can reach the same phase at the combining point, the phase compensation line is added at the input end of the peak power amplifier.
In this embodiment, the input and output matching network performs dual-frequency impedance matching by using a structure in which a T-shaped structure and a step microstrip line are connected in series, and expands the bandwidths of two operating frequency bands to a certain extent. The carrier input matching/biasing network is the same as the peak input matching/biasing network, and the biasing circuit is realized by adopting a conventional technical method in the field; carrier output matching to 2R opt Matching the peak output to R opt . The carrier power amplifier impedance transformation line is the same as the peak power amplifier phase compensation line and is based on left-hand and right-hand transmissionThe line is a dual-frequency impedance transformation line (at center frequency) having a characteristic impedance of 50 Ω.
Wherein R is opt The optimal load resistance value of the carrier amplifier and the peak amplifier in the B-type mode is obtained.
Referring to fig. 3 and 4, a schematic block diagram and a simulation result of the dual-frequency power divider of this embodiment are shown, the dual-frequency power divider based on the left-right hand transmission line is composed of microstrip lines TL 1-TL 15, arc microstrip lines Curve 1-Curve 4, capacitors C1-C6, and a resistor R1, wherein one end of the microstrip line TL1 is used as a port 1, and the other section is connected with one ends of TL2 and TL 3. Microstrip lines TL14, TL15 have one end as port 2 and port 3, and the other end connected to one end of TL12, TL13, respectively. The microstrip line TL2, the arc microstrip line Curve1, the microstrip line TL5, the capacitor C1, the capacitor C2, the capacitor C3, the microstrip line TL10, the arc microstrip line Curve3 and the microstrip line TL12 are sequentially connected in series to form one path of the power divider, and the microstrip line TL3, the arc microstrip line Curve2, the microstrip line TL14, the capacitor C4, the capacitor C5, the capacitor C6, the microstrip line TL11, the arc microstrip line Curve4 and the microstrip line TL13 are sequentially connected in series to form the other path of the power divider. Short-circuit branch microstrip lines TL6 and TL7 are loaded between capacitors C1 and C2 and between C2 and C3 respectively to form a left-right hand compound line structure, and short-circuit branch microstrip lines TL8 and TL9 are loaded between capacitors C4 and C5 and between C5 and C6 respectively to form a left-right hand compound line structure. Series resistors R1 are connected between microstrip lines TL12 and TL13 in series to balance current, so that a double-frequency Wilkinson power divider based on a left-hand and right-hand composite line is formed, and the working frequency band is 3.3-3.6GHz and 4.8-5.0 GHz; the percentage of the components is 1: 1.
referring to fig. 5, the impedance inverter of the present embodiment adopts a left-right-hand composite line structure instead of the conventional 50 Ω, 1/4 wavelength line. The left-hand and right-hand compound line structure is formed by sequentially connecting a microstrip line TL16, a capacitor C7, a capacitor C8, a capacitor C9 and a microstrip line TL19 in series, the connecting part of the capacitor C7 and the capacitor C8 and the connecting part of the capacitor C8 and the capacitor C9 are respectively connected with a short-circuit stub microstrip line TL17 and a short-circuit stub microstrip TL18 in parallel, and the propagation constant and the characteristic impedance of the left-hand and right-hand compound line are respectively as follows:
wherein, L' R 、C' R 、L' L 、C' L Respectively is distributed inductance and capacitance of unit length; and omega is an operating frequency point. If a composite right and left handed transmission line is used instead of the 1/4 wavelength impedance transformation line, it is necessary to satisfy:
β CRLH (ω＝ω 1 )＝β 1 (4)
wherein, Z t Characteristic impedance of a conventional 1/4 wavelength impedance inverter; omega 1 Is the first working frequency point; beta is a 1 The phase shift corresponding to the first working frequency point.
The formula and the characteristic impedance which meet the conditions form three independent equations which contain four variables, so that the equation has a degree of freedom, the equation can possibly meet the working condition of a second working frequency point, and the parameters of the left-hand and right-hand composite transmission line are as follows:
wherein, ω is 1 、ω 2 Two frequency points for work, beta 1 、β 2 The phase shifts are respectively corresponding to the two working frequency points. The above parameters are ideal and uniform composite right-left hand transmission lines, but in practical application, the LC ladder network is usually used to construct the composite right-left hand transmission lines, so the parameters of the actual right-left hand transmission lines are as follows:
wherein N is the number of LC trapezoidal structural units, phi 1 、φ 2 Is the total phase shift of the N building blocks.
In this embodiment, L is R ，C R ,L L Converted into microstrip line and retained C L The original value of (a). Left-right hand composite line selection C in double-frequency power divider L 1pF, short circuit branch line is selected as Z 0 90 omega and 75 theta, and Z is selected from the right-hand line at two ends 0 90 Ω, θ 135 °; left-right hand composite wire selection C in double-frequency impedance inverter L 1pF, short circuit branch line is selected as Z 0 57 omega and theta 51 degrees, and Z is selected from right-hand lines at two ends 0 ＝47Ω、θ＝133°。
Referring to fig. 6, which is a graph of simulation results of S parameters of the dual-band impedance inverter of the present embodiment, S11 can be suppressed below-15 dB in both frequency bands of 3.3-3.6GHz and 4.8-5.0GHz, and has a good effect on impedance transformation in two frequency bands, thereby better implementing replacement of 1/4 wavelength impedance transformation-resistant line.
Referring to fig. 7, which is a schematic diagram of a large signal characteristic simulation result of the dual-frequency Doherty power amplifier based on the left-right-hand composite line structure in this embodiment, due to the application of the composite left-right-hand structure to the dual-frequency impedance inverter and the dual-frequency power divider, the Doherty power amplifier can extend the working bandwidth to a certain extent while ensuring the saturation efficiency and the back-off efficiency in two frequency bands of the 5G standard. The saturation output power in the working frequency band of 3.3-3.6GHz and 4.8-5.0GHz is about 42dBm, the saturation drain efficiency is 68-60%, and the 6dB back-off efficiency is 55-43%.
The utility model also discloses a design method of double-frenquency Doherty power amplifier based on left and right hands composite line structure specifically includes following step:
step S1: load pull is carried out on the used power amplifier according to the required frequency to obtain the required optimal power and the impedance of the optimal efficiency point;
step S2: carrying out corresponding double-frequency output matching circuit design on the optimal impedance value;
step S3: designing an impedance inverter, which comprises the following specific steps:
obtaining a central frequency point omega according to the required double-frequency band 1 、ω 2 (ii) a According to the requirementsThe total phase shift phi of the two required frequency points is obtained by analysis 1 、φ 2 (ii) a Analyzing according to circuit parameter requirements to obtain the number N of the required LC structural units; identifying the characteristic impedance Z of an impedance inverter t 50 Ω; converting the parameters obtained by the analysis into the inductance and capacitance element parameters of the actual left-right-hand transmission line by using the following formula; considering an actual circuit, utilizing microstrip line equivalent left and right hand line parameters;
step S4: designing an input matching circuit;
step S5: designing a bias circuit;
step S6: the method comprises the following specific steps of designing a double-frequency power divider:
obtaining two central frequency points omega according to the required double-frequency band 1 、ω 2 (ii) a Total phase shift phi required for analyzing two frequency points 1 、φ 2 (ii) a Analyzing according to circuit parameter requirements to obtain the required number N of LC structure units, and confirming impedance Z t 70.7 Ω; converting the parameters obtained by the analysis into inductance and capacitance element parameters of actual left-right-hand transmission lines by using the following formula; considering an actual circuit, utilizing the equivalent left-hand line and right-hand line parameters of the microstrip line, and applying the obtained structure to two branches of the power divider;
step S7: designing a phase compensation line circuit;
step S8: designing a post-design matching circuit;
step S9: and building an overall circuit and optimizing the overall circuit.
As a further improvement, the design process of converting the parameters obtained by the analysis into the parameters of the lc element of the actual right-left-handed transmission line in the steps S3 and S6 by using the following formula includes:
the propagation constant and characteristic impedance of the left-hand and right-hand composite lines are respectively:
wherein, L' R 、C' R 、L' L 、C' L Respectively is distributed inductance and capacitance of unit length; and omega is an operating frequency point. If a composite right and left handed transmission line is used instead of the 1/4 wavelength impedance transformation line, it is necessary to satisfy:
β CRLH (ω＝ω 1 )＝β 1 (4)
wherein Z is t Characteristic impedance of a conventional 1/4 wavelength impedance inverter; omega 1 Is the first working frequency point; beta is a 1 The phase shift corresponding to the first working frequency point.
The formula and the characteristic impedance which meet the conditions form three independent equations which contain four variables, so that the equation has a degree of freedom, the equation can possibly meet the working condition of a second working frequency point, and the parameters of the left-hand and right-hand composite transmission line are as follows:
wherein, ω is 1 、ω 2 Two frequency points for work, beta 1 、β 2 The phase shifts are respectively corresponding to the two working frequency points. The parameters are ideally uniform composite right-left hand transmission lines, but in practical application, the LC ladder network is usually used to construct the composite right-left hand transmission lines, so that the actual right-left hand transmission linesParameters of the line:
wherein N is the number of LC trapezoidal structure units, phi 1 、φ 2 Is the total phase shift of the N building blocks.
In this embodiment, L is R ，C R ,L L Converted into microstrip line and retained C L The original value of (a).
Finally, it should be noted that: the above embodiments are only used to illustrate the technical solution of the present invention, and not to limit the same; although the present invention has been described in detail with reference to the foregoing embodiments, it should be understood by those skilled in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some or all of the technical features may be equivalently replaced; such modifications and substitutions do not depart from the spirit and scope of the present invention.
Claims (6)
1. The double-frequency Doherty power amplifier based on a left-hand and right-hand composite line structure is characterized by comprising a double-frequency power divider, a carrier power amplification module, a peak power amplification module, a double-frequency impedance inverter and a combined output matching network;
the input end of the double-frequency power divider is connected with the radio frequency signal output end, and the double-frequency power divider is divided into two paths of outputs which are respectively connected with the carrier loop and the peak loop;
the carrier loop at least comprises a carrier power amplification module and a double-frequency impedance inverter, wherein the carrier power amplification module comprises a carrier input matching/biasing network, a carrier power amplifier and a carrier output matching/biasing network;
the peak value loop at least comprises a peak value power amplifier phase compensation line and a peak value power amplification module, wherein the peak value power amplification module comprises a peak value input matching/biasing network, a peak value power amplifier and a peak value output matching/biasing network;
the carrier loop and the peak loop are combined to output and are connected with a load through a combined output matching network, and the combined output matching network adopts a three-step impedance matching microstrip line;
the double-frequency power divider and the double-frequency impedance inverter both adopt a composite left-right hand transmission line structure.
2. The dual-frequency Doherty power amplifier based on a left-hand and right-hand composite line structure as claimed in claim 1, wherein the dual-frequency power divider is a dual-frequency Wilkinson power divider based on a left-hand and right-hand composite line, and is composed of microstrip lines TL 1-TL 15, arc microstrip lines Curve 1-Curve 4, capacitors C1-C6 and a resistor R1, wherein one end of the microstrip line TL1 is used as an input port, and the other end of the microstrip line TL1 is connected with one ends of microstrip lines TL2 and TL 3; the microstrip line TL2, the arc microstrip line Curve1, the microstrip line TL5, the capacitor C1, the capacitor C2, the capacitor C3, the microstrip line TL10, the arc microstrip line Curve3 and the microstrip line TL12 are sequentially connected in series to form one path of the power divider, and the microstrip line TL3, the arc microstrip line Curve2, the microstrip line TL14, the capacitor C4, the capacitor C5, the capacitor C6, the microstrip line TL11, the arc microstrip line Curve4 and the microstrip line TL13 are sequentially connected in series to form the other path of the power divider; short-circuit branch microstrip lines TL6 and TL7 are loaded between capacitors C1 and C2 and between capacitors C2 and C3 respectively to form a left-right hand composite line structure; short-circuit stub microstrip lines TL8 and TL9 are loaded between capacitors C4 and C5 and between C5 and C6 respectively to form a left-right hand composite line structure; a resistor R1 is connected in series between the microstrip lines TL12 and TL13 to balance current, one end of the microstrip line TL14 is connected with one end of the microstrip line TL12 and one end of the resistor R1, one end of the microstrip line TL15 is connected with one end of the microstrip line TL13 and the other end of the resistor R1, and the other ends of the microstrip line TL14 and the microstrip line TL15 are respectively used as output ports.
3. The dual-frequency Doherty power amplifier based on the left-right hand composite line structure as claimed in claim 2, wherein the operating frequency bands of the dual-frequency power divider are 3.3-3.6GHz and 4.8-5.0 GHz; the percentage of the components is 1: 1.
4. the dual-frequency Doherty power amplifier based on a left-right hand composite line structure as claimed in claim 1, wherein the input and output matching networks adopt a T-shaped structure and a series connection structure of step microstrip lines for dual-frequency impedance matching, and the bandwidths of the two working frequency bands are expanded.
5. The dual-band Doherty power amplifier of claim 1 based on composite right and left handed line structure wherein the carrier input match/bias network is the same as the peak input match/bias network and the carrier output is matched to 2R opt Matching the peak output to R opt (ii) a Wherein R is opt The optimal load resistance value of the carrier amplifier and the peak amplifier under the bias condition of B class is obtained.
6. The dual-band Doherty power amplifier based on a left-hand and right-hand composite line structure as claimed in claim 1, wherein the combined output matching network is formed by multiple sections of series-connected step microstrip lines, and the output bandwidth of the combined output matching network is expanded to a certain extent.
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN114372434A (en) * | 2021-12-13 | 2022-04-19 | 杭州电子科技大学富阳电子信息研究院有限公司 | Double-frequency Doherty power amplifier based on left-hand and right-hand composite line structure and design method thereof |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN114372434A (en) * | 2021-12-13 | 2022-04-19 | 杭州电子科技大学富阳电子信息研究院有限公司 | Double-frequency Doherty power amplifier based on left-hand and right-hand composite line structure and design method thereof |
| CN114372434B (en) * | 2021-12-13 | 2024-06-04 | 杭州电子科技大学 | Double-frequency Doherty power amplifier based on left-right hand composite line structure and design method thereof |
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