CN109067364B - Doherty power amplifier with broadband and efficient output - Google Patents
Doherty power amplifier with broadband and efficient output Download PDFInfo
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- CN109067364B CN109067364B CN201810577902.XA CN201810577902A CN109067364B CN 109067364 B CN109067364 B CN 109067364B CN 201810577902 A CN201810577902 A CN 201810577902A CN 109067364 B CN109067364 B CN 109067364B
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
- H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
- H03F1/0288—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using a main and one or several auxiliary peaking amplifiers whereby the load is connected to the main amplifier using an impedance inverter, e.g. Doherty amplifiers
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/42—Modifications of amplifiers to extend the bandwidth
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/56—Modifications of input or output impedances, not otherwise provided for
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/21—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers with semiconductor devices only
- H03F3/217—Class D power amplifiers; Switching amplifiers
- H03F3/2176—Class E amplifiers
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Abstract
The invention discloses a broadband high-efficiency output Doherty power amplifier, which comprises a power divider, a phase shifter, a main power amplifier, an auxiliary power amplifier, a compensation network and a load modulation network, wherein the main power amplifier is connected with the auxiliary power amplifier through the phase shifter; the output end of the power divider is connected to the input end of a phase shifter, the output end of the phase shifter is respectively connected to the input ends of a main power amplifier and an auxiliary power amplifier, and the output ends of the main power amplifier and the auxiliary power amplifier are both connected to the input end of a load modulation network through a compensation network. Compared with the prior art, the invention has simple structure and convenient implementation, and can ensure that the Doherty power amplifier can still keep high-efficiency output characteristics in a wide frequency range.
Description
Technical Field
The invention relates to the field of wireless communication, in particular to a broadband high-efficiency output Doherty power amplifier.
Background
Radio frequency power amplifiers are important components of wireless systems, and with the continuous development of wireless communication technologies, data transmission rates and channel capacities in communication systems are continuously increased, which puts new requirements on the design of power amplifiers. The efficiency and the bandwidth are two core indexes of the power amplifier, the bandwidth is expanded, the communication equipment can support more bandwidth systems and transmission protocols, the efficiency is improved, and the energy loss can be reduced.
In order to reduce the nonlinear distortion of a signal when transmitting a high peak-to-average ratio modulated signal, a power back-off technique is often used to keep the signal away from the saturation region of the power amplifier. The efficiency of the conventional power amplifier is drastically reduced with the back-off of the output power, and the Doherty power amplifier is widely used in a communication system because it can maintain a high efficiency in a back-off power range. In a conventional Doherty power amplifier, a compensation line is generally used before two power amplifiers to adjust the phase characteristics of the two power amplifiers, and the phase difference of the two power amplifiers can be changed violently along with the change of frequency due to the fact that the phase of the compensation line is changed violently along with the change of frequency, so that the output efficiency of the two power amplifiers after being combined is reduced violently, and the high-efficiency output characteristics cannot be maintained in a wide frequency band range.
Disclosure of Invention
In order to solve the above problems, an object of the present invention is to provide a wide-band Doherty power amplifier with high output efficiency, which can maintain the high output efficiency of the Doherty power amplifier in a wide frequency range.
In order to make up for the defects of the prior art, the invention adopts the technical scheme that:
a broadband Doherty power amplifier with high-efficiency output comprises a power divider, a phase shifter, a main power amplifier, an auxiliary power amplifier, a compensation network and a load modulation network; the output end of the power divider is connected to the input end of a phase shifter, the output end of the phase shifter is respectively connected to the input ends of a main power amplifier and an auxiliary power amplifier, and the output ends of the main power amplifier and the auxiliary power amplifier are both connected to the input end of a load modulation network through a compensation network.
Further, the phase shifter comprises a phasing line and a reference line; the input end of the phase shifting line is connected to the first output end of the power divider, and the output end of the phase shifting line is connected to the input end of the main power amplifier; the input of the reference line is connected to the second output of the power divider and the output is connected to the input of the auxiliary power amplifier.
Further, the compensation network comprises a compensation line TL1, a compensation line TL2 and an impedance transformation line TL3, wherein two ends of the impedance transformation line TL3 are respectively connected to output ends of the compensation line TL1 and the compensation line TL 2; the output end of the main power amplifier is connected to the input end of the load modulation network through a compensation line TL1 and an impedance transformation line TL3, and the output end of the auxiliary power amplifier is connected to the input end of the load modulation network through a compensation line TL 2.
Further, the phase-shifting line adopts a T-shaped structure and comprises a transmission line TL8, an open-circuit branch TL9 and a transmission line TL10, wherein the transmission line TL8, the open-circuit branch TL9 and the transmission line TL10 are connected in a pairwise manner, one end of the transmission line TL8 is connected to the first output end of the power divider, and one end of the open-circuit branch TL9 is connected to the input end of the main power amplifier.
Further, the load modulation network comprises a transmission line TL4, a transmission line TL5, a transmission line TL6, a transmission line TL7 and a load resistor RL which are connected in series in sequence, wherein the transmission line TL4 is respectively connected to a compensation line TL2 and an impedance transformation line TL3, and the load resistor RL is connected to a reference ground.
Preferably, the characteristic impedance of both the compensation line TL1 and the compensation line TL2 is 50 ohms.
Preferably, the characteristic impedance and electrical length of the transmission line TL8 and the transmission line TL10 are the same.
Preferably, the load modulation network is a chebyshev impedance transformation network.
Preferably, the power divider is an unequal Wilkinson power divider.
Preferably, the main power amplifier and the auxiliary power amplifier are both inverse class F power amplifiers.
The invention has the beneficial effects that: the phase shifter structure is adopted to replace a compensation line structure arranged in front of the main power amplifier and the auxiliary power amplifier in the prior art, so that the change degree of the phase difference of the two branches along with the frequency change can be reduced, and the Doherty power amplifier can always keep high-efficiency output; the compensation network can enable the two paths of power amplifier outputs to form a combined path and then output the combined path to the outside through the load modulation network, thereby realizing communication. Therefore, the invention has simple structure and convenient implementation, and can ensure that the Doherty power amplifier can still keep high-efficiency output characteristics in a wide frequency range.
Drawings
The following description of the preferred embodiments of the present invention will be made in conjunction with the accompanying drawings.
FIG. 1 is a schematic diagram of the structure of the present invention;
FIG. 2 is a comparison graph of phase difference of two power amplifiers comparing the present invention with a conventional Doherty power amplifier;
fig. 3 is a graph comparing the maximum drain efficiency at saturated output power compared to a conventional Doherty power amplifier.
Detailed Description
Referring to fig. 1, the broadband high-efficiency output Doherty power amplifier of the invention includes a power divider PD, a phase shifter 1, a main power amplifier PA1, an auxiliary power amplifier PA2, a compensation network 2 and a load modulation network 3; the output terminal of the power divider PD is connected to the input terminal of the phase shifter 1, the output terminal of the phase shifter 1 is connected to the input terminals of the main power amplifier PA1 and the auxiliary power amplifier PA2, respectively, and the output terminals of the main power amplifier PA1 and the auxiliary power amplifier PA2 are connected to the input terminal of the load modulation network 3 through the compensation network 2.
Preferably, the load modulation network 3 is a chebyshev impedance transformation network.
Preferably, the power divider PD is an unequal Wilkinson power divider.
Preferably, the main power amplifier PA1 and the auxiliary power amplifier PA2 are both inverse F-class power amplifiers, and the output matching network thereof not only satisfies the optimal matching condition of fundamental wave, but also presents impedance close to infinity for odd harmonics and presents impedance close to infinity for even harmonics, so that the current on the inner plane of the transistor presents square wave, the voltage presents half sine wave, and a certain angle relationship is presented between the two, so that the time domain overlapping of the voltage and the current is reduced, and the direct current consumption energy is reduced, thereby improving the efficiency; the main PA1 may be turned on at any input power condition and the auxiliary PA2 is turned on at the point where the output power of the Doherty PA is backed off to 6 dB.
Specifically, the operating principle of the conventional Doherty power amplifier is well known, wherein the phase relationship between the main power amplifier PA1 and the auxiliary power amplifier PA2 is mainly determined by a compensation line, and the phase characteristics of the conventional compensation line are linear with the change of frequency, and at the central frequency, the optimal phase can be obtained by adjusting the length of the compensation line, so that the main power amplifier PA1 and the auxiliary power amplifier PA2 are in the optimal combining state, but when the operating frequency deviates from the central frequency, the operating frequency is generally reflected at two ends of the operating range, i.e., in a wide frequency range, the phase difference between two branches can be drastically changed with the change of frequency, and the combining efficiency can be greatly influenced;
the phase shifter 1 is adopted to replace a compensation line structure arranged in front of a main power amplifier PA1 and an auxiliary power amplifier PA2 in the prior art, so that the change degree of the phase difference of the two branches along with the frequency change can be reduced, and the Doherty power amplifier can always keep high-efficiency output; the compensation network 2 can combine the two paths of power amplifier outputs and then output the combined output to the outside through the load modulation network 3, thereby realizing communication. Therefore, the invention has simple structure and convenient implementation, and can ensure that the Doherty power amplifier can still keep high-efficiency output characteristic in a wide frequency range;
according to experiments, referring to fig. 3, in the saturated output power state, the maximum drain efficiency of the present invention is slightly lower than that of the conventional Doherty power amplifier in the frequency band range of 2.45GHz to 2.65GHz, that is, in the central frequency band range, but in the frequency band range of 1.9GHz to 2.45GHz and the frequency band range of 2.65GHz to 3.0GHz, that is, in the wide frequency range, the maximum drain efficiency of the present invention is greatly improved compared with that of the conventional Doherty power amplifier, and the maximum drain efficiency in the frequency range of 2.2GHz to 2.7GHz is maintained at more than 70%.
Further, referring to fig. 1, the phase shifter 1 includes a phasing line 11 and a reference line Q; the input end of the phasing line 11 is connected to the first output end of the power divider PD, and the output end is connected to the input end of the main power amplifier PA 1; the input of the reference line Q is connected to the second output of the power divider PD and the output is connected to the input of the auxiliary power amplifier PA 2.
Preferably, the reference line Q is a common transmission line; the design center frequency of the phase shifter 1 is 2.5GHz, the phase difference of the phase shifter 1 at the frequency point is also designed to be 80 degrees according to the phase difference required by the original compensation line being 80 degrees, as can be seen from fig. 2, the phase of the original compensation line linearly changes with the frequency, when the frequency of the input signal deviates from the center frequency, the change of the phase difference is large, and after the phase shifter 1 is adopted, the change degree of the phase difference of the two branches can be seen to be obviously slowed down, so that the combining efficiency of the Doherty power amplifier in the frequency band is improved.
Further, referring to fig. 1, the compensation network 2 includes a compensation line TL1, a compensation line TL2, and an impedance transformation line TL3, wherein two ends of the impedance transformation line TL3 are respectively connected to output ends of the compensation line TL1 and the compensation line TL2, so as to form a combination; the output end of the main power amplifier PA1 is connected to the input end of the load modulation network 3 through a compensation line TL1 and an impedance transformation line TL3, and the output end of the auxiliary power amplifier PA2 is connected to the input end of the load modulation network 3 through a compensation line TL2, that is, the combining end is connected to the load modulation network 3 in series, preferably, the characteristic impedances of the compensation line TL1 and the compensation line TL2 are both 50 ohms, and the characteristic impedance of the impedance transformation line TL3 may also be 50 ohms.
Further, referring to fig. 1, the phasing line 11 is of a T-shaped structure and includes a transmission line TL8, an open stub TL9 and a transmission line TL10, the transmission line TL8, the open stub TL9 and the transmission line TL10 are connected in pairs, one end of the transmission line TL8 is connected to the first output end of the power divider PD, and one end of the open stub TL9 is connected to the input end of the main power amplifier PA 1; preferably, the characteristic impedance and electrical length of the transmission line TL8 and the transmission line TL10 are the same.
Further, referring to fig. 1, the load modulation network 3 includes a transmission line TL4, a transmission line TL5, a transmission line TL6, a transmission line TL7, and a load resistor RL connected in series in sequence, where the transmission line TL4 is connected to a compensation line TL2 and an impedance transformation line TL3, the load resistor RL is connected to a reference ground, and can convert the combined characteristic impedance into half of the original characteristic impedance, and an output end of the load modulation network 3 may be directly used as an output end of the Doherty power amplifier, and of course, a relevant adjusting circuit or module may be disposed at a rear end of the load modulation network 3 to perform output.
While the preferred embodiments and basic principles of the present invention have been described in detail, it will be understood by those skilled in the art that the invention is not limited to the embodiments, but is intended to cover various modifications, equivalents and alternatives falling within the scope of the invention as claimed.
Claims (8)
1. A broadband Doherty power amplifier with high-efficiency output is characterized in that: the power amplifier circuit comprises a Power Divider (PD), a phase shifter (1), a main power amplifier (PA1), an auxiliary power amplifier (PA2), a compensation network (2) and a load modulation network (3); the output end of the Power Divider (PD) is connected to the input end of a phase shifter (1), the output end of the phase shifter (1) is respectively connected to the input ends of a main power amplifier (PA1) and an auxiliary power amplifier (PA2), and the output ends of the main power amplifier (PA1) and the auxiliary power amplifier (PA2) are connected to the input end of a load modulation network (3) through a compensation network (2);
the phase shifter (1) comprises a phase shifting line (11) and a reference line (Q); the input end of the phasing line (11) is connected to a first output end of the Power Divider (PD), and the output end is connected to the input end of a main power amplifier (PA 1); an input of the reference line (Q) is connected to a second output of the Power Divider (PD) and an output is connected to an input of an auxiliary power amplifier (PA 2);
the phase-shifting line (11) adopts a T-shaped structure and comprises a transmission line TL8, an open-circuit branch TL9 and a transmission line TL10, wherein the transmission line TL8, the open-circuit branch TL9 and the transmission line TL10 are connected in a pairwise manner, one end of the transmission line TL8 is connected to a first output end of a Power Divider (PD), and one end of the open-circuit branch TL9 is connected to an input end of a main power amplifier (PA 1).
2. The wide-band high-efficiency Doherty power amplifier of claim 1, wherein: the compensation network (2) comprises a compensation line TL1, a compensation line TL2 and an impedance transformation line TL3, wherein two ends of the impedance transformation line TL3 are respectively connected to output ends of the compensation line TL1 and the compensation line TL 2; the output end of the main power amplifier (PA1) is connected to the input end of the load modulation network (3) through a compensation line TL1 and an impedance transformation line TL3, and the output end of the auxiliary power amplifier (PA2) is connected to the input end of the load modulation network (3) through a compensation line TL 2.
3. The wide-band high-efficiency Doherty power amplifier of claim 2, wherein: the load modulation network (3) comprises a transmission line TL4, a transmission line TL5, a transmission line TL6, a transmission line TL7 and a load resistor RL which are sequentially connected in series, wherein the transmission line TL4 is respectively connected to a compensation line TL2 and an impedance transformation line TL3, and the load resistor RL is connected to a reference ground.
4. The wide-band high-efficiency Doherty power amplifier of claim 2, wherein: the characteristic impedance of both the compensation line TL1 and the compensation line TL2 is 50 ohms.
5. The wide-band high-efficiency Doherty power amplifier of claim 1, wherein: the transmission line TL8 and the transmission line TL10 have the same characteristic impedance and electrical length.
6. The wide-band high-efficiency Doherty power amplifier of claim 1, wherein: the load modulation network (3) is a Chebyshev impedance transformation network.
7. The wide-band high-efficiency Doherty power amplifier according to any one of claims 1-6, wherein: the Power Divider (PD) is an unequal Wilkinson power divider.
8. The broadband high-efficiency Doherty power amplifier of claim 7, wherein: the main power amplifier (PA1) and the auxiliary power amplifier (PA2) are both inverse class F power amplifiers.
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Citations (4)
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| CN103580623A (en) * | 2012-08-10 | 2014-02-12 | 中兴通讯股份有限公司 | Radiofrequency power amplifier device and radiofrequency power amplifying method |
| CN107547051A (en) * | 2017-08-28 | 2018-01-05 | 广东顺德中山大学卡内基梅隆大学国际联合研究院 | Doherty power amplifier based on distributed broadband impedance mapped structure |
| CN107887678A (en) * | 2017-10-11 | 2018-04-06 | 电子科技大学 | A kind of design method of phase shifter |
| US9973150B1 (en) * | 2016-12-30 | 2018-05-15 | Nxp Usa, Inc. | Doherty architecture for wideband power amplifier design |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| JP5732014B2 (en) * | 2012-09-20 | 2015-06-10 | 旭化成エレクトロニクス株式会社 | Doherty amplifier |
| US9531328B2 (en) * | 2014-12-16 | 2016-12-27 | Nxp Usa, Inc. | Amplifiers with a short phase path, packaged RF devices for use therein, and methods of manufacture thereof |
| EP3322091B1 (en) * | 2015-02-04 | 2019-09-18 | Ampleon Netherlands B.V. | Doherty amplifier |
| US9831857B2 (en) * | 2015-03-11 | 2017-11-28 | Peregrine Semiconductor Corporation | Power splitter with programmable output phase shift |
| CN106257827B (en) * | 2015-06-17 | 2020-08-18 | 南京中兴新软件有限责任公司 | Symmetrical Doherty power amplifier circuit device and power amplifier |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103580623A (en) * | 2012-08-10 | 2014-02-12 | 中兴通讯股份有限公司 | Radiofrequency power amplifier device and radiofrequency power amplifying method |
| US9973150B1 (en) * | 2016-12-30 | 2018-05-15 | Nxp Usa, Inc. | Doherty architecture for wideband power amplifier design |
| CN107547051A (en) * | 2017-08-28 | 2018-01-05 | 广东顺德中山大学卡内基梅隆大学国际联合研究院 | Doherty power amplifier based on distributed broadband impedance mapped structure |
| CN107887678A (en) * | 2017-10-11 | 2018-04-06 | 电子科技大学 | A kind of design method of phase shifter |
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