CN215342986U - Dipole antenna - Google Patents

Abstract

The utility model relates to the technical field of antennas, and provides a dipole antenna which comprises a conductive floor; the radiation unit is arranged opposite to the conductive floor and is connected with the conductive floor through a feed structure, one end of the feed structure is arranged at the central position of the radiation unit and is used as a feed point, and the other end of the feed structure is connected with the conductive floor; and a plurality of ground posts connected to the conductive floor and distributed around the feed structure in a central symmetry manner, wherein central symmetry axes of the ground posts coincide with an axis of the feed structure, and the radiation unit includes: the first dipole or the second dipole comprises a pair of butterfly radiating plates which are symmetrically arranged, and the center of the orthogonal intersection of the first dipole and the second dipole is the feeding point. Therefore, miniaturization is realized, the bandwidth of the antenna is increased, and wide beam coverage is realized by optimizing the structure and the size of the antenna.

Description

Dipole antenna

Technical Field

The utility model relates to the technical field of antennas, in particular to an antenna with dual-polarized crossed dipoles.

Background

The antenna is one of the most important components of a system such as wireless broadcasting, wireless communication and wireless detection, and the structure and the characteristics of the antenna determine the working performance of the whole system to a great extent. The dual-polarized antenna is composed of two antennas with mutually orthogonal polarization, and is widely applied to modern radar, communication and other systems. Commonly used dual polarized antennas are in the form of microstrip antennas, dipole antennas, Vivaldi antennas, etc. The crisscross dual-polarized antenna formed by two mutually orthogonal dipole antennas has the advantages of wide bandwidth, low processing difficulty, high reliability and the like, and is commonly used as an array unit of a dual-polarized phased array. However, the impedance of the conventional dual-polarized dipole antenna can be drastically changed during large-angle scanning, which further causes impedance mismatch and serious return loss.

Furthermore, the manufacturing costs and the resulting costs of prior art crossed dipole antennas are high. In addition, under some limited installation space environments, it is difficult to realize dual polarization, large bandwidth and wide beam coverage of the antenna.

The information disclosed in this background section is only for enhancement of understanding of the general background of the application and should not be taken as an acknowledgement or any form of suggestion that this information forms the prior art already known to a person skilled in the art.

SUMMERY OF THE UTILITY MODEL

In order to solve the technical problems, the utility model provides an antenna with dual-polarized crossed dipoles, which realizes miniaturization by optimizing the structure and size of the antenna, increases the bandwidth of the antenna by utilizing edge coupling of the crossed dipoles, widens the widths of E-plane and H-plane wave lobes of the antenna and realizes wide beam coverage.

The present invention provides a dipole antenna, comprising:

a conductive floor;

the radiating unit is arranged opposite to the conductive floor and is connected with the conductive floor through a feed structure, one end of the feed structure is arranged at the central position of the radiating unit and is used as a feed point, and the other end of the feed structure is connected with the conductive floor;

a plurality of grounding posts which are connected with the conductive floor and are distributed around the feed structure in a central symmetry way, and the central symmetry axes of the grounding posts are superposed with the central axis of the feed structure,

wherein, aforementioned radiating element includes: the first dipole or the second dipole comprises a pair of butterfly radiating plates which are symmetrically arranged, and the center of the orthogonal intersection of the first dipole and the second dipole is the feeding point.

Preferably, the first dipole and the second dipole orthogonally arranged in the radiation unit are arranged in the same plane, and the plane is parallel to the surface where the conductive floor is located.

Preferably, the intervals between the edges of the adjacent butterfly-shaped radiation plates in the first dipole and the second dipole are the same.

Preferably, the butterfly-shaped radiation plates in the first dipole and the second dipole are regular patterns with matched shapes of adjacent edges.

Preferably, the projection shape of each butterfly-shaped radiation plate on the conductive floor is a combined shape of a trapezoid and a rectangle, and the length of the side of the rectangle participating in splicing with the trapezoid is equal to that of the side participating in splicing.

Preferably, the projection shape of each butterfly-shaped radiation plate on the conductive floor is a sector shape, the sector angles of a pair of butterfly-shaped radiation plates on the same dipole are the same, and the sum of the sector angles of two pairs of butterfly-shaped radiation plates on different dipoles is less than or equal to 360 °.

Preferably, the two pairs of butterfly radiation plates located on different dipoles have the same sector radius.

Preferably, the number of the plurality of ground posts is an even number, and projections of the even number of the plurality of ground posts on the conductive floor are distributed at equal central angles with the center of the conductive floor as a center.

Preferably, the interval between adjacent butterfly-shaped radiation plate edges gradually increases outwards along the ray with the feeding point as the starting point.

Preferably, the heights of the plurality of grounding posts are all the same and are smaller than the distance between the radiating unit and the conductive floor.

The utility model has the beneficial effects that: the utility model provides a dipole antenna, which comprises a conductive floor; the radiation unit is arranged opposite to the conductive floor and is connected with the conductive floor through a feed structure, one end of the feed structure is arranged at the central position of the radiation unit and is used as a feed point, and the other end of the feed structure is connected with the conductive floor; and a plurality of ground posts connected to the conductive floor and distributed around the feed structure in a central symmetry manner, wherein central symmetry axes of the ground posts coincide with a central axis of the feed structure, and the radiation unit includes: the first dipole or the second dipole comprises a pair of butterfly radiating plates which are symmetrically arranged, and the center of the orthogonal intersection of the first dipole and the second dipole is the feeding point. Therefore, miniaturization is realized by optimizing the structure and the size of the antenna; the edge coupling of the (orthogonal) crossed dipole is utilized, so that the bandwidth of the antenna is increased; and the distributed capacitance is introduced through a plurality of grounding columns to adjust the 3dB bandwidth of the E surface and the H surface of the antenna, so that the wide beam coverage is realized.

Drawings

The above and other objects, features and advantages of the present invention will become more apparent from the following description of the embodiments of the present invention with reference to the accompanying drawings.

Fig. 1 is a perspective view of a dual-polarized crossed dipole antenna according to an embodiment of the present invention;

fig. 2 is a schematic cross-sectional view and a schematic size diagram of the dual-polarized crossed dipole antenna shown in fig. 1;

fig. 3 shows a front view structural diagram of the dual polarized crossed dipole antenna shown in fig. 1;

fig. 4 shows a top view structural diagram of the dual polarized crossed dipole antenna shown in fig. 1;

fig. 5a is a top view structural diagram of the dual-polarized crossed dipole antenna shown in fig. 4 with the radiating elements removed;

fig. 5b and 5c respectively show schematic diagrams of deformed configurations of the radiating elements in the dual-polarized crossed-dipole antenna shown in fig. 4 in other alternative embodiments;

fig. 6 shows a graphical representation of the reflection coefficient of the dual polarized crossed dipole antenna of fig. 1;

FIG. 7 shows a schematic gain curve of the E-plane, H-plane pattern of the dual-polarized crossed-dipole antenna of FIG. 1 as a function of the angle of the theta at a frequency of 1.2 GHz;

FIG. 8 is a graph showing the gain curve of the E-plane, H-plane pattern of the dual-polarized crossed-dipole antenna of FIG. 1 as a function of the angle of the theta at a frequency of 1.62 GHz;

fig. 9 shows a gain curve diagram of the E-plane, H-plane pattern of the dual-polarized crossed-dipole antenna of fig. 1 as a function of the angle of the theta at a frequency of 1.84 GHz.

Detailed Description

To facilitate an understanding of the utility model, the utility model will now be described more fully with reference to the accompanying drawings. Preferred embodiments of the present invention are shown in the drawings. The utility model may, however, be embodied in different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete.

Unless defined otherwise, all technical and scientific terms used herein have the same meaning as commonly understood by one of ordinary skill in the art to which this invention belongs. The terminology used herein in the description of the utility model is for the purpose of describing particular embodiments only and is not intended to be limiting of the utility model.

Modern communication systems can be divided into two categories according to the way of data transmission: wired communication and wireless communication. Wired communication requires information to be transferred via various transmission lines, such as a local area network, a wired telephone, etc.; wireless communication is the transmission of information by means of radio waves, such as mobile communication, satellite communication, navigation, remote sensing, etc., and the combination of the two communication modes promotes the development of modern communication business. In recent years, wireless communication technology has been developed due to the push of new technologies, and antennas have also played an increasingly important role as important components of wireless communication terminals.

With the coming of the big data era of the internet, people put higher requirements on real-time, rapid, large-capacity and accurate data transmission, and a fifth-generation mobile communication system (5G) provides a faster network transmission rate and relatively lower cost, so that the interconnection of everything becomes possible, and the development trend of future communication systems is formed. Although mobile communication systems are continuously updated, at present, multiple systems coexist, and operators need to support 2G, 3G, LTE and 5G systems which are put into commercial use in the future, and the coexistence of multiple communication systems and increasingly scarce site resources, so that people have more demands on broadband antennas which can serve multiple systems simultaneously.

With the increasingly complex electromagnetic environment, the electromagnetic waves can encounter a large number of buildings, trees, rain, fog and other obstacles in the transmission process to be reflected, refracted and scattered, so that the electromagnetic waves with different amplitudes and phases received by a receiving end are superposed, and the normal operation of the system can be influenced by the multipath fading phenomenon. Diversity technology is usually used to reduce the influence of multipath fading, and this technology can make the receiving end obtain multiple signals, and combine them through certain data processing to obtain the final received signal, thereby reducing the influence of multipath fading. The dual-polarized antenna can work in a transceiving duplex mode simultaneously as one of diversity technologies, namely, the dual-polarized antenna can simultaneously transmit or receive two electromagnetic waves with mutually orthogonal polarization, and the influence caused by multipath attenuation is reduced through frequency multiplexing.

It can be known from the basic knowledge of the antenna that some performances of the antenna are mutually restricted, and each performance of the antenna is comprehensively considered and reasonably balanced when the antenna is designed, for example, the working bandwidth of the antenna cannot be ignored due to pursuit of miniaturization of the antenna, and the size of the whole structure of the antenna cannot be ignored due to pursuit of high gain and simple increase of the number of antenna array subunits. Therefore, designing an antenna with simple structure, low cost, wide frequency band, stable in-band gain and good directivity faces huge challenges. The broadband dual-polarized antenna has become one of the research hotspots in the field of modern wireless communication due to its unique advantages.

Therefore, the utility model provides the dipole antenna with the crossed dual-polarized dipole, and not only miniaturization is realized, but also the bandwidth of the antenna is increased and wide beam coverage is effectively realized by optimizing the structure and the size of the antenna.

The present invention will be described in detail below with reference to the accompanying drawings.

Fig. 1 is a perspective structural view of a dual-polarized cross dipole antenna according to an embodiment of the present invention, fig. 2 is a schematic cross-sectional view and a schematic size view of the dual-polarized cross dipole antenna shown in fig. 1, fig. 3 is a schematic front view of the dual-polarized cross dipole antenna shown in fig. 1, and fig. 4 is a schematic top view of the dual-polarized cross dipole antenna shown in fig. 1.

Referring to fig. 1 to 4, an embodiment of the present invention provides a dipole antenna 100 with dual-polarized crossed dipoles, which can be used for communication of various installation platforms, such as ground, aircraft, poles, and the like. Under the condition of not destroying the aerodynamics of the carrier, the directional radiation electromagnetic signal with high gain and large scanning angle can be effectively provided, and the high-quality communication effect is ensured.

The dipole antenna 100 includes: a conductive floor 10, a radiating element 30, a feed structure (not shown) and a plurality of ground posts 20,

wherein, the radiation unit 30 is disposed opposite to the conductive floor 10, and is connected to the conductive floor 10 through a feeding structure, one end of the feeding structure is disposed at the center of the radiation unit 30 and serves as a feeding point of the radiation unit 30, and the other end of the feeding structure is connected to the conductive floor 10;

the grounding posts 20 are connected with the conductive floor 10 and are distributed around the feeding structure in a central symmetry manner, and the central symmetry axes of the grounding posts 20 coincide with the central axis of the feeding structure,

the radiation unit 30 includes a first dipole 301 and a second dipole 302 arranged orthogonally in a crossing manner, each of the first dipole 301 and the second dipole 302 includes a pair of butterfly-shaped radiation plates symmetrically arranged, and a center of the orthogonal crossing of the first dipole 301 and the second dipole 302 is a feeding point of the center of the radiation unit 30.

In the present embodiment, the feeding structure may include, for example, two Γ -type feeding lines 40 and a feeding cable 50 coupled to the Γ -type feeding line 40, the feeding cable 50 has an inner core and an outer skin surrounding the inner core, specifically, one end of the Γ -type feeding line 40 is connected to a feeding point of a corresponding dipole, the other end is connected to the inner core of the feeding cable 50, and the outer skin of the feeding cable 50 is connected to the conductive floor 10.

In another embodiment, the radiating element 30 may also adopt an air-filled coaxial feeding structure, which may include, for example, an outer wall 50 and an inner probe 40, the inner probe 40 is wrapped inside the outer wall 50, one end of the outer wall 50 is connected to the radiating element 30, the other end of the outer wall 50 is connected to the conductive floor 10 for grounding and supporting the radiating element 30, one end of the inner probe 40 is connected to the feeding point of the first dipole 301 or the second dipole 302 through a feeding connection component, and the other end of the inner probe 40 is connected to an SMA connector under the conductive floor 10, so that the inner probe can be directly connected to a signal receiving device (e.g., a low noise amplifier) of the coaxial feeding.

In this embodiment, the first dipole 301 and the second dipole 302 orthogonally crossed in the radiation unit 30 are disposed in the same plane, and the plane is parallel to the surface on which the conductive floor 10 is located, as shown in fig. 2 and 3.

In this embodiment, the intervals between the adjacent butterfly-shaped radiation plate edges in the first dipole 301 and the second dipole 302 may be the same (as shown in fig. 5b and fig. 5 c), or the intervals between the adjacent butterfly-shaped radiation plate edges gradually increase outwards along the ray whose starting point is the feeding point (as shown in fig. 4).

In this embodiment, the butterfly-shaped radiation plates in the first dipole 301 and the second dipole 302 are in regular patterns with matching shapes of adjacent edges, as shown in fig. 5b and 5 c.

In an embodiment of the present invention, a projection shape of each of the butterfly-shaped radiation plates on the conductive floor 10 is a combination shape of a trapezoid and a rectangle, as shown in fig. 5b, and lengths of sides of the rectangle and the trapezoid participating in splicing are equal.

In another embodiment of this embodiment, the projection shape of each of the butterfly radiation plates on the conductive floor 10 is a sector shape, as shown in fig. 5c, and the sector angles of one pair of butterfly radiation plates located on the same dipole are the same, and the sum of the sector angles of two pairs of butterfly radiation plates located on different dipoles is less than or equal to 360 °.

In this embodiment, the two pairs of butterfly radiating plates located on different dipoles have the same radius of the sector.

It should be noted that, the foregoing fig. 4, fig. 5a and fig. 5c only exemplarily show several ways of the projection shape of the radiation unit 30 on the foregoing conductive floor 10, but are not limited thereto, and the projection shape of the radiation unit 30 in the present invention may also be other embodiments that can be easily conceived by a person having ordinary skill in the art, and is not limited to the present invention.

It should be noted that, the dimensions and schematic simulation results of the components in the dipole antenna 100 structure given below are given on the basis of the structure shown in fig. 4, and the structures and dimensions of the components in the dipole antenna 100 structure are also adaptively adjusted according to the simulation results for achieving the same or better bandwidth gain and miniaturization effect for the radiating elements of different embodiments, which are not described in detail herein.

In this embodiment, referring to fig. 5a, the grounding posts 20 are distributed with an even number of grounding posts 20 with the center of the conductive floor 10 as the center and with an evenly divided center angle, for example, the circle radius D/2 where the connecting line of the centers of the grounding posts 20 is located may be set to be 36 mm.

In this embodiment, the heights of the plurality of ground studs 20 may be the same and smaller than the distance between the radiation unit 30 and the conductive floor 10. Referring to fig. 2 and 5a, the height H (antenna size) of the radiating element 30 from the conductive floor 10 is 60mm, the height H of the plurality of ground studs 20 may be 35mm, and the diameter d may be 4 mm.

In the present embodiment, referring to fig. 4, in the projection shapes of the butterfly radiation plates located in the first dipole 301 and the second dipole 302 on the conductive floor 10, the width c of the bottom side of the trapezoid may be set to 55mm, the width a of the rectangle may be set to 11.5mm, and in the projection shapes of the pair of butterfly radiation plates located in the same dipole on the conductive floor 10, the distance b between the far sides of the rectangles located opposite to each other may be set to 90 mm. In a further embodiment, for example, the projected shape of the conductive floor 10 is a square, and the side length c of the square is 200 mm.

The dipole antenna 100 provided by the utility model uses the patch antenna with a pair of butterfly-shaped radiation plates which are horizontally arranged in a crossed manner as the first dipole 301 and the second dipole 302, is used for improving the impedance fluctuation of the antenna during large-angle scanning, reduces the size of the antenna by using the mutual coupling of the adjacent edges of the crossed dipoles through structural deformation and increases the bandwidth of the antenna.

In addition, a coaxial feed structure is adopted to excite two dipoles of the antenna simultaneously, and distribution capacitors are introduced through eight grounding columns to reduce main lobe gain so as to widen the lobe width of the antenna, and the 3dB lobe widths of the E surface and the H surface of the antenna are effectively adjusted according to the symmetrical oscillator theory, so that wide beam coverage is realized.

Fig. 6 is a graph showing a reflection coefficient of the dual-polarized cross dipole antenna shown in fig. 1, fig. 7 is a graph showing a gain curve of an E-plane and H-plane pattern of the dual-polarized cross dipole antenna shown in fig. 1 as a function of the angle of the theta at a frequency of 1.2GHz, fig. 8 is a graph showing a gain curve of an E-plane and H-plane pattern of the dual-polarized cross dipole antenna shown in fig. 1 as a function of the angle of the theta at a frequency of 1.62GHz, and fig. 9 is a graph showing a gain curve of an E-plane and H-plane pattern of the dual-polarized cross dipole antenna shown in fig. 1 as a function of the angle of the theta at a frequency of 1.84 GHz.

Fig. 6 shows the reflection coefficient S11 in the whole desired frequency band range, and it can be seen from fig. 6 that the reflection coefficient S11 of the dipole antenna 100 is less than-10 dB in the frequency band range of 0.9GHz to 1.84GHz, which can meet the engineering requirement.

Referring to fig. 7, from the gain curve of the dual-polarized cross-dipole antenna 100 provided by the present invention, when the frequency is 1.2GHz, the E-plane (Phi is 0 °) and H-plane (Phi is 90 °) patterns of the antenna change with the theta angle, the antenna has a stable pattern, the half-power beam width of the antenna is greater than 60 °, the antenna gain is greater than 2.4dB, the axial cross polarization ratio is greater than 15dB, and the cross polarization ratio in the 90-degree direction is greater than 10 dB.

Similarly, referring to fig. 8 and fig. 9, from the gain curves of the dual-polarized cross dipole antenna 100 provided by the present invention, when the frequency is 1.62GHz and 1.84GHz, respectively, the E-plane (Phi ═ 0 °) and H-plane (Phi ═ 90 °) patterns of the antenna change with the theta angle, the three frequency points m1, m2, and m3 of the antenna in the E-plane, and the 3dB lobe widths of the antenna in the three frequency points m1, m4, and m5 of the H-plane are all greater than 60 °, and the antenna gain is greater than 2.4 dB.

Therefore, the dipole antenna 100 with dual-polarized crossed dipoles provided by the utility model can meet the requirement of the width of the wave lobe in engineering application.

In summary, the dipole antenna provided by the present invention includes: a conductive floor 10; the radiating element 30 is arranged opposite to the conductive floor 10, the radiating element 30 is connected with the conductive floor 10 through a feed structure, one end of the feed structure is arranged in the center of the radiating element 30 and is used as a feed point of the radiating element, and the other end of the feed structure is connected with the conductive floor 10; and a plurality of ground posts 20 connected to the conductive floor 10 and distributed around the feeding structure in a central symmetry manner, and a central symmetry axis of the plurality of ground posts 20 coincides with a central axis of the feeding structure, wherein the radiating unit 30 includes: a first dipole 301 and a second dipole 302 arranged orthogonally in a crossing manner, wherein the first dipole 301 or the second dipole 302 includes a pair of butterfly radiating plates arranged symmetrically therein, and the center of the orthogonal crossing of the first dipole 301 and the second dipole 302 is the aforementioned feeding point. Therefore, miniaturization is realized by optimizing the structure and the size of the antenna; the edge coupling of (orthogonal) crossed dipoles (301 and 302) is utilized, so that the bandwidth of the antenna is increased; and the distributed capacitance is introduced by the grounding posts 20 to adjust the 3dB bandwidth of the E surface and the H surface of the antenna, so that the wide-beam coverage is realized, and the wide-beam coverage has a wide application prospect in ultrahigh frequency (UHF) communication.

It should be noted that in the description of the present invention, it is to be understood that the terms "upper", "lower", "inner", and the like, indicate orientation or positional relationship, are only for convenience of describing the present invention and simplifying the description, but do not indicate or imply that the referenced components or elements must have a particular orientation, be constructed and operated in a particular orientation, and thus should not be construed as limiting the present invention.

Further, in this document, the contained terms "include", "contain" or any other variation thereof are intended to cover a non-exclusive inclusion, so that a process, a method, an article or an apparatus including a series of elements includes not only those elements but also other elements not explicitly listed or inherent to such process, method, article or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.

Finally, it should be noted that: it should be understood that the above examples are only for clearly illustrating the present invention and are not intended to limit the embodiments. Other variations and modifications will be apparent to persons skilled in the art in light of the above description. And are neither required nor exhaustive of all embodiments. And obvious variations or modifications of the utility model may be made without departing from the scope of the utility model.

Claims (10)

1. A dipole antenna, comprising:

a conductive floor;

the radiating unit is arranged opposite to the conductive floor and is connected with the conductive floor through a feed structure, one end of the feed structure is arranged at the central position of the radiating unit and is used as a feed point, and the other end of the feed structure is connected with the conductive floor;

a plurality of grounding posts which are connected with the conductive floor and are distributed around the feed structure in a centrosymmetric manner, and the centrosymmetric axes of the grounding posts are superposed with the central axis of the feed structure,

wherein the radiation unit includes: the antenna comprises a first dipole and a second dipole which are arranged in an orthogonal crossing manner, wherein the first dipole or the second dipole comprises a pair of butterfly-shaped radiating plates which are symmetrically arranged, and the center of the orthogonal crossing of the first dipole and the second dipole is the feed point.

2. The dipole antenna of claim 1, wherein the first dipole and the second dipole orthogonally crossed in the radiating element are disposed in a same plane, and the plane is parallel to a surface on which the conductive floor is disposed.

3. A dipole antenna as recited in claim 1, wherein adjacent edges of said butterfly radiating plates of said first and second dipoles are equally spaced.

4. A dipole antenna as recited in claim 3, wherein said bowtie-shaped radiating patches of said first and second dipoles are in a regular pattern with adjacent edge shapes.

5. The dipole antenna of claim 4, wherein the projected shape of each said butterfly-shaped radiating plate on said conductive floor is a combined shape of a trapezoid and a rectangle, and the length of the side of said rectangle and said trapezoid participating in splicing is equal.

6. The dipole antenna of claim 4, wherein the projection shape of each said butterfly radiating plate on said conductive floor is a sector shape, and the sector angles of a pair of butterfly radiating plates located on the same dipole are the same, and the sum of the sector angles of two pairs of butterfly radiating plates located on different dipoles is less than or equal to 360 °.

7. A dipole antenna as recited in claim 6, wherein the two pairs of bowtie radiating patches on different dipoles have the same radius of curvature.

8. The dipole antenna of claim 5, wherein the number of the plurality of ground studs is even, and the projections of the even number of the plurality of ground studs on the conductive floor are distributed at equal central angles with the center of the conductive floor as the center.

9. The dipole antenna of claim 1 wherein the spacing between adjacent bowtie radiating plate edges increases progressively outwardly along a ray originating at said feed point.

10. A dipole antenna according to claim 1 wherein said plurality of ground posts are all the same height and less than the distance between said radiating element and said conductive ground plane.

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