CN214014106U - Low-cost single-stage power factor correction control circuit and switching power supply - Google Patents
Low-cost single-stage power factor correction control circuit and switching power supply Download PDFInfo
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- CN214014106U CN214014106U CN202022490623.5U CN202022490623U CN214014106U CN 214014106 U CN214014106 U CN 214014106U CN 202022490623 U CN202022490623 U CN 202022490623U CN 214014106 U CN214014106 U CN 214014106U
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- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The utility model discloses a single-stage power factor correction control circuit and switching power supply with low costs, this single-stage power factor correction control circuit with low costs includes electric wire netting input Vin, rectifier bridge DB1, electric capacity C1, electric capacity C2, switch tube S1, switch tube S2, switch tube S3, diode D1, inductance L1, transformer T1, first output rectifier circuit, output electric capacity Co, power factor correction control circuit and resonance control drive circuit. Has the advantages that: the utility model provides a single-stage power factor correction control circuit with low costs, in the input electric wire netting voltage range of broad, realize that the power factor is rectified, reduce the current harmonic distortion, also can restrict and stabilize bus capacitor voltage, avoid the device overstress.
Description
Technical Field
The utility model relates to a circuit and switching power supply field particularly, relate to a control circuit and switching power supply are rectified to single-stage power factor with low costs.
Background
In the field of power supplies, a driving power supply with high power density, high efficiency and low cost is more competitive. Usually, the driving power source selects a resonant circuit to achieve the objectives of high power density and high efficiency. The resonant circuit can realize zero voltage switching-on of two or more switching tubes on the primary side and zero current switching-off of the secondary side rectifier diode, can reduce the switching loss of a power supply, and improves the efficiency and the power density of the power converter. Meanwhile, in order to improve the power factor, a primary active PFC power factor correction circuit is often added at a front stage of the resonant circuit, but this results in a complex circuit and high cost.
Therefore, in the prior art, a charge pump circuit replaces a PFC circuit, so that a single-stage resonant circuit meets the requirement of power factors. However, the resonant circuit having the charge pump has the following problems: when the circuit is under the working condition that the amplitude of the input voltage is changed within a certain range, when the amplitude of the input voltage is increased and the energy required by the resonance main circuit is unchanged, the voltage on the bus capacitor is immediately increased; or, when the output power of the resonant main circuit changes within a certain range (i.e. the power required by the resonant main circuit changes within a certain range), the output power decreases and the input voltage does not change, and the voltage on the bus capacitor increases immediately. If the voltage on the bus capacitor is at a higher amplitude level, the related devices of the later stage resonant main circuit need to bear higher voltage stress. Therefore, when designing the circuit, these devices of the resonant main circuit need to select the withstand voltage performance according to the bus capacitor voltage of the highest magnitude. The devices with high voltage resistance are expensive, and for circuits which work under low-amplitude bus capacitor voltage for a long time and occasionally work under high-amplitude bus capacitor voltage, the devices with high voltage resistance are selected to be too wasteful and must be selected, otherwise, the devices can be damaged due to voltage resistance under the high-amplitude bus capacitor voltage.
Meanwhile, the charge pump PFC is used as a passive measure, so that ideal power factor correction is difficult to realize in a wider input and load range, and the power factor and harmonic effect are not ideal.
In view of this, a technical problem to be solved by those skilled in the art is to stably limit the voltage of the bus capacitor to a certain voltage value, to avoid voltage stress on the device due to the overhigh voltage of the bus capacitor, and to achieve better power factor correction in a wider input and load range.
An effective solution to the problems in the related art has not been proposed yet.
SUMMERY OF THE UTILITY MODEL
To the problem among the correlation technique, the utility model provides a single-stage power factor correction control circuit and switching power supply with low costs to overcome the above-mentioned technical problem that current correlation technique exists.
Therefore, the utility model discloses a specific technical scheme as follows:
according to an aspect of the utility model, a single-stage power factor correction control circuit with low cost is provided, this single-stage power factor correction control circuit with low cost includes electric wire netting input Vin, rectifier bridge DB1, electric capacity C1, electric capacity C2, switch tube S1, switch tube S2, switch tube S3, diode D1, inductance L1, transformer T1, first output rectifier circuit, output electric capacity Co, power factor correction control circuit and resonance control drive circuit;
the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected in parallel to the first output rectifying circuit, the first output rectifying circuit is connected in parallel to the output capacitor Co, the other end of the capacitor C2 is sequentially connected to the first end of the switch tube S3, the negative electrode of the diode D1 and the fourth end of the rectifier bridge DB1, the positive electrode of the diode D1 is sequentially connected to the negative electrode of the capacitor C1, and the first end of the second output rectifying circuit is connected to the output rectifying circuit b1, The second end of the switch tube S3 and the second end of the switch tube S2 are connected and grounded, the third end of the switch tube S3 is connected with the power factor correction control circuit, the third end of the switch tube S2 is connected with the second end of the resonance control driving circuit, and the third end of the switch tube S1 is connected with the first end of the resonance control driving circuit;
the on-time of the switch tube S3 is controlled, so that the voltage of the capacitor C1 can be limited and stabilized; when the inductor current of the L1 flows in the positive half cycle, the conduction time of the switch tube S3 is controlled, the current which is supplied to the capacitor C1 through the rectifier bridge DB1 and the input power grid Vin can be controlled, the longer the conduction time of the switch tube S3 is, the smaller the current which is charged to the capacitor C1 is, and on the contrary, the shorter the conduction time of the switch tube S3 is, the larger the current which is charged to the capacitor C1 is; when the on-time of the switch tube S3 is at a certain value, the charging and discharging currents of the capacitor C1 are equal, and the voltage of the capacitor C1 is at a steady state;
according to the input power grid voltage, the conduction time or the conduction duty ratio of the switch tube S3 is controlled and modulated, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid tracks the input power grid voltage in the power frequency period, and the power factor correction function can be realized.
Further, the capacitor C1 is a polar capacitor.
Further, the output capacitor Co is a polar capacitor.
According to another aspect of the present invention, there is provided a switching power supply comprising the above-described low-cost single-stage power factor correction control circuit.
The utility model has the advantages that:
(1) the utility model provides a single-stage power factor correction control circuit with low costs, in the input electric wire netting voltage range of broad, realize that the power factor is rectified, reduce the current harmonic distortion, also can restrict and stabilize bus capacitor voltage, avoid the device overstress.
(2) The utility model discloses a single-stage power factor correction control circuit with low costs, through control switch S3' S on-time, restriction and the voltage of having stabilized electric capacity C1 prevent the overstress of circuit device. Meanwhile, the current of the input power grid is sampled, and the peak voltage of the capacitor represents the average value of the current through capacitance integration. By adopting a peak value control mode, the input current tracks the input power grid voltage by controlling the conduction time of the switch S3, and the power factor correction function is realized. The utility model discloses a single-stage power factor correction circuit, the circuit is simple, and control is convenient. Compared with a two-stage circuit, the circuit has lower cost. Compared with a passive charge pump PFC, the method can well give consideration to bus capacitance voltage and power factors, and can be suitable for a wider input and output load range.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings required to be used in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to these drawings without creative efforts.
Fig. 1 is a schematic diagram according to a first embodiment of the present invention;
fig. 2 is a voltage waveform diagram according to a first embodiment of the invention;
fig. 3 is a partial schematic view according to a first embodiment of the present invention;
fig. 4 is a schematic diagram according to a second embodiment of the present invention;
fig. 5 is a voltage waveform diagram according to a second embodiment of the present invention;
fig. 6 is a schematic diagram of the power factor correction control circuit of fig. 4.
Detailed Description
For further explanation of the embodiments, the drawings are provided as part of the disclosure and serve primarily to illustrate the embodiments and, together with the description, to explain the principles of operation of the embodiments, and to provide further explanation of the invention and advantages thereof, it will be understood by those skilled in the art that various other embodiments and advantages of the invention are possible, and that elements in the drawings are not to scale and that like reference numerals are generally used to designate like elements.
According to the utility model discloses an embodiment provides a single-stage power factor correction control circuit and switching power supply with low costs.
Example one
Referring now to the drawings and the detailed description, as shown in fig. 1, according to the embodiment of the present invention, a low-cost single-stage power factor correction control circuit includes a power grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switch tube S1, a switch tube S2, a switch tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifier circuit, an output capacitor Co, a power factor correction control circuit, and a resonance control driving circuit;
the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected in parallel to the first output rectifying circuit, the first output rectifying circuit is connected in parallel to the output capacitor Co, the other end of the capacitor C2 is sequentially connected to the first end of the switch tube S3, the negative electrode of the diode D1 and the fourth end of the rectifier bridge DB1, the positive electrode of the diode D1 is sequentially connected to the negative electrode of the capacitor C1, and the first end of the second output rectifying circuit is connected to the output rectifying circuit b1, The second end of the switch tube S3 and the second end of the switch tube S2 are connected to ground, the third end of the switch tube S3 is connected to the power factor correction control circuit, the third end of the switch tube S2 is connected to the second end of the resonance control driving circuit, and the third end of the switch tube S1 is connected to the first end of the resonance control driving circuit.
In one embodiment, for the capacitor C1 described above, the capacitor C1 is a polar capacitor.
In one embodiment, the output capacitor Co is a polar capacitor.
In one embodiment, when the current of the inductor L1 flows from right to left in a negative half cycle, the diode D1 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input grid Vin.
In one embodiment, when the current of the inductor L1 flows from left to right in a positive half cycle, if the switching tube S3 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input grid Vin.
In one embodiment, when the current of the inductor L1 flows from left to right in a positive half cycle, if the switch tube S3 is turned off, the rectifier bridge DB1 is turned on, and the current passes through the input grid Vin.
In one embodiment, the resonant control drive circuit supplies energy to the output capacitor Co and the load through the transformer T1, the first output rectifying circuit.
In one embodiment, the resonant control driving circuit adopts frequency feedback control of output voltage or output current, the control mode of the resonant control driving circuit is similar to that of a general series resonance or series-parallel resonance circuit, the switching tube S1 and the switching tube S2 are symmetrically and complementarily driven, and the set output voltage Vo or output current Io is obtained through frequency control.
The utility model also provides a switching power supply, this switching power supply comprises above-mentioned single-stage power factor correction control circuit with low costs.
In one embodiment, when the switching tube S3 is in a continuous conduction state, the input voltage is input to the grid Vin, the rectifier bridge DB1 and the capacitor C1 to form an uncontrolled rectifier circuit, and no power factor correction function is provided, at this time, the working voltage of the capacitor C1 is the lowest, and the grid current harmonic is also large; when the switch tube S3 is turned off all the time, the positive half-cycle resonant current of the L1 inductor passes through the rectifier bridge DB1 and is input to the grid Vin to charge the capacitor C1. The current flowing through the switch tube S1 is necessarily smaller than the positive half cycle current of the inductor L1, so the charging current is always larger than the discharging current, and the voltage of the capacitor C1 will rise all the time until the device is damaged. As shown in fig. 2 and fig. 3, the voltage of the capacitor C1 can be limited and stabilized by controlling the on-time of the switch tube S3. When the inductor current of the L1 flows in the positive half cycle, the on-time of the switching tube S3 is controlled, so that the current supplied to the capacitor C1 through the rectifier bridge DB1 and the input grid Vin can be controlled, the longer the on-time of the switching tube S3 is, the smaller the current supplied to the capacitor C1 is, and conversely, the shorter the on-time of the switching tube S3 is, the larger the current supplied to the capacitor C1 is. When the on-time of the switch tube S3 is at a certain value, the charging and discharging currents of the capacitor C1 are equal, and the voltage of the capacitor C1 is in a steady state. Therefore, the on-time of the switch tube S3 is controlled to limit and stabilize the voltage of the capacitor C1, thereby avoiding overstressing the circuit device.
In one embodiment, the conduction time or the conduction duty ratio of the switching tube S3 is controlled and modulated according to the input power grid voltage, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid tracks the input power grid voltage in the power frequency period, the power factor correction function can be realized, the input power factor is improved, and the current harmonic wave is reduced.
In one embodiment, the power factor correction control circuit performs feedback control on the voltage of the stable bus capacitor C1 to realize the power factor correction function.
Example two
As shown in fig. 4, according to the embodiment of the present invention, the single-stage power factor correction control circuit with low cost includes a power grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switch tube S1, a switch tube S2, a switch tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectification circuit, an output capacitor Co, a power factor correction control circuit, a resonance control driving circuit, a second output rectification circuit, a current transformer CT1, a capacitor C3, and a switch tube S4;
wherein, the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected to the first output rectifying circuit in parallel, the first output rectifying circuit is connected to the output capacitor Co in parallel, and the other end of the capacitor C2 is sequentially connected to the Vds _ S3 end of the power factor correction control circuit, the first end of the switch tube S3, the negative electrode of the diode D1 and the second input end of the current transformer CT1, the anode of the diode D1 is sequentially connected to the cathode of the capacitor C1, the second end of the switch tube S3 and the second end of the switch tube S2 and grounded, the third end of the switch tube S3 is connected to the Vg _ S3 end of the power factor correction control circuit, the third end of the switch tube S2 is connected to the second end of the resonance control drive circuit, the third end of the switch tube S1 is sequentially connected to the first end of the resonance control drive circuit and the Vg _ S1 end of the power factor correction control circuit, the first input end of the current transformer CT1 is connected to the fourth end of the rectifier bridge DB1, the output end of the current transformer CT1 is connected to the capacitor C3 in parallel, the cathode of the capacitor C3 is connected to the first end of the switch tube S4 and grounded, the anode of the capacitor C3 is sequentially connected to the Vc end of the power factor correction control circuit and the second end of the switch tube S4, the third end of the switch tube S4 is connected with the Vg _ S4 end of the power factor correction control circuit, and the Vin _ rec end of the power factor correction control circuit is connected with the second output rectifying circuit;
wherein the capacitor C3 is a polar capacitor.
In one embodiment, as shown in fig. 4, the input grid current is sampled by the current transformer CT1, and charge integration is performed by the capacitor C3, so that each time the switch S3 is turned on, the switch S4 is turned on to release and reset the voltage across the capacitor C3 to zero. When the capacitance of the capacitor C1 is large enough, it can be approximately considered that the resonant circuit switch operating frequency is substantially the same throughout the power frequency cycle. As can be seen from I × t — C × V, the peak value of the capacitor C3 is proportional to the average current flowing through the input grid during the switching period, and its magnitude represents the average value of the input current during the switching period. The average value of the input current can be modulated and controlled by modulating the conduction duty ratio of the switching tube S3 by adopting peak value comparison control.
In one embodiment, as shown in fig. 6, the voltage control of the bus capacitor C1 is implemented by using an operational amplifier negative feedback circuit, and PI integral control is used as loop compensation;
in one embodiment, as shown in fig. 5 and fig. 6, the negative feedback output Vcomp of the operational amplifier and the steamed bread wave voltage of the input voltage Vin pass through the multiplier to serve as a peak comparison reference of the voltage Vc of the capacitor C3, and when Vc rises to the reference, the switching tube S3 is turned on; the input current is indirectly controlled to follow the input voltage through the charge integration following the peak value control of the input power grid, and the power factor correction is realized.
In one embodiment, when the current of the inductor L1 is converted from positive half cycle to negative half cycle and flows, the switching tube S3 is still in a conducting state, instead of conducting D1, so as to reduce the conducting loss; when the negative half-cycle current flowing through the switch tube S3 gradually decreases to the set comparison value, the switch tube S3 is turned off; when the current is ensured to be conducted in the positive half cycle, the current can flow into the input power grid through the rectifier bridge DB 1.
In one embodiment, when the switch S3 is Mosfet (metal oxide semiconductor field effect transistor), the voltage Vds _ S3 across the switch S3 can be detected to determine the on-state current of the switch S3, and when the voltage Vds increases from a low negative value to a predetermined value Vth, a rising edge is detected to trigger the switch S3 to turn off.
For the convenience of understanding the technical solution of the present invention, the following detailed description is made on the working principle or the operation mode of the present invention in the practical process.
In the actual application of the method, the device is used,
when the switch tube S1 turns on the switch tube S2 and turns off, and the switch tube S3 or the diode D1 turns on, the current passes through the switch tube S1, the inductor L1, the transformer T1, the resonant capacitor C2, the switch tube S3 or the diode D1, and the capacitor C1;
when the switch tube S1 turns off the switch tube S2 and turns on, and the switch tube S3 or the diode D1 turns on, the current passes through the switch tube S2, the inductor L1, the transformer T1, the resonant capacitor C2, the switch tube S3 or the diode D1;
when the switch tube S1 is connected and the switch tube S2 is turned off, and the switch tube S3 and the diode D1 are turned off, current passes through the switch tube S1, the inductor L1, the transformer T1, the resonant capacitor C2, the rectifier bridge DB1 and is input into a power grid Vin;
when the switch tube S1 turns off the switch tube S2 and turns on, and the switch tube S3 and the diode D1 turn off, current flows through the switch tube S1, the inductor L1, the transformer T1, the resonant capacitor C2, the rectifier bridge DB1, and is input to the grid Vin.
To sum up, the utility model provides a single-stage power factor correction control circuit with low costs realizes power factor correction in the input grid voltage range of broad, reduces the current harmonic distortion, also can restrict and stabilize bus capacitor voltage, avoids the device overstress. The utility model discloses a single-stage power factor correction control circuit with low costs, through control switch S3' S on-time, restriction and the voltage of having stabilized electric capacity C1 prevent the overstress of circuit device. Meanwhile, the current of the input power grid is sampled, and the peak voltage of the capacitor represents the average value of the current through capacitance integration. By adopting a peak value control mode, the input current tracks the input power grid voltage by controlling the conduction time of the switch S3, and the power factor correction function is realized. The utility model discloses a single-stage power factor correction circuit, the circuit is simple, and control is convenient. Compared with a two-stage circuit, the circuit has lower cost. Compared with a passive charge pump PFC, the method can well give consideration to bus capacitance voltage and power factors, and can be suitable for a wider input and output load range.
The above description is only a preferred embodiment of the present invention, and should not be taken as limiting the invention, and any modifications, equivalent replacements, improvements, etc. made within the spirit and principle of the present invention should be included in the protection scope of the present invention.
Claims (4)
1. A low-cost single-stage power factor correction control circuit is characterized by comprising a power grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switch tube S1, a switch tube S2, a switch tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectification circuit, an output capacitor Co, a power factor correction control circuit and a resonance control drive circuit;
the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected in parallel to the first output rectifying circuit, the first output rectifying circuit is connected in parallel to the output capacitor Co, the other end of the capacitor C2 is sequentially connected to the first end of the switch tube S3, the negative electrode of the diode D1 and the fourth end of the rectifier bridge DB1, the positive electrode of the diode D1 is sequentially connected to the negative electrode of the capacitor C1, and the first end of the second output rectifying circuit is connected to the output rectifying circuit b1, The second end of the switch tube S3 and the second end of the switch tube S2 are connected and grounded, the third end of the switch tube S3 is connected with the power factor correction control circuit, the third end of the switch tube S2 is connected with the second end of the resonance control driving circuit, and the third end of the switch tube S1 is connected with the first end of the resonance control driving circuit;
the on-time of the switch tube S3 is controlled, so that the voltage of the capacitor C1 can be limited and stabilized; according to the input power grid voltage, the conduction time or the conduction duty ratio of the switch tube S3 is controlled and modulated, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid tracks the input power grid voltage in the power frequency period, and the power factor correction function can be realized.
2. The low cost single stage pfc control circuit of claim 1, wherein the capacitor C1 is a polar capacitor.
3. The low cost single stage power factor correction control circuit of claim 1, wherein said output capacitor Co is a polar capacitor.
4. A switching power supply comprising the low cost single stage power factor correction control circuit of any of claims 1-3.
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| CN202022490623.5U CN214014106U (en) | 2020-11-02 | 2020-11-02 | Low-cost single-stage power factor correction control circuit and switching power supply |
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| CN202022490623.5U CN214014106U (en) | 2020-11-02 | 2020-11-02 | Low-cost single-stage power factor correction control circuit and switching power supply |
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116404863A (en) * | 2023-06-07 | 2023-07-07 | 杰华特微电子股份有限公司 | Power factor correction converter |
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Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN116404863A (en) * | 2023-06-07 | 2023-07-07 | 杰华特微电子股份有限公司 | Power factor correction converter |
| CN116404863B (en) * | 2023-06-07 | 2023-09-22 | 杰华特微电子股份有限公司 | Power factor correction converter |
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Address after: 237300 Standardized Workshop B-8 of Jinwutong Pioneer Park, Jinzhai Modern Industrial Park, Luan City, Anhui Province Patentee after: Anhui Letu Electronic Technology Co.,Ltd. Address before: 237300 Standardized Workshop B-8 of Jinwutong Pioneer Park, Jinzhai Modern Industrial Park, Luan City, Anhui Province Patentee before: Anhui Letu Electronic Technology Co.,Ltd. |