CN112366934A - Single-stage power factor correction control circuit and switching power supply - Google Patents

Single-stage power factor correction control circuit and switching power supply Download PDF

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Publication number
CN112366934A
CN112366934A CN202011204597.3A CN202011204597A CN112366934A CN 112366934 A CN112366934 A CN 112366934A CN 202011204597 A CN202011204597 A CN 202011204597A CN 112366934 A CN112366934 A CN 112366934A
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China
Prior art keywords
capacitor
switch tube
factor correction
current
control circuit
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CN202011204597.3A
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Chinese (zh)
Inventor
宋祖梅
陈圣伦
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Anhui Letu Electronic Technology Co ltd
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Anhui Letu Electronic Technology Co ltd
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Priority to CN202011204597.3A priority Critical patent/CN112366934A/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/4815—Resonant converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention discloses a single-stage power factor correction control circuit and a switching power supply, wherein the single-stage power factor correction control circuit comprises a power grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switching tube S1, a switching tube S2, a switching tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifying circuit, an output capacitor Co, a power factor correction control circuit and a resonance control drive circuit. Has the advantages that: the invention provides a single-stage power factor correction control circuit, which can realize power factor correction, reduce current harmonic distortion, limit and stabilize bus capacitor voltage and avoid overstress of devices in a wider input power grid voltage range.

Description

Single-stage power factor correction control circuit and switching power supply
Technical Field
The invention relates to the field of circuits and switching power supplies, in particular to a single-stage power factor correction control circuit and a switching power supply.
Background
In the field of power supplies, a driving power supply with high power density, high efficiency and low cost is more competitive. Usually, the driving power source selects a resonant circuit to achieve the objectives of high power density and high efficiency. The resonant circuit can realize zero voltage switching-on of two or more switching tubes on the primary side and zero current switching-off of the secondary side rectifier diode, can reduce the switching loss of a power supply, and improves the efficiency and the power density of the power converter. Meanwhile, in order to improve the power factor, a primary active PFC power factor correction circuit is often added at a front stage of the resonant circuit, but this results in a complex circuit and high cost.
Therefore, in the prior art, a charge pump circuit replaces a PFC circuit, so that a single-stage resonant circuit meets the requirement of power factors. However, the resonant circuit having the charge pump has the following problems: when the circuit is under the working condition that the amplitude of the input voltage is changed within a certain range, when the amplitude of the input voltage is increased and the energy required by the resonance main circuit is unchanged, the voltage on the bus capacitor is immediately increased; or, when the output power of the resonant main circuit changes within a certain range (i.e. the power required by the resonant main circuit changes within a certain range), the output power decreases and the input voltage does not change, and the voltage on the bus capacitor increases immediately. If the voltage on the bus capacitor is at a higher amplitude level, the related devices of the later stage resonant main circuit need to bear higher voltage stress. Therefore, when designing the circuit, these devices of the resonant main circuit need to select the withstand voltage performance according to the bus capacitor voltage of the highest magnitude. The devices with high voltage resistance are expensive, and for circuits which work under low-amplitude bus capacitor voltage for a long time and occasionally work under high-amplitude bus capacitor voltage, the devices with high voltage resistance are selected to be too wasteful and must be selected, otherwise, the devices can be damaged due to voltage resistance under the high-amplitude bus capacitor voltage.
Meanwhile, the charge pump PFC is used as a passive measure, so that ideal power factor correction is difficult to realize in a wider input and load range, and the power factor and harmonic effect are not ideal.
In view of this, a technical problem to be solved by those skilled in the art is to stably limit the voltage of the bus capacitor to a certain voltage value, to avoid voltage stress on the device due to the overhigh voltage of the bus capacitor, and to achieve better power factor correction in a wider input and load range.
An effective solution to the problems in the related art has not been proposed yet.
Disclosure of Invention
The present invention provides a single-stage power factor correction control circuit and a switching power supply, which are directed to the problems in the related art, so as to overcome the technical problems in the related art.
Therefore, the invention adopts the following specific technical scheme:
according to an aspect of the present invention, there is provided a single-stage power factor correction control circuit, including a grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switching tube S1, a switching tube S2, a switching tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifying circuit, an output capacitor Co, a power factor correction control circuit, and a resonance control driving circuit;
the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected in parallel to the first output rectifying circuit, the first output rectifying circuit is connected in parallel to the output capacitor Co, the other end of the capacitor C2 is sequentially connected to the first end of the switch tube S3, the negative electrode of the diode D1 and the fourth end of the rectifier bridge DB1, the positive electrode of the diode D1 is sequentially connected to the negative electrode of the capacitor C1, and the, The second end of the switch tube S3 and the second end of the switch tube S2 are connected and grounded, the third end of the switch tube S3 is connected with the power factor correction control circuit, the third end of the switch tube S2 is connected with the second end of the resonance control driving circuit, and the third end of the switch tube S1 is connected with the first end of the resonance control driving circuit;
the on-time of the switch tube S3 is controlled, so that the voltage of the capacitor C1 can be limited and stabilized; when the inductor current of the L1 flows in the positive half cycle, the conduction time of the switch tube S3 is controlled, the current which is supplied to the capacitor C1 through the rectifier bridge DB1 and the input power grid Vin can be controlled, the longer the conduction time of the switch tube S3 is, the smaller the current which is charged to the capacitor C1 is, and on the contrary, the shorter the conduction time of the switch tube S3 is, the larger the current which is charged to the capacitor C1 is; when the on-time of the switch tube S3 is at a certain value, the charging and discharging currents of the capacitor C1 are equal, and the voltage of the capacitor C1 is at a steady state;
according to the input power grid voltage, the conduction time or the conduction duty ratio of the switch tube S3 is controlled and modulated, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid tracks the input power grid voltage in the power frequency period, and the power factor correction function can be realized.
Further, the capacitor C1 is a polar capacitor.
Further, the output capacitor Co is a polar capacitor.
Further, when the current of the inductor L1 flows from right to left in the negative half cycle, the diode D1 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input grid Vin.
Further, when the current of the inductor L1 flows from left to right in a positive half cycle, if the switching tube S3 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input grid Vin.
Further, when the current of the inductor L1 flows from left to right in a positive half cycle, if the switching tube S3 is turned off, the rectifier bridge DB1 is turned on, and the current passes through the input grid Vin.
Further, the resonance control driving circuit supplies energy to the output capacitor Co and the load through the transformer T1 and the first output rectifying circuit.
Further, the resonance control driving circuit adopts frequency feedback control of output voltage or output current.
According to another aspect of the present invention, there is provided a switching power supply comprising the single-stage power factor correction control circuit described above.
The invention has the beneficial effects that:
(1) the invention provides a single-stage power factor correction control circuit, which can realize power factor correction, reduce current harmonic distortion, limit and stabilize bus capacitor voltage and avoid overstress of devices in a wider input power grid voltage range.
(2) The single-stage power factor correction control circuit limits and stabilizes the voltage of the capacitor C1 by controlling the conduction time of the switch S3, thereby preventing the overstress of circuit devices. Meanwhile, the current of the input power grid is sampled, and the peak voltage of the capacitor represents the average value of the current through capacitance integration. By adopting a peak value control mode, the input current tracks the input power grid voltage by controlling the conduction time of the switch S3, and the power factor correction function is realized. The single-stage power factor correction circuit is simple in circuit and convenient to control. Compared with a two-stage circuit, the circuit has lower cost. Compared with a passive charge pump PFC, the method can well give consideration to bus capacitance voltage and power factors, and can be suitable for a wider input and output load range.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings needed in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and it is obvious for those skilled in the art to obtain other drawings without creative efforts.
FIG. 1 is a schematic diagram of a first embodiment of the present invention;
FIG. 2 is a voltage waveform diagram according to a first embodiment of the invention;
FIG. 3 is a partial schematic view of a first embodiment of the invention;
FIG. 4 is a schematic diagram according to a second embodiment of the present invention;
FIG. 5 is a graph of voltage waveforms according to the second embodiment of the present invention;
fig. 6 is a schematic diagram of the power factor correction control circuit of fig. 4.
Detailed Description
For further explanation of the various embodiments, the drawings which form a part of the disclosure and which are incorporated in and constitute a part of this specification, illustrate embodiments and, together with the description, serve to explain the principles of operation of the embodiments, and to enable others of ordinary skill in the art to understand the various embodiments and advantages of the invention, and, by reference to these figures, reference is made to the accompanying drawings, which are not to scale and wherein like reference numerals generally refer to like elements.
According to the embodiment of the invention, a single-stage power factor correction control circuit and a switching power supply are provided.
Example one
Referring to the drawings and the detailed description, as shown in fig. 1, the single-stage power factor correction control circuit according to the embodiment of the present invention includes a grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switching tube S1, a switching tube S2, a switching tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifier circuit, an output capacitor Co, a power factor correction control circuit, and a resonance control driving circuit;
the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected in parallel to the first output rectifying circuit, the first output rectifying circuit is connected in parallel to the output capacitor Co, the other end of the capacitor C2 is sequentially connected to the first end of the switch tube S3, the negative electrode of the diode D1 and the fourth end of the rectifier bridge DB1, the positive electrode of the diode D1 is sequentially connected to the negative electrode of the capacitor C1, and the, The second end of the switch tube S3 and the second end of the switch tube S2 are connected to ground, the third end of the switch tube S3 is connected to the power factor correction control circuit, the third end of the switch tube S2 is connected to the second end of the resonance control driving circuit, and the third end of the switch tube S1 is connected to the first end of the resonance control driving circuit.
In one embodiment, for the capacitor C1 described above, the capacitor C1 is a polar capacitor.
In one embodiment, the output capacitor Co is a polar capacitor.
In one embodiment, when the current of the inductor L1 flows from right to left in a negative half cycle, the diode D1 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input grid Vin.
In one embodiment, when the current of the inductor L1 flows from left to right in a positive half cycle, if the switching tube S3 is turned on, the rectifier bridge DB1 is turned off, and the current does not pass through the input grid Vin.
In one embodiment, when the current of the inductor L1 flows from left to right in a positive half cycle, if the switch tube S3 is turned off, the rectifier bridge DB1 is turned on, and the current passes through the input grid Vin.
In one embodiment, the resonant control drive circuit supplies energy to the output capacitor Co and the load through the transformer T1, the first output rectifying circuit.
In one embodiment, the resonant control driving circuit adopts frequency feedback control of output voltage or output current, the control mode of the resonant control driving circuit is similar to that of a general series resonance or series-parallel resonance circuit, the switching tube S1 and the switching tube S2 are symmetrically and complementarily driven, and the set output voltage Vo or output current Io is obtained through frequency control.
The invention also provides a switching power supply which consists of the single-stage power factor correction control circuit.
In one embodiment, when the switching tube S3 is in a continuous conduction state, the input voltage is input to the grid Vin, the rectifier bridge DB1 and the capacitor C1 to form an uncontrolled rectifier circuit, and no power factor correction function is provided, at this time, the working voltage of the capacitor C1 is the lowest, and the grid current harmonic is also large; when the switch tube S3 is turned off all the time, the positive half-cycle resonant current of the L1 inductor passes through the rectifier bridge DB1 and is input to the grid Vin to charge the capacitor C1. The current flowing through the switch tube S1 is necessarily smaller than the positive half cycle current of the inductor L1, so the charging current is always larger than the discharging current, and the voltage of the capacitor C1 will rise all the time until the device is damaged. As shown in fig. 2 and fig. 3, the voltage of the capacitor C1 can be limited and stabilized by controlling the on-time of the switch tube S3. When the inductor current of the L1 flows in the positive half cycle, the on-time of the switching tube S3 is controlled, so that the current supplied to the capacitor C1 through the rectifier bridge DB1 and the input grid Vin can be controlled, the longer the on-time of the switching tube S3 is, the smaller the current supplied to the capacitor C1 is, and conversely, the shorter the on-time of the switching tube S3 is, the larger the current supplied to the capacitor C1 is. When the on-time of the switch tube S3 is at a certain value, the charging and discharging currents of the capacitor C1 are equal, and the voltage of the capacitor C1 is in a steady state. Therefore, the on-time of the switch tube S3 is controlled to limit and stabilize the voltage of the capacitor C1, thereby avoiding overstressing the circuit device.
In one embodiment, the conduction time or the conduction duty ratio of the switching tube S3 is controlled and modulated according to the input power grid voltage, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid tracks the input power grid voltage in the power frequency period, the power factor correction function can be realized, the input power factor is improved, and the current harmonic wave is reduced.
In one embodiment, the power factor correction control circuit realizes the power factor correction function by feedback control of the voltage of the stable bus capacitor C1.
Example two
As shown in fig. 4, the single-stage power factor correction control circuit according to the embodiment of the present invention includes a grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switch tube S1, a switch tube S2, a switch tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifying circuit, an output capacitor Co, a power factor correction control circuit, a resonance control driving circuit, a second output rectifying circuit, a current transformer CT1, a capacitor C3, and a switch tube S4;
wherein, the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected to the first output rectifying circuit in parallel, the first output rectifying circuit is connected to the output capacitor Co in parallel, and the other end of the capacitor C2 is sequentially connected to the Vds _ S3 end of the power factor correction control circuit, the first end of the switch tube S3, the negative electrode of the diode D1 and the second input end of the current transformer CT1, the anode of the diode D1 is sequentially connected to the cathode of the capacitor C1, the second end of the switch tube S3 and the second end of the switch tube S2 and grounded, the third end of the switch tube S3 is connected to the Vg _ S3 end of the power factor correction control circuit, the third end of the switch tube S2 is connected to the second end of the resonance control drive circuit, the third end of the switch tube S1 is sequentially connected to the first end of the resonance control drive circuit and the Vg _ S1 end of the power factor correction control circuit, the first input end of the current transformer CT1 is connected to the fourth end of the rectifier bridge DB1, the output end of the current transformer CT1 is connected to the capacitor C3 in parallel, the cathode of the capacitor C3 is connected to the first end of the switch tube S4 and grounded, the anode of the capacitor C3 is sequentially connected to the Vc end of the power factor correction control circuit and the second end of the switch tube S4, the third end of the switch tube S4 is connected with the Vg _ S4 end of the power factor correction control circuit, and the Vin _ rec end of the power factor correction control circuit is connected with the second output rectifying circuit;
wherein the capacitor C3 is a polar capacitor.
In one embodiment, as shown in fig. 4, the input grid current is sampled by the current transformer CT1, and charge integration is performed by the capacitor C3, so that each time the switch S3 is turned on, the switch S4 is turned on to release and reset the voltage across the capacitor C3 to zero. When the capacitance of the capacitor C1 is large enough, it can be approximately considered that the resonant circuit switch operating frequency is substantially the same throughout the power frequency cycle. As can be seen from I × t — C × V, the peak value of the capacitor C3 is proportional to the average current flowing through the input grid during the switching period, and its magnitude represents the average value of the input current during the switching period. The average value of the input current can be modulated and controlled by modulating the conduction duty ratio of the switching tube S3 by adopting peak value comparison control.
In one embodiment, as shown in fig. 6, the voltage control of the bus capacitor C1 is implemented by using an operational amplifier negative feedback circuit, and PI integral control is used as loop compensation;
in one embodiment, as shown in fig. 5 and fig. 6, the negative feedback output Vcomp of the operational amplifier and the steamed bread wave voltage of the input voltage Vin pass through the multiplier to serve as a peak comparison reference of the voltage Vc of the capacitor C3, and when Vc rises to the reference, the switching tube S3 is turned on; the input current is indirectly controlled to follow the input voltage through the peak value control of the charge integration following input power grid, and the power factor correction is realized.
In one embodiment, when the current of the inductor L1 is converted from positive half cycle to negative half cycle and flows, the switching tube S3 is still in a conducting state, instead of conducting D1, so as to reduce the conducting loss; when the negative half-cycle current flowing through the switch tube S3 gradually decreases to the set comparison value, the switch tube S3 is turned off; when the current is ensured to be conducted in the positive half cycle, the current can flow into the input power grid through the rectifier bridge DB 1.
In one embodiment, when the switch S3 is Mosfet (metal oxide semiconductor field effect transistor), the voltage Vds _ S3 across the switch S3 can be detected to determine the on-state current of the switch S3, and when the voltage Vds increases from a low negative value to a predetermined value Vth, a rising edge is detected to trigger the switch S3 to turn off.
For the convenience of understanding the technical solutions of the present invention, the following detailed description will be made on the working principle or the operation mode of the present invention in the practical process.
In the actual application of the method, the device is used,
when the switch tube S1 turns on the switch tube S2 and turns off, and the switch tube S3 or the diode D1 turns on, the current passes through the switch tube S1, the inductor L1, the transformer T1, the resonant capacitor C2, the switch tube S3 or the diode D1, and the capacitor C1;
when the switch tube S1 turns off the switch tube S2 and turns on, and the switch tube S3 or the diode D1 turns on, the current passes through the switch tube S2, the inductor L1, the transformer T1, the resonant capacitor C2, the switch tube S3 or the diode D1;
when the switch tube S1 is connected and the switch tube S2 is turned off, and the switch tube S3 and the diode D1 are turned off, current passes through the switch tube S1, the inductor L1, the transformer T1, the resonant capacitor C2, the rectifier bridge DB1 and is input into a power grid Vin;
when the switch tube S1 turns off the switch tube S2 and turns on, and the switch tube S3 and the diode D1 turn off, current flows through the switch tube S1, the inductor L1, the transformer T1, the resonant capacitor C2, the rectifier bridge DB1, and is input to the grid Vin.
In summary, the present invention provides a single-stage power factor correction control circuit, which can achieve power factor correction in a wider input power grid voltage range, reduce current harmonic distortion, limit and stabilize bus capacitor voltage, and avoid device overstress. The single-stage power factor correction control circuit limits and stabilizes the voltage of the capacitor C1 by controlling the conduction time of the switch S3, thereby preventing the overstress of circuit devices. Meanwhile, the current of the input power grid is sampled, and the peak voltage of the capacitor represents the average value of the current through capacitance integration. By adopting a peak value control mode, the input current tracks the input power grid voltage by controlling the conduction time of the switch S3, and the power factor correction function is realized. The single-stage power factor correction circuit is simple in circuit and convenient to control. Compared with a two-stage circuit, the circuit has lower cost. Compared with a passive charge pump PFC, the method can well give consideration to bus capacitance voltage and power factors, and can be suitable for a wider input and output load range.
The above description is only for the purpose of illustrating the preferred embodiments of the present invention and is not to be construed as limiting the invention, and any modifications, equivalents, improvements and the like that fall within the spirit and principle of the present invention are intended to be included therein.

Claims (9)

1. A single-stage power factor correction control circuit is characterized by comprising a power grid input Vin, a rectifier bridge DB1, a capacitor C1, a capacitor C2, a switch tube S1, a switch tube S2, a switch tube S3, a diode D1, an inductor L1, a transformer T1, a first output rectifying circuit, an output capacitor Co, a power factor correction control circuit and a resonance control drive circuit;
the grid input Vin is connected to the first end and the third end of the rectifier bridge DB1, the second end of the rectifier bridge DB1 is sequentially connected to the positive electrode of the capacitor C1 and the first end of the switch tube S1, the second end of the switch tube S1 is sequentially connected to one end of the inductor L1 and the first end of the switch tube S2, the other end of the inductor L1 is connected to the first input end of the transformer T1, the second input end of the transformer T1 is connected to one end of the capacitor C2, the output end of the transformer T1 is connected in parallel to the first output rectifying circuit, the first output rectifying circuit is connected in parallel to the output capacitor Co, the other end of the capacitor C2 is sequentially connected to the first end of the switch tube S3, the negative electrode of the diode D1 and the fourth end of the rectifier bridge DB1, the positive electrode of the diode D1 is sequentially connected to the negative electrode of the capacitor C1, and the, The second end of the switch tube S3 and the second end of the switch tube S2 are connected and grounded, the third end of the switch tube S3 is connected with the power factor correction control circuit, the third end of the switch tube S2 is connected with the second end of the resonance control driving circuit, and the third end of the switch tube S1 is connected with the first end of the resonance control driving circuit;
the on-time of the switch tube S3 is controlled, so that the voltage of the capacitor C1 can be limited and stabilized; when the inductor current of the L1 flows in the positive half cycle, the conduction time of the switch tube S3 is controlled, the current which is supplied to the capacitor C1 through the rectifier bridge DB1 and the input power grid Vin can be controlled, the longer the conduction time of the switch tube S3 is, the smaller the current which is charged to the capacitor C1 is, and on the contrary, the shorter the conduction time of the switch tube S3 is, the larger the current which is charged to the capacitor C1 is; when the on-time of the switch tube S3 is at a certain value, the charging and discharging currents of the capacitor C1 are equal, and the voltage of the capacitor C1 is at a steady state;
according to the input power grid voltage, the conduction time or the conduction duty ratio of the switch tube S3 is controlled and modulated, so that the average value of the current flowing through the rectifier bridge DB1 and the power grid tracks the input power grid voltage in the power frequency period, and the power factor correction function can be realized.
2. The single stage pfc control circuit of claim 1, wherein the capacitor C1 is a polar capacitor.
3. The single-stage power factor correction control circuit of claim 1, wherein the output capacitor Co is a polar capacitor.
4. The single-stage PFC control circuit of claim 1, wherein when the current in inductor L1 flows from right to left for a negative half cycle, diode D1 is turned on, rectifier bridge DB1 is turned off, and current does not pass through the input grid Vin.
5. The single-stage PFC control circuit of claim 1, wherein when the inductor L1 is conducting from left to right for a positive half cycle, if the switch S3 is conducting, the bridge DB1 is blocking and current does not pass through the input grid Vin.
6. The single-stage PFC control circuit of claim 1, wherein when the inductor L1 is conducting current from left to right for a positive half cycle, if the switch S3 is turned off, the rectifier bridge DB1 is conducting and current is passed through the input grid Vin.
7. The single-stage power factor correction control circuit of claim 1, wherein the resonant control driving circuit supplies energy to the output capacitor Co and the load through a transformer T1 and a first output rectifying circuit.
8. The single stage power factor correction control circuit of claim 1, wherein the resonant control drive circuit employs frequency feedback control of the output voltage or output current.
9. A switching power supply comprising the single stage power factor correction control circuit of any of claims 1-8.
CN202011204597.3A 2020-11-02 2020-11-02 Single-stage power factor correction control circuit and switching power supply Pending CN112366934A (en)

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CN202011204597.3A CN112366934A (en) 2020-11-02 2020-11-02 Single-stage power factor correction control circuit and switching power supply

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Application Number Priority Date Filing Date Title
CN202011204597.3A CN112366934A (en) 2020-11-02 2020-11-02 Single-stage power factor correction control circuit and switching power supply

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023246061A1 (en) * 2022-06-20 2023-12-28 Oppo广东移动通信有限公司 Transformer circuit, voltage conversion circuit, electronic device, and circuit starting method

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023246061A1 (en) * 2022-06-20 2023-12-28 Oppo广东移动通信有限公司 Transformer circuit, voltage conversion circuit, electronic device, and circuit starting method

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