CN210182584U - Beam forming antenna structure - Google Patents
Beam forming antenna structure Download PDFInfo
- Publication number
- CN210182584U CN210182584U CN201921456131.5U CN201921456131U CN210182584U CN 210182584 U CN210182584 U CN 210182584U CN 201921456131 U CN201921456131 U CN 201921456131U CN 210182584 U CN210182584 U CN 210182584U
- Authority
- CN
- China
- Prior art keywords
- integrated waveguide
- substrate integrated
- metal layer
- antenna
- substrate
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Images
Landscapes
- Variable-Direction Aerials And Aerial Arrays (AREA)
Abstract
The utility model discloses a novel beam forming antenna structure, wherein antenna structure includes linear array radiating element and feed network. The feed network is composed of a plurality of substrate integrated waveguide power distributors with symmetrical structures and substrate integrated waveguide delay lines, and the linear array radiation unit is connected with the tail end of the substrate integrated waveguide feed network. The utility model discloses the antenna has realized a novel cosecant quadra antenna array suitable for millimeter wave synthetic aperture radar. Under the condition of the same radar scattering cross section, the antenna can achieve the purpose that the received echo powers of targets with different distances in the target view field are equal, and therefore the utilization efficiency of energy is improved. Meanwhile, the feed network consists of symmetrical equal-power distributors, and has the advantages of simple design, high reliability, high tolerance on processing errors and the like.
Description
Technical Field
The utility model relates to a field such as electron, microwave radio frequency, radar especially relate to a novel beam forming antenna's structure and design method.
Background
With the continuous development of science and technology, the millimeter wave technology has the excellent characteristics of small size, large bandwidth and the like, and is concerned by various research institutions at home and abroad. The millimeter wave antenna array as a key component of a millimeter wave radar and a communication system has very important influence on the link index performance of the whole system.
Such an application scenario often occurs in the field of communications: the transmitting terminal is placed at a high position and needs to obliquely downwards cover a receiving user in a certain angle area. Since higher Equivalent Isotropic Radiated Power (EIRP) is required to detect more distant targets, it is impractical to increase the transmit power in a trivial way, so the more distant the detection distance, the higher the required antenna array gain. In order to improve the energy utilization efficiency, the former shapes the beam. The antenna array has lower gain at a position with a close distance and higher gain at a position with a far distance. Therefore, the receiving ends at different positions on the ground can receive the same energy. Since this is a one-way communication, the received power is inversely proportional to the square of the distance. Therefore, the designed antenna is called a cosecant square antenna.
The existing cosecant square antenna schemes generally have the following: 1) adopting a lens/reflective array structure, and realizing corresponding phase shift by utilizing the phase shift effect of different units on the lens/reflective array so as to realize a cosecant directional diagram; 2) the cosecant square radiation directional diagram is realized by designing a complex feed network to feed different linear arrays of the planar antenna array.
Disadvantages of the prior art
From the concept of an antenna directional diagram, the existing cosecant square antenna concept is only suitable for communication of unidirectional transmission and a two-station radar application scene (namely, a transmitting end is located in the air, and a receiving end is located on the ground), but is not suitable for a single-station radar application scene (both the transmitting end and the receiving end are in the air) such as a synthetic aperture radar.
In a unidirectional scene, a signal is transmitted from a transmitting end in the air to a receiving end on the ground, the signal path is unidirectional, and therefore the receiving power is inversely proportional to the square of the distance. For a synthetic aperture radar scene, signals are transmitted from an air transmitting end, hit to the ground, are reflected and then are received by an air receiving end. The signal path is therefore bi-directional, with the received power inversely proportional to the fourth power of the distance, for which conventional cosecant squared antennas are not suitable.
From the technical realization of beam forming antenna, the antenna designed by using the lens/reflective array in the first scheme is heavy, high in structural section and large in size, and is difficult to integrate with a planar circuit. In the second scheme, in order to realize a special directional diagram, the power distribution ratio of each port is not regular, a feed network of the second scheme often uses a large number of asymmetric structures, the design is very complex, the tolerance of the asymmetric structures to processing errors is low, and the difference between a processed antenna test result and a simulation result is large.
In summary, at present, no antenna can support the cosut forming application of the millimeter wave synthetic aperture radar, and simultaneously, the characteristics of low profile, easy integration with a planar circuit, simple processing of a feed network, high reliability and the like are met.
Disclosure of Invention
The utility model discloses the technical problem that will solve is: the proposed beamforming concept can meet the cosecant beamforming requirements for synthetic aperture radar applications. Under the condition of the same radar scattering cross section, the received echo powers of targets with different distances in the target view field can be approximately equal, so that the utilization efficiency of transmitted energy is effectively improved
In order to solve the technical problem, the utility model discloses a technical scheme is:
a beamforming antenna structure, characterized by: skyThe horizontal plane directional diagram of the linear array meets the requirement of a cosecant quartic formula within a radar target view field angle, namely:
θ∈[-0.5θ1,0.5θ1]wherein theta0For residual cutting of the starting angle of the covered area, theta1Angular range, θ, to be covered by the radar2Is the included angle between the central line of the coverage area and the horizontal direction.
A beam-forming antenna array structure comprises a linear array radiation unit and a substrate integrated waveguide feed network, wherein the substrate integrated waveguide feed network comprises a path-division multi-path substrate integrated waveguide power divider and a substrate integrated waveguide delay line, and each output end of the feed network is connected with the input end of the linear array radiation unit.
The substrate integrated waveguide power divider is of a structure that one path is divided into twelve paths, and the output end of each path is connected with the input end of a substrate integrated waveguide delay line.
The structure of dividing one path into twelve paths is formed by mutually combining five substrate integrated waveguide equal-power distributors with symmetrical structures.
The power distribution structure with one path divided into twelve paths is composed of five-level symmetrical substrate integrated waveguide equal power distributors. Different output ports pass through different stages of the equal power divider, so that different power division ratios are realized. And the output ports of the twelve-channel substrate integrated waveguide channels are finally kept flush.
The beam forming antenna array adopts a multilayer printed circuit board process, and comprises the following steps from top to bottom: the device comprises a top metal layer, a top dielectric substrate, a first middle metal layer, a pasting dielectric layer, a second middle metal layer, a bottom dielectric substrate and a bottom metal layer.
One half of the substrate integrated waveguide delay line structure is arranged on the bottom layer medium substrate, the other half of the substrate integrated waveguide delay line structure is arranged on the top layer medium substrate, and the middle of the substrate integrated waveguide delay line structure is connected through a gap coupling structure between different layers. The positions of the output ports of the substrate integrated waveguide delay line on the top dielectric substrate are flush with each other.
The linear array radiating unit adopts a series feed microstrip patch antenna mode, and every two linear arrays are arranged at equal intervals.
A design method of an antenna structure with a cosecant quadrivalent radiation directional diagram specifically comprises the following steps:
the method comprises the following steps: the linear array radiation unit structure is determined by the actually required vertical plane beam width, and relevant structural parameters of the series-fed microstrip linear array radiation unit are adjusted according to the reflection coefficient performance requirement;
step two: determining the number of linear array radiation units arranged in the horizontal direction according to the requirements of a cosecant quadrivalent antenna target directional diagram on antenna gain and the horizontal plane detection range;
step three: determining the distance between every two linear arrays and the amplitude and phase of excitation of each linear array port according to a preset cosecant quadrivalent antenna target directional diagram; the horizontal plane directional diagram of the antenna array meets the requirement of a cosecant quartic formula within the radar target view field angle, namely:
θ∈[-0.5θ1,0.5θ1]wherein theta0For residual cutting of the starting angle of the covered area, theta1Angular range, θ, to be covered by the radar2Is the included angle between the central line of the coverage area and the horizontal direction.
Step four: designing an integrated substrate integrated waveguide feed network according to the distance between different radiation units designed in the third step and the feed amplitude of each path, and meeting the requirement of a reflection coefficient;
step five: and calculating the phase of each path needing extra delay according to the phase requirement needed by each port and the phase output by each port of the step four middle feeding network. Different lengths of the substrate integrated waveguide delay line are designed to meet the phase requirements of each port. And simultaneously, designing a gap coupling feed structure between different layers to be used for connecting delay lines between different dielectric layers. One half of the substrate integrated waveguide delay line is arranged on a bottom medium substrate, the other half of the substrate integrated waveguide delay line is arranged on a top medium substrate, and the middle of the substrate integrated waveguide delay line is connected through a gap coupling structure between different layers. The positions of the output ports of the substrate integrated waveguide delay line on the top dielectric substrate are flush with each other.
Step six: and combining the series feed microstrip linear array radiating unit designed in the step one, the substrate integrated waveguide antenna feed network designed in the step four and the substrate integrated waveguide delay line designed in the step five together to form a complete antenna array.
Compared with the prior art, the beneficial effects of the utility model are that:
1. the utility model provides an antenna structure can support millimeter wave synthetic aperture radar's surplus cutting figurative demand. Under the condition of the same target radar scattering cross section, the cosecant quadrifilar antenna can achieve the purpose that the return echo powers of targets at different angle positions in a field of view are equal.
2. The power distribution ratio of the output port of the one-path twelve-path power divider of the feed network part of the utility model is an integer power distribution of two, namely 1:1:1:2:2:8:8:2:2:2:2, and the power distribution ratio can be just formed by a 5-level equipower symmetrical structure with the power distribution ratio of 1:1, so that the design is simpler and more convenient, and meanwhile, due to the symmetrical structure, under the same processing error, the influence of the symmetrical structure is smaller than that of an asymmetrical structure, so that the tolerance to the processing error is higher.
3. Firstly, the feed network needs to occupy a certain layout area and a layer of medium. The utility model discloses place most structures of feed network on the metal level of bottom medium promptly substrate integrated waveguide function distributor, make the radiating element part of substrate integrated waveguide function distributor and antenna be located the medium of difference, avoided conflicting with antenna part. Because the radiating unit of the antenna and the substrate integrated waveguide function distributor are not in the same dielectric layer, and the radiating unit and the substrate integrated waveguide function distributor can occupy the same space, the total layout area can be saved, and the antenna array is more compact.
Drawings
Fig. 1 is a schematic diagram of a multi-layer circuit structure hierarchy of an antenna array according to the present invention;
fig. 2 is a schematic diagram of a top metal layer structure of an antenna array according to the present invention;
fig. 3 is a schematic diagram of a first intermediate metal layer structure of an antenna array according to the present invention;
fig. 4 is a schematic diagram of a second intermediate metal layer structure of the antenna array according to the present invention;
fig. 5 is a schematic structural view of a bottom metal layer of the antenna array according to the present invention;
fig. 6 shows simulation and test results of the antenna array reflection coefficient performance of the present invention;
fig. 7 is a diagram of antenna array horizontal plane pattern (H-plane) simulation and test results according to the present invention;
fig. 8 is a graph of antenna array tilted vertical plane pattern (tilted E-plane) simulation and test results according to the present invention;
fig. 9 shows simulation and test results of the present invention relating to antenna array gain;
fig. 10 is a schematic view of an application scenario of the antenna array according to the present invention.
Detailed Description
The invention is described in further detail below with reference to the accompanying drawings:
as shown in fig. 1, the antenna array structure of the present invention includes four layers of circuits, including a top metal layer 1, a first middle metal layer 2, a second middle metal layer 3 and a bottom metal layer 4. The dielectric aspect has two dielectric substrates (top dielectric layer 5 and bottom dielectric layer 7 and paste layer 6. the metal layer, dielectric substrate, and paste layer are represented by grey, white, and shading, respectively, and signals between different layers are coupled through apertures 8 between layers.
Fig. 2 shows the structure of the top metal layer 1 of the antenna of the present invention, which mainly comprises a series-fed microstrip line array radiating element 9, a substrate integrated waveguide delay line 10(10 is the part of the delay line on the top layer) and twelve output ports 12-23 of a feed network (the feed network is composed of a twelve-way substrate integrated waveguide power divider and a substrate integrated waveguide delay line). Each output port of the feed network is connected with a series feed microstrip linear array radiating unit. The antenna array has twelve linear array radiating elements along the + x direction, and the linear array radiating elements form an integral antenna array together. All round holes in the figure represent metallized through holes. The linear array radiating element 9 is in the form of a series-fed microstrip. The phases required by the twelve output ports 12-23 of the feed network are 35.8 degrees, 123.5 degrees, 191.6 degrees, 256.8 degrees, 0 degrees, 114.7 degrees, 133 degrees, 200.9 degrees, 275.1 degrees, 319.1 degrees, 14.4 degrees and 115.6 degrees respectively.
Fig. 3 shows the structure of the first middle metal layer 2 of the antenna array according to the present invention, and it can be seen that in order to couple each sub-substrate integrated waveguide delay line from the bottom dielectric layer 7 to the top dielectric layer 5, there is a coupling slot 24 and a inductive metal via 11 for impedance matching in the first middle metal layer 2. In order to meet the phase requirement of each linear array port of the quadratic of cosecant, the design length of each substrate integrated waveguide delay line needs to be adjusted. The top medium and the bottom medium are both provided with delay line structures, and each layer of medium corresponds to two layers of circuits. Therefore, a substrate integrated waveguide delay line structure is arranged on each of the four metal layers. Fig. 4 shows the structure of the second intermediate metal layer 3 of the antenna array according to the present invention, and it can be seen that this layer is mainly the core part of the beamforming antenna, i.e. the substrate integrated waveguide power divider. The substrate integrated waveguide power divider is of a one-path twelve-path structure and consists of five symmetrical one-path two-path power dividers 25-29 of a one-path two-path power divider and a two-path power divider. From the input port, the first stage passes through a power divider 25 of a power divider/. And each time the signal passes through the first-stage equal-power distributor, the signal power is changed into half of the original power. Therefore, the power distribution ratio of 1:1:1:1:2:2:8:8:2:2:2:2 can be seen at the output ports 30-41 of the one-path twelve-path power divider. This divide twelve road chip integrated waveguide power divider structure all the way and divide the ware design to accomplish by symmetry one minute two merit, compare in asymmetric structure, the utility model provides a power distribution structural design is more simple and very high to the machining error tolerance. At the same time, there is also a substrate integrated waveguide delay line 42 of a corresponding length on the second intermediate metal layer 3. It should be noted that in order to ensure that the twelve output ports 12-23 of the feed network are level with each other, the length 42 of each sub-substrate integrated waveguide delay line at the bottom layer and the length 10 of each sub-substrate integrated waveguide delay line at the top layer should be equal.
Fig. 5 shows the structure of the bottom metal layer 4 of the antenna array of the present invention, in order to be able to be matched with the standard test interface, the substrate integrated waveguide is herein designed to be the transition structure 31 of the coplanar waveguide, thereby the substrate integrated waveguide is transited to the grounded coplanar waveguide by adopting the gradual transition mode at the input end of the substrate integrated waveguide, so as to facilitate the subsequent related test.
The linear array radiation unit adopts a series-fed microstrip patch antenna form, every two linear arrays are arranged at equal intervals, and the interval is 6.8 mm.
A design method of an antenna structure with a cosecant quadrivalent radiation directional diagram specifically comprises the following steps:
the method comprises the following steps: the linear array radiation unit structure is determined by the actually required vertical plane beam width, and a six-unit series feed microstrip linear array is adopted to meet the requirement of 15 degrees of half-power beam width in the vertical direction. Relevant parameters were adjusted by commercial full-wave simulation software to meet the reflection coefficient and antenna pattern performance requirements.
Step two: determining the number of linear array radiation units arranged in the horizontal direction according to the requirements of a cosecant quadrivalent antenna target directional diagram on antenna gain and the horizontal plane detection range; here, twelve line radiation units are determined in the horizontal direction.
Step three: determining the amplitude and the phase of excitation of each linear array port according to a preset cosecant quadrivalent antenna target directional diagram; the horizontal plane directional diagram of the antenna array meets the requirement of a cosecant quartic formula within the radar target view field angle, namely:
θ∈[-0.5θ1,0.5θ1]wherein theta0For residual cutting of the starting angle of the covered area, theta1Angular range, θ, to be covered by the radar2Is the included angle between the central line of the coverage area and the horizontal direction. Wherein the phases required by the twelve output ports 12-23 of the feed network35.8 degrees, 123.5 degrees, 191.6 degrees, 256.8 degrees, 0 degrees, 114.7 degrees, 133 degrees, 200.9 degrees, 275.1 degrees, 319.1 degrees, 14.4 degrees, 115.6 degrees, respectively. The required power ratio is 1:1:1:1:2:2:8:8:2:2:2:2, theta in the design0,θ1,θ215 degrees, 40 degrees and 35 degrees, respectively.
Step four: designing an integrated substrate integrated waveguide feed network according to the distance between different radiation units designed in the third step and the feed amplitude of each path, and meeting the requirement of a reflection coefficient;
step five: and calculating the phase of each path needing extra delay according to the phase requirement needed by each port and the phase output by each port of the step four middle feeding network. Different lengths of the substrate integrated waveguide delay line are designed to meet the phase requirements of each port. And simultaneously, designing a gap coupling feed structure between different layers to be used for connecting delay lines between different dielectric layers. One half of the substrate integrated waveguide delay line is arranged on a bottom medium substrate, the other half of the substrate integrated waveguide delay line is arranged on a top medium substrate, and the middle of the substrate integrated waveguide delay line is connected through a gap coupling structure between different layers. The positions of the output ports of the substrate integrated waveguide delay line on the top dielectric substrate are flush with each other.
Step six: and combining the series feed microstrip linear array radiating unit designed in the step one, the substrate integrated waveguide antenna feed network designed in the step four and the substrate integrated waveguide delay line designed in the step five together to form a complete antenna array.
Compared with the prior art, the utility model provides an antenna structure can support millimeter wave synthetic aperture radar's cosecant cutting figurative demand. Under the condition of the same target radar scattering cross section, the cosecant quadrifilar antenna can achieve the purpose that the return echo powers of targets at different angle positions in a field of view are equal. And the feed network part consists of symmetrical equal-power substrate integrated waveguide power dividers, so that the tolerance to processing errors is higher. Meanwhile, most of the feed network is placed on the bottom layer, and the occupied area of the whole antenna is only a little larger than that of the radiating unit, so that the whole structure is more compact.
In order to verify the performance of the antenna array of the utility model, based on the above method and structure, adopt microwave panel Taconic TLY-5 that dielectric constant 2.2, thickness are 0.508mm as top layer, bottom medium, and dielectric constant 3.52, thickness are 0.101 mm's Rogers 4450F as the sticker, have processed the cosecant fourth power beam forming antenna array who works in the Ka band. The vector network analyzer and the frequency expansion equipment are adopted to test the antenna reflection coefficient, the test result is shown in figure 6, and the test result and the simulation result are better in accordance; meanwhile, the directional diagram of the antenna is tested in a far-field darkroom, the horizontal plane (H plane) and inclined E plane radiation directional diagrams of the antenna array are shown in figures 7 and 8, the gain is shown in figure 9, and both simulation and test results reach the design target. The related simulation and test results of the array antenna structure show that the antenna structure can meet the cosut shaping requirement for the application of the synthetic aperture radar. Under the condition of the same radar scattering cross section, the received echo powers of targets with different distances in the target field of view are approximately equal (as shown in fig. 10), so that the utilization efficiency of the transmitted energy is effectively improved. Meanwhile, the antenna array has the advantages of low profile, easiness in integration with a planar circuit, high reliability of a feed network design and the like.
Above embodiment only is for explaining the utility model discloses a technical thought can not be injectd with this the utility model discloses a protection scope, all according to the utility model provides a technical thought, any change of doing on technical scheme basis all falls into the utility model discloses within the protection scope.
Claims (7)
1. A beamforming antenna structure, characterized by: the horizontal plane directional diagram of the antenna array meets the requirement of a cosecant quartic formula within the radar target view field angle, namely:
wherein theta is0For residual cutting of the starting angle of the covered area, theta1Angular range, θ, to be covered by the radar2Is the included angle between the central line of the coverage area and the horizontal direction.
2. The beamforming antenna structure according to claim 1, wherein: the integrated waveguide power feed network comprises a path-division multi-path substrate integrated waveguide power divider and a substrate integrated waveguide delay line, and each output end of the power feed network is connected with the input end of the linear array radiating unit; by adjusting the amplitude and the phase of the feed of each port of the linear array radiation unit, the horizontal plane directional diagram of the antenna array meets the requirement of a cosecant quartic formula within the radar target view field angle.
3. The beamforming antenna structure according to claim 2, wherein: the substrate integrated waveguide power divider is of a structure that one path is divided into twelve paths, and the output end of each path is connected with the input end of one substrate integrated waveguide delay line.
4. A beamforming antenna structure according to claim 3, wherein: the power distribution structure with one path divided into twelve paths consists of one-half and two-half power substrate integrated waveguide power dividers which are symmetrical in a five-level structure; the power distribution ratio of the output ports of the power divider dividing one path into twelve paths is 1:1:1:2:2:8:8:2:2: 2.
5. A beamforming antenna structure according to one of claims 2 to 4, wherein: the beam forming antenna array structure is respectively as follows from top to bottom: the device comprises a top metal layer, a top dielectric substrate, a first middle metal layer, a pasting dielectric layer, a second middle metal layer, a bottom dielectric substrate and a bottom metal layer; the top metal layer and the first middle metal layer are positioned on the upper surface and the lower surface of the top dielectric substrate, and the second middle metal layer and the bottom metal layer are positioned on the upper surface and the lower surface of the bottom dielectric substrate;
arranging the linear array radiation unit, the output end of the feed network and one half of the substrate integrated waveguide delay line structure on the top metal layer; the other half of the substrate integrated waveguide delay line structure is arranged on the bottom layer medium substrate; the two half substrate integrated waveguide delay lines are connected in the middle through a gap coupling structure between different layers;
and arranging the substrate integrated waveguide power divider on the second intermediate metal layer.
6. The beamforming antenna structure according to claim 5, wherein: the positions of the output ports of the substrate integrated waveguide delay line on the top dielectric substrate are flush with each other.
7. The beamforming antenna structure according to claim 1, wherein: the linear array radiating unit adopts a series feed microstrip patch antenna mode, and every two linear arrays are arranged at equal intervals.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201921456131.5U CN210182584U (en) | 2019-09-03 | 2019-09-03 | Beam forming antenna structure |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201921456131.5U CN210182584U (en) | 2019-09-03 | 2019-09-03 | Beam forming antenna structure |
Publications (1)
| Publication Number | Publication Date |
|---|---|
| CN210182584U true CN210182584U (en) | 2020-03-24 |
Family
ID=69842844
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201921456131.5U Active CN210182584U (en) | 2019-09-03 | 2019-09-03 | Beam forming antenna structure |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN210182584U (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN114024129A (en) * | 2021-10-12 | 2022-02-08 | 中国电子科技集团公司第二十九研究所 | Balanced microstrip series-fed array antenna |
| CN114614259A (en) * | 2020-12-09 | 2022-06-10 | 中国联合网络通信集团有限公司 | Shaping control method, device, equipment and storage medium for luneberg lens antenna |
| TWI801155B (en) * | 2021-04-26 | 2023-05-01 | 友達光電股份有限公司 | Antenna array |
-
2019
- 2019-09-03 CN CN201921456131.5U patent/CN210182584U/en active Active
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN114614259A (en) * | 2020-12-09 | 2022-06-10 | 中国联合网络通信集团有限公司 | Shaping control method, device, equipment and storage medium for luneberg lens antenna |
| TWI801155B (en) * | 2021-04-26 | 2023-05-01 | 友達光電股份有限公司 | Antenna array |
| CN114024129A (en) * | 2021-10-12 | 2022-02-08 | 中国电子科技集团公司第二十九研究所 | Balanced microstrip series-fed array antenna |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN110534923B (en) | Beam forming antenna structure and design method | |
| CN106911011B (en) | Array antenna structure and design method | |
| Valkonen | Compact 28-GHz phased array antenna for 5G access | |
| CN210182584U (en) | Beam forming antenna structure | |
| CN114614257B (en) | Planar high-isolation K/Ka frequency band common-caliber phased array antenna | |
| CN101533961B (en) | Shared substrate multi-beam antenna based on eight port junctions | |
| CN111987435B (en) | Low-profile dual-polarized antenna, array antenna and wireless communication equipment | |
| CN107968267B (en) | Multi-beam end-fire antenna | |
| CN101931122A (en) | C/X dual-band microstrip antenna | |
| CN201383549Y (en) | Multibeam antenna with high radiation efficiency | |
| CN101291017A (en) | Multi-beam antenna of substrate integrated wave-guide based on principal of Rotman lens | |
| CN115207636A (en) | Millimeter wave circularly polarized antenna unit of gap coupling multiple spot feed | |
| CN111262025A (en) | Integrated substrate gap waveguide beam scanning leaky-wave antenna | |
| CN112054275A (en) | Low-loss switching device of substrate integrated waveguide end feed antenna | |
| CN114709627B (en) | Multi-band configurable receiving antenna | |
| CN211670320U (en) | ISGW (integrated signal ground wire) beam scanning leaky-wave antenna | |
| Temga et al. | 28GHz-band 2x2 patch antenna module vertically integrated with a compact 2-D BFN in broadside coupled stripline structure | |
| CN114361788A (en) | High-radiation-efficiency circularly polarized antenna unit suitable for millimeter wave frequency band | |
| KR102251287B1 (en) | 5g beamforming antenna over a wide-band miniaturized by segmenting the substrate-integrated-waveguide structure into layers and stacking them | |
| TWI674704B (en) | Low sidelobe array antenna | |
| CN113488769A (en) | Parallel plate waveguide power divider and CTS antenna | |
| CN201215831Y (en) | Low loss substrate integrated wave-guide multi-beam antenna | |
| Liu et al. | A low sidelobe multibeam slot array antenna fed by Rotman lens | |
| YE et al. | Multibeam antenna based on butler matrix for 3G/LTE/5G/B5G base station applications | |
| Pavithra et al. | Design of microstrip patch array antenna using beamforming technique for ISM band |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| GR01 | Patent grant | ||
| GR01 | Patent grant |