CN1913320B - Digital controlled inversion power supply and its control method - Google Patents

Abstract

This invention discloses a digit controlled inversion supply and its control method, in which, the output of an augmented state feedback digit controller is connected with the input of an inverter, the output of which is connected with the input of a voltage sensor and a load, the first output end of the voltage sensor is connected with the negative input of a subtracter, the positive input of which receives reference volume ur, the output of which is connected with the input of a controller, the inverter is connected DC supply, the current led out from the inverter is connected with the inputof the current sensor, the output of which and a second output of the voltage sensor are connected with the negative input of the controller constituting a microprocessor with the subtracter.

Description

The control method of numerically controlled inverter

Technical field

The present invention relates to a kind of control method of numerically controlled inverter.

Background technology

Along with development of science and technology, the raising of the level of informatization, important department, power consumption equipment increase day by day to the requirement of power supply power supply quality on the one hand, the continuous increase of a large amount of uses of power electronic equipment, nonlinear load makes that the harmonic pollution of electrical network is very serious on the other hand, has formed distinct imbalance between supply and demand.For this reason, the research of High Performance PWM inverter more and more receives publicity in recent years.

Digital control have many superior parts with respect to simulation control, makes it to be subjected to extensive concern.The particularly development of advancing by leaps and bounds along with microelectric techniques such as microprocessors in recent years, numerically controlled hardware platform upgrades day by day, more accelerates numerically controlled applying.Response characteristic was bad when the digitial controller of PWM inverter adopted conventional control strategy, compared performance with the conventional simulation controller and obviously descended; Repeat control and can suppress periodic disturbance well, improve the steady-state response of system, but dynamic response is unhappy, at least at one more than the primitive period; Dead beat control has dynamic responding speed faster, but control performance is strong to the system parameters dependence, and parameter is changed sensitivity, and poor robustness might reduce the stability of a system or even unstable; Be suggested though as seen more can bring into play several special digital control methods of digital control advantage, exist not enough.

In " based on the PWM inverter Research on Control of state space theory " (Central China University of Science and Technology's thesis for the doctorate in 2004) a kind of PWM inverter has been proposed.This PWM inverter as a state variable, carries out augmented state feedback digital control to inverter with filter inductance electric current or filter capacitor electric current.This control method is compared with above-mentioned digital control method, advantage is to take into account the dynamic and steady-error coefficient characteristic of inverter, but still exist for problems such as the switching tube ON time loss that exists in digital control, load disturbance influences, and its control effect still has suitable gap than simulation control.

Summary of the invention

The objective of the invention is to overcome above-mentioned the deficiencies in the prior art part, a kind of control method of numerically controlled inverter is provided; Utilize this control method can make the inverter dynamic response fast, steadily, the total percent harmonic distortion of output voltage is low under the nonlinear load situation, surpass under 3 the situation at specified nonlinear load, load current crest factor, the total percent harmonic distortion of output voltage is also lower, the stable state accuracy height, and simple in structure, cost is lower.

The control method of numerically controlled inverter provided by the invention, described inverter comprises inverter, the control input end and the microprocessor of inverter join, the output of inverter joins with the input of voltage sensor and load, the electric current of drawing in the inverter and the input of current sensor join, the direct-flow input end of inverter links to each other with DC power supply, and the output of voltage sensor and the output of current sensor join with microprocessor respectively; Described control method may further comprise the steps:

The 1st step was gathered the inverter output voltage u of the current bat k of voltage sensor output ₀(k) and the output current i (k) of the current bat k of current sensor output;

The 2nd step utilized formula A to calculate the error intergal signal e of current bat k _i(k), e wherein _i(k-1) be the last one error intergal signal of clapping, its initial value is 0;

e _i(k)＝e(k)+e _i(k-1) (A)

Wherein e (k) is current bat error signal, and its value equals the reference quantity u of current bat k _r(k) with the current output voltage u that claps k ₀(k) difference;

It is load current i that the 3rd step was worked as the output current i that gathers ₀The time, utilize the error intergal signal e of current bat _i(k) calculate the control signal u of next bat ₁(k+1), u ₁(k+1) be the control signal of next bat of inverter; Its processing procedure is:

The 3.1st step utilized formula D1 to calculate the output voltage measured value of next bat Filter inductance electric current measured value with next bat

U wherein ₁(k), i ₀(k) and i ₁(k) be respectively control signal, load current and the filter inductance electric current of current bat, Be respectively output voltage measured value and the filter inductance electric current measured value of current bat k, T is the sampling period:

$\left[\begin{array}{c}{\hat{u}}_0(k+1)\\ {\hat{i}}_1(k+1)\end{array}\right]=(A_d-{\mathrm{HC}}_d)\left[\begin{array}{c}{\hat{u}}_0\left(k\right)\\ {\hat{i}}_1\left(k\right)\end{array}\right]+B_d\left[\begin{array}{c}{u}_1\left(k\right)\\ i_0\left(k\right)\end{array}\right]+{\mathrm{HC}}_d\left[\begin{array}{c}{u}_0\left(k\right)\\ i_1\left(k\right)\end{array}\right]---\left(D1\right)$

Wherein,

$A_d=\left[\begin{array}{cc}{e}^{-\frac{r}{2L}T}\cos {\mathrm{\ω}}_{d}T+\frac{r}{2L{\mathrm{\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T& \frac{1}{C{\mathrm{\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T\\ -\frac{1}{{\mathrm{L\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T& e^{-\frac{r}{2L}T}\cos {\mathrm{\ω}}_{d}T-\frac{r}{2L{\mathrm{\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T\end{array}\right]$

B _d＝[H ₁?H ₂]

$H_1=\left[\begin{array}{c}{e}^{-\frac{r}{2L}T}(-\cos {\mathrm{\ω}}_{d}T-\frac{r}{2L{\mathrm{\ω}}_d}\sin {\mathrm{\ω}}_{d}T)+1\\ \frac{1}{L{\mathrm{\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T\end{array}\right]$

$H_2=\left[\begin{array}{c}r(e^{-\frac{r}{2L}T}\cos {\mathrm{\ω}}_{d}T+\frac{r}{2L{\mathrm{\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T-1)-\frac{1}{C{\mathrm{\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T\\ -e^{-\frac{r}{2L}T}\cos {\mathrm{\ω}}_{d}T-\frac{r}{2L{\mathrm{\ω}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\ω}}_{d}T+1\end{array}\right]$

C _d＝[1?0]

${\mathrm{\ω}}_n=\frac{1}{\sqrt{\mathrm{LC}}},$ Natural frequency of oscillation for inverter

${\mathrm{\ω}}_d=\sqrt{\frac{1}{\mathrm{LC}}-\frac{r^2}{4L^2}},$ Damped oscillation frequency for inverter

L is the filter inductance of inverter, and C is the filter capacitor of inverter, and r is the equivalent damping resistance of inverter, and H is the feedback gain matrix of state observer;

The 3.2nd step utilized formula D2 to calculate the error signal measured value of next bat

Wherein

Reference quantity for next bat:

$\hat{e}(k+1)=u_r(k+1)-{\hat{u}}_0(k+1)---\left(D2\right)$

The 3.3rd step utilized formula D3 to calculate the error intergal signal measured value of next bat

${\hat{e}}_i(k+1)=\hat{e}(k+1)+e_i\left(k\right)---\left(D3\right)$

The 3.4th step utilized formula D4 or formula D5-D6 to calculate the control signal u of next bat ₁(k+1), wherein Filter capacitor electric current measured value for next bat:

$u_1(k+1)=k_i{\hat{e}}_i(k+1)-k_1{\hat{u}}_0(k+1)-k_2{\hat{i}}_1(k+1)---\left(D4\right)$

${\hat{i}}_c(k+1)={\hat{i}}_1(k+1)-i_0\left(k\right)---\left(D5\right)$

$u_1(k+1)=k_i{\hat{e}}_i(k+1)-k_1{\hat{u}}_0(k+1)-k_2{\hat{i}}_c(k+1)---\left(D6\right)$

Wherein, $k_i=\frac{1+{\mathrm{\β}}_2+{\mathrm{\β}}_3+{\mathrm{\β}}_4}{1-2e^{-\frac{r}{2L}T}\cos {\mathrm{\ω}}_{d}T+e^{-\frac{r}{L}T}}$

${\mathrm{<figure-callout\; id="1"\; label="k"\; filenames="H2006100197123E00042.png"\; state="\{\{state\}\}">k</figure-callout>}}_1=\frac{{\mathrm{\&beta;}}_2-{\mathrm{\&beta;}}_4+1+2a_1-e^{-\frac{r}{L}T}-(1-a_1-a_2)k_i}{1-2a_1+e^{-\frac{r}{L}T}}$

$k_2=\frac{{\mathrm{\&beta;}}_2+1+2a_1-(1-a_1-a_2)({\mathrm{<figure-callout\; id="1"\; label="k"\; filenames="H2006100197123E00042.png"\; state="\{\{state\}\}">k</figure-callout>}}_1+k_i)}{2a_2/r}$

$a_1=e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T$

$a_2=\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T;$

β ₂, β ₃And β ₄Be respectively closed-loop pole Z by expectation ₁, Z ₂, Z ₃Characteristic equation (the Z-Z that determines ₁) (Z-Z ₂) (Z-Z ₃)=Z ³+ β ₂Z ²+ β ₃Z+ β ₄In the quadratic term, once and the coefficient of constant term of expansion;

The 4th step was utilized control signal u ₁(k+1) inverter is regulated;

The 5th step made k=k+1, repeated for the 1st step to the 4th step, until end-of-job.

The present invention compared with prior art has the following advantages:

(1) under the idle condition, it is short that the settling time of waveform is followed the tracks of in the inverter control system dynamic instruction that is made of augmented state feedback digital controller and inverter, is no more than 3.5ms, and overshoot is little, less than 9%.

When (2) load changing reached rated power, dynamic transition process was no more than 2ms, and the output voltage rate of change is no more than 10%, and workload-adaptability strengthens.

(3) under the various loading conditions from the zero load to the nominal load, all within 0.5%, steady-state error reduces the precision of voltage regulation greatly.

(4) the total percent harmonic distortion of output voltage is low under the nonlinear load situation, surpass under 3 the situation at specified nonlinear load, load current crest factor, the total percent harmonic distortion of output voltage is also lower, for example, at the electric current crest factor is 3.03 o'clock, THD=1.9% shows the wave distortion that nonlinear load is caused and has stronger inhibition ability.

(5) the present invention is in the design to inverter augmented state feedback digital controller Control Parameter, adopt STATE FEEDBACK CONTROL to realize any configuration of system's closed-loop pole, with stability, the dynamic property of safeguards system and reduce steady-state error, whole power-supply system has stronger robustness. under various load disturbance situation, all can obtain colory ac output voltage; Whole inverter system changes insensitive to inverter parameter, augmented state feedback digital controller parameter, the system responses performance is stable.

(6) circuit structure of the present invention is simple, and cost is low, is easy to realize.

Description of drawings

Fig. 1 is the structural representation of the inverter of augmented state feedback digital control;

Fig. 2 is the microprocessor main program flow chart;

Fig. 3 is the control algolithm program flow diagram one among Fig. 2;

Fig. 4 is the schematic circuit block diagram one of Fig. 1;

Fig. 5 is the control algolithm program flow diagram two among Fig. 2;

Fig. 6 is the schematic circuit block diagram two of Fig. 1;

Fig. 7 is the control algolithm program flow diagram three among Fig. 2;

Fig. 8 is the control algolithm program flow diagram four among Fig. 2;

Fig. 9 is the schematic circuit block diagram three of Fig. 1.

Embodiment

Below in conjunction with accompanying drawing the present invention is described in further detail.

As shown in Figure 1, the structure of the inverter of augmented state feedback digital control of the present invention is: the output of augmented state feedback digital controller 7 and the control input end of inverter 2 join, the input of the output of inverter 2 and voltage sensor 5 and load 3 are joined, the first via output of voltage sensor 5 and the negative input end of subtracter 8 join, and the positive input terminal of subtracter 8 receives reference quantity u _rThe input of the output of subtracter 8 and augmented state feedback digital controller 7 joins, the direct-flow input end of inverter 2 connects DC power supply 4, the input of electric current of drawing in the inverter 2 and current sensor 6 joins, and the second road output of the output of current sensor 6 and voltage sensor 5 joins with two inverting inputs of augmented state feedback digital controller 7 respectively.

Inverter 2, voltage sensor 5 and current sensor 6 can be selected common inverter, voltage sensor and current sensor for use.

Subtracter 8 and augmented state feedback digital controller 7 constitute microprocessor 1.Wherein microprocessor can be single-chip microcomputer or digital signal processing chip.

Microprocessor 1 is gathered the voltage signal of voltage sensor 5 outputs and the current signal of current sensor 6 outputs, according to electric current, voltage signal and reference quantity, and the calculation control signal, and export inverter 2 to, control inverter 2 work.

Microprocessor 1 and inverter 2 constitute an augmented state feedback digital control system, current i in the inverter 2 and output voltage u ₀Enter microprocessor 1 through over-current sensor and voltage sensor respectively, microprocessor 1 is through producing control signal u behind the sequential operation ₁Inverter 2 is implemented control, and wherein the current signal i in the inverter 2 can be the filter inductance current i ₁, the filter capacitor current i _cWith load current i ₀

The control method that augmented state feedback digital controller 7 is adopted the steps include: as shown in Figure 2

(1) gathers the output voltage u of the current bat that voltage sensor obtains ₀(k) and the output current i (k) of the current bat that obtains of current sensor, calculate the error signal e (k) of current bat, e (k) equals the reference quantity u of current bat _r(k) with the output voltage u of current bat ₀(k) difference; A sampling period T is called a bat in numerical control system, discrete constantly the expression with kT, be abbreviated as k, and represent k the discrete moment, its initial value is 0.

(2) utilize formula (A) to calculate the error intergal signal e of current bat _i(k), e wherein _i(k-1) be the last one error intergal signal of clapping, its initial value is 0;

e _i(k)＝e(k)+e _i(k-1) (A)

(3) utilize the error intergal signal e of current bat _i(k) calculate the control signal u of next bat ₁(k+1);

Because the current i in the inverter 2 comprises the filter inductance current i ₁, the filter capacitor current i _cWith load current i ₀,, adopt the control signal u of different next bats of algorithm computation according to the difference of the current signal of gathering ₁(k+1), illustrated respectively below.

(3A) the current signal i when collection is the filter inductance current i ₁The time, as shown in Figure 3, utilize formula (B) to calculate the control signal u of next bat ₁(k+1), i wherein ₁(k) be the filter inductance electric current of current bat:

u ₁(k+1)＝k _ie _i(k)-k ₁u ₀(k)-k ₂i ₁(k) (B)

Fig. 4 is corresponding with it schematic circuit block diagram.As shown in Figure 4, output voltage u ₀With reference quantity u _rRelatively the error signal e of back generation produces error intergal signal e through integral element 9 _i, error intergal signal e _iMultiply by integral coefficient k _iAfter deduct output voltage u ₀With the Voltage Feedback coefficient k ₁Product, deduct the filter inductance current i again ₁With the current feedback coefficient k ₂Product, last controlled signal u ₁Inverter 2 is regulated.

(3B) the current signal i when collection is the filter capacitor current i _cThe time, as shown in Figure 5, utilize formula (C) to calculate the control signal u of next bat ₁(k+1), i wherein _c(k) be the filter capacitor electric current of current bat:

u ₁(k+1)＝k _ie _i(k)-k ₁u ₀(k)-k ₂i _c(k) (C)

Fig. 6 is corresponding with it schematic circuit block diagram.As shown in Figure 6, its structure is similar to Fig. 4, and difference is that the electric current of inverter 2 among Fig. 4 is filter inductance current i ₁, and the electric current of inverter 2 is filter capacitor current i among Fig. 6 _c

(3C) the current signal i when collection is load current i ₀The time, as shown in Figure 7 and Figure 8, step (3) comprises following process:

(3C1) utilize formula (D1) to calculate the output voltage measured value of next bat Filter inductance electric current measured value with next bat

I wherein ₀(k) be the load current of current bat:

$\left[\begin{array}{c}{\hat{u}}_0(k+1)\\ {\hat{i}}_1(k+1)\end{array}\right]=(A_d-{\mathrm{HC}}_d)\left[\begin{array}{c}{\hat{u}}_0\left(k\right)\\ {\hat{i}}_1\left(k\right)\end{array}\right]+B_d\left[\begin{array}{c}{u}_1\left(k\right)\\ i_0\left(k\right)\end{array}\right]+{\mathrm{HC}}_d\left[\begin{array}{c}{u}_0\left(k\right)\\ i_1\left(k\right)\end{array}\right]---\left(D1\right)$

$A_d=\left[\begin{array}{cc}{e}^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T+\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T& \frac{1}{C{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\\ -\frac{1}{{\mathrm{L\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T& e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T-\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\end{array}\right]$

B _d＝[H ₁?H ₂]

${\mathrm{<figure-callout\; id="1"\; label="H"\; filenames="H2006100197123E00042.png"\; state="\{\{state\}\}">H</figure-callout>}}_1=\left[\begin{array}{c}{e}^{-\frac{r}{2L}T}(-\cos {\mathrm{\&omega;}}_{d}T-\frac{r}{2L{\mathrm{\&omega;}}_d}\sin {\mathrm{\&omega;}}_{d}T)+1\\ \frac{1}{L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\end{array}\right]$

$H_2=\left[\begin{array}{c}r(e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T+\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T-1)-\frac{1}{C{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\\ -e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T-\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T+1\end{array}\right]$

C _d＝[1?0]

${\mathrm{\&omega;}}_n=\frac{1}{\sqrt{\mathrm{LC}}},$ Natural frequency of oscillation for inverter 2

${\mathrm{\&omega;}}_d=\sqrt{\frac{1}{\mathrm{LC}}-\frac{r^2}{4L^2}},$ Damped oscillation frequency for inverter 2

Wherein L is the filter inductance of inverter 2, and C is the filter capacitor of inverter 2, and r is the equivalent damping resistance of inverter 2;

H is the feedback gain matrix of state observer 10, according to (A _d-HC _d) characteristic value select feedback gain matrix H to get final product than the fast principle more than 5 times of the closed loop characteristic value of inverter 2.

(3C2) utilize formula (D2) to calculate the error signal measured value of next bat

$\hat{e}(k+1)=u_r(k+1)-{\hat{u}}_0(k+1)---\left(D2\right)$

(3C3) utilize formula (D3) to calculate the error intergal signal measured value of next bat

${\hat{e}}_i(k+1)=\hat{e}(k+1)+e_i\left(k\right)---\left(D3\right)$

(3C4) utilize formula (D4) or formula (D5)-(D6) to calculate the control signal u of next bat ₁(k+1), wherein Filter capacitor electric current measured value for next bat:

$u_1(k+1)=k_i{\hat{e}}_i(k+1)-k_1{\hat{u}}_0(k+1)-k_2{\hat{i}}_1(k+1)---\left(D4\right)$

${\hat{i}}_c(k+1)={\hat{i}}_1(k+1)-i_0\left(k\right)---\left(D5\right)$

$u_1(k+1)=k_i{\hat{e}}_i(k+1)-k_1{\hat{u}}_0(k+1)-k_2{\hat{i}}_c(k+1)---\left(D6\right)$

Fig. 9 is the schematic circuit block diagram corresponding with Fig. 7 and Fig. 8.As shown in Figure 9, its structure is similar to Fig. 4, and difference is that the electric current of inverter 2 among Fig. 4 is filter inductance current i ₁, and the electric current of inverter 2 is load current i among Fig. 9 ₀ Comprise state observer 10 in the augmented state feedback digital controller 7 among Fig. 9.State observer 10 is according to the output voltage u of current bat ₀(k) and the load current i of current bat ₀(k) observe the output voltage measured value of next bat Filter inductance electric current measured value with next bat

Its computing formula is formula (D1).

Three state variables, i.e. output voltage u are arranged in the augmented state feedback digital control system ₀, the filter inductance current i ₁(filter capacitor current i _c) and error intergal signal e _i, three state variables respectively corresponding three Control Parameter, i.e. Voltage Feedback coefficient k ₁, the current feedback coefficient k ₂With integral coefficient k _iThe design key of augmented state feedback digital controller 7 is determining of its three Control Parameter.

If the state feedback gain matrix is:

K＝[k ₁?k ₂?k _i]

Closed-loop pole Z by expectation ₁, Z ₂, Z ₃The characteristic equation of determining is:

(Z-Z ₁)(Z-Z ₂)(Z-Z ₃)＝Z ³+β ₂Z ²+β ₃Z+β ₄

β in the following formula ₂, β ₃And β ₄Be respectively the quadratic term of characteristic equation expansion, once and the coefficient of constant term.

Relatively can get:

$k_i=\frac{1+{\mathrm{\&beta;}}_2+{\mathrm{\&beta;}}_3+{\mathrm{\&beta;}}_4}{1-2e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T+e^{-\frac{r}{L}T}}$

${\mathrm{<figure-callout\; id="1"\; label="k"\; filenames="H2006100197123E00042.png"\; state="\{\{state\}\}">k</figure-callout>}}_1=\frac{{\mathrm{\&beta;}}_2-{\mathrm{\&beta;}}_4+1+2a_1-e^{-\frac{r}{L}T}-(1-a_1-a_2)k_i}{1-2a_1+e^{-\frac{r}{L}T}}$

$k_2=\frac{{\mathrm{\&beta;}}_2+1+2a_1-(1-a_1-a_2)({\mathrm{<figure-callout\; id="1"\; label="k"\; filenames="H2006100197123E00042.png"\; state="\{\{state\}\}">k</figure-callout>}}_1+k_i)}{2a_2/r}$

Wherein $a_1=e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T$

$a_2=\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T$

In the above-mentioned derivation with the filter inductance current i ₁As a state variable, if use the filter capacitor current i _cReplace inductive current i ₁As state variable, because of the system features equation is identical, so Control Parameter is still determined by top three formulas.

(4) utilize control signal u ₁(k+1) inverter 2 is regulated;

(5) make k=k+1, repeating step (1)-(4) are until end-of-job.

Claims (1)

1. the control method of a numerically controlled inverter, described inverter comprises inverter, the control input end and the microprocessor of inverter join, the output of inverter joins with the input of voltage sensor and load, the electric current of drawing in the inverter and the input of current sensor join, the direct-flow input end of inverter links to each other with DC power supply, and the output of voltage sensor and the output of current sensor join with microprocessor respectively; Described control method may further comprise the steps:

The 1st step was gathered the inverter output voltage u of the current bat k of voltage sensor output ₀(k) and the output current i (k) of the current bat k of current sensor output;

The 2nd step utilized formula A to calculate the error intergal signal e of current bat k _i(k), e wherein _i(k-1) be the last one error intergal signal of clapping, its initial value is 0;

e _i(k)＝e(k)+e _i(k-1) (A)

Wherein e (k) is current bat error signal, and its value equals the reference quantity u of current bat k _r(k) with the current output voltage u that claps k ₀(k) difference;

It is load current i that the 3rd step was worked as the output current i that gathers ₀The time, utilize the error intergal signal e of current bat _i(k) calculate the control signal u of next bat ₁(k+1), u ₁(k+1) be the control signal of next bat of inverter; Its processing procedure is:

The 3.1st step utilized formula D1 to calculate the output voltage measured value of next bat Filter inductance electric current measured value with next bat U wherein ₁(k), i ₀(k) and i ₁(k) be respectively control signal, load current and the filter inductance electric current of current bat k, Be respectively output voltage measured value and the filter inductance electric current measured value of current bat k, T is the sampling period:

$\left[\begin{array}{c}{\hat{u}}_0(k+1)\\ {\hat{i}}_1(k+1)\end{array}\right]=(A_d-{\mathrm{HC}}_d)\left[\begin{array}{c}{\hat{u}}_0\left(k\right)\\ {\hat{i}}_1\left(k\right)\end{array}\right]+B_d\left[\begin{array}{c}{u}_1\left(k\right)\\ i_0\left(k\right)\end{array}\right]+{\mathrm{HC}}_d\left[\begin{array}{c}{u}_0\left(k\right)\\ i_1\left(k\right)\end{array}\right]---\left(D1\right)$

Wherein,

$A_d=\left[\begin{array}{cc}{e}^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T+\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T& \frac{1}{C{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\\ -\frac{1}{{\mathrm{L\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T& e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T-\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\end{array}\right]$

B _d＝[H ₁?H ₂]

$H_1=\left[\begin{array}{c}{e}^{-\frac{r}{2L}T}(-{\cos \mathrm{\&omega;}}_{d}T-\frac{r}{2L{\mathrm{\&omega;}}_d}\sin {\mathrm{\&omega;}}_{d}T)+1\\ \frac{1}{{\mathrm{L\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\end{array}\right]$

$H_2=\left[\begin{array}{c}r(e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T+\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T-1)-\frac{1}{{\mathrm{C\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T\\ -e^{-\frac{r}{2L}t}\cos {\mathrm{\&omega;}}_{d}T-\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T+1\end{array}\right]$

C _d＝[1?0]

${\mathrm{\&omega;}}_n=\frac{1}{\sqrt{\mathrm{LC}}},$ Natural frequency of oscillation for inverter

${\mathrm{\&omega;}}_d=\sqrt{\frac{1}{\mathrm{LC}}-\frac{r^2}{{4L}^2}},$ Damped oscillation frequency for inverter

L is the filter inductance of inverter, and C is the filter capacitor of inverter, and r is the equivalent damping resistance of inverter, and H is the feedback gain matrix of state observer;

The 3.2nd step utilized formula D2 to calculate the error signal measured value of next bat

U wherein _r(k+1) be the reference quantity of next bat:

$\hat{e}(k+1)=u_r(k+1)-{\hat{u}}_0(k+1)---\left(D2\right)$

The 3.3rd step utilized formula D3 to calculate the error intergal signal measured value of next bat

${\hat{e}}_i(k+1)=\hat{e}(k+1)+e_i\left(k\right)---\left(D3\right)$

The 3.4th step utilized formula D4 or formula D5-D6 to calculate the control signal u of next bat ₁(k+1), wherein Filter capacitor electric current measured value for next bat:

$u_1(k+1)=k_i{\hat{e}}_i(k+1)-k_1{\hat{u}}_0(k+1)-k_2{\hat{i}}_1(k+1)---\left(D4\right)$

${\hat{i}}_c(k+1)={\hat{i}}_1(k+1)-i_0\left(k\right)---\left(D5\right)$

$u_1(k+1)=k_i{\hat{e}}_i(k+1)-k_1{\hat{u}}_0(k+1)-k_2{\hat{i}}_c(k+1)---\left(D6\right)$

Wherein, $k_i=\frac{1+{\mathrm{\&beta;}}_2+{\mathrm{\&beta;}}_3+{\mathrm{\&beta;}}_4}{1-{2e}^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T+e^{-\frac{r}{L}T}}$

$k_1=\frac{{\mathrm{\&beta;}}_2-{\mathrm{\&beta;}}_4+1+{2a}_1-e^{-\frac{r}{L}T}-(1-a_1-a_2)k_i}{1-{2a}_1+e^{-\frac{r}{L}T}}$

$k_2=\frac{{\mathrm{\&beta;}}_2+1+{2a}_1-(1-a_1-a_2)(k_1+k_i)}{{2a}_2/r}$

$a_1=e^{-\frac{r}{2L}T}\cos {\mathrm{\&omega;}}_{d}T$

$a_2=\frac{r}{2L{\mathrm{\&omega;}}_d}{e}^{-\frac{r}{2L}T}\sin {\mathrm{\&omega;}}_{d}T;$

β ₂, β ₃And β ₄Be respectively closed-loop pole Z by expectation ₁, Z ₂, Z ₃Characteristic equation (the Z-Z that determines ₁) (Z-Z ₂) (Z-Z ₃)=Z ³+ β ₂Z ²+ β ₃Z+ β ₄In the quadratic term, once and the coefficient of constant term of expansion;

The 4th step was utilized control signal u ₁(k+1) inverter is regulated;

The 5th step made k=k+1, repeated for the 1st step to the 4th step, until end-of-job.

Images