CN1543056A - Motor control device and method - Google Patents
Motor control device and method Download PDFInfo
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- CN1543056A CN1543056A CNA2004100059995A CN200410005999A CN1543056A CN 1543056 A CN1543056 A CN 1543056A CN A2004100059995 A CNA2004100059995 A CN A2004100059995A CN 200410005999 A CN200410005999 A CN 200410005999A CN 1543056 A CN1543056 A CN 1543056A
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- duty ratio
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/14—Electronic commutators
- H02P6/16—Circuit arrangements for detecting position
- H02P6/18—Circuit arrangements for detecting position without separate position detecting elements
- H02P6/182—Circuit arrangements for detecting position without separate position detecting elements using back-emf in windings
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/505—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
- H02M7/515—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
- H02M7/525—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with automatic control of output waveform or frequency
- H02M7/527—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only with automatic control of output waveform or frequency by pulse width modulation
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/08—Arrangements for controlling the speed or torque of a single motor
- H02P6/085—Arrangements for controlling the speed or torque of a single motor in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P2209/00—Indexing scheme relating to controlling arrangements characterised by the waveform of the supplied voltage or current
- H02P2209/09—PWM with fixed limited number of pulses per period
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
- Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10S388/00—Electricity: motor control systems
- Y10S388/907—Specific control circuit element or device
- Y10S388/912—Pulse or frequency counter
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
- Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y10S388/00—Electricity: motor control systems
- Y10S388/923—Specific feedback condition or device
- Y10S388/9281—Counter or back emf, CEMF
Abstract
Provided is an apparatus and a method for controlling a motor which stabilizes the estimation of a rotor position even when a control for lowering the applied voltage to the motor is performed. The apparatus for controlling the motor estimates the position of the rotor (31) based on the induced voltage of non-energizing phase of a brushless DC motor (29) to be driven by an inverter (32), outputs a PWM switching signal pulse-width-modulated based on this estimated result to the inverter (32), and controls the applied voltage to the brushless DC motor (29). When the switching signal having the duty ratio corresponding to the applied voltage is generated, the apparatus includes a controller (34) for regulating the carrier frequency of the PWM switching signal so that the pulse width of the switching signal becomes a predetermined pulse width or more.
Description
Technical field
The present invention relates to motor control assembly and motor control method, particularly the motor control assembly of estimated rotor position and motor control method.
Background technology
In the past, the induced voltage of the non-energising phase of the motor that known basis is driven by inverter comes the position of estimated rotor, according to this estimated result, the switching signal of pulse-width modulation is outputed to inverter, control is to the motor control assembly that applies voltage (for example, with reference to patent documentation 1) of motor.
As above-mentioned motor, known brushless DC motor, its general employing is not provided with the transducer of detection rotor position, and detects the control mode (no transducer control mode) of induced voltage and estimated rotor position.And, in motor control assembly, for example adopt the 120 degree energising rectangular wave drive modes that inverter is controlled, so that the alternating voltage of three-phase is switched on 120 degree on motor, thereby the induced voltage that detection occurs in the nothing energising mutually of the output of inverter comes the position of estimated rotor.
As the parts that come the estimated rotor position according to induced voltage, come more detected induced voltage and reference voltage with the rotor position detection circuit that comprises comparator, the output signal of microcomputer input rotor position detection circuit, the position of estimated rotor.
Induced voltage occurs as the voltage of the pulse type of reply switching signal, in rotor position detection circuit, carries out comparison with reference voltage according to the magnitude of voltage in the conduction period of the voltage of this pulse type.
In this motor control assembly, poor in power status, when being applied to the DC voltage rising on the inverter, or when the revolution of motor descends, in order to reduce the voltage that applies to motor, the carrier frequency that carries out switching signal immobilizes, and shortens the control of the pulse duration of switching signal, promptly reduces the control of the duty ratio of switching signal.
[patent documentation 1]
(Japan) spy opens communique 2002 No. 186274
But, in above-mentioned motor control assembly, in order to reduce the voltage that applies to motor, in the pulse duration that shortens switching signal and when reducing the control of duty ratio, exist the pulse duration of the induced voltage of the pulse type of tackling switching signal also to shorten, when the pulse duration of this induced voltage is too short, can not deal with input and response, problem that can not the estimated rotor position according to the characteristic of rotor position detection circuit.
Summary of the invention
In view of the foregoing, the object of the present invention is to provide a kind of motor control assembly and motor control method,, also can realize the stable estimation of rotor-position even reduce the control that applies voltage to motor.
In order to solve above-mentioned problem, motor control assembly of the present invention comes the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that is driven by inverter, according to this estimated result, the switching signal of pulse-width modulation is outputed to described inverter, control is to the voltage that applies of described motor, it is characterized in that, this motor control assembly comprises the frequency adjustment component, when generation has the described switching signal of the described duty ratio that applies voltage of reply, adjust the carrier frequency of described switching signal, so that the pulse duration of this switching signal is more than the pulse duration of regulation.
In addition, motor control assembly of the present invention comes the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that is driven by inverter, according to this estimated result, the switching signal of pulse-width modulation is outputed to described inverter, control is to the voltage that applies of described motor, it is characterized in that this motor control assembly comprises: set parts, setting threshold in the duty ratio of described switching signal; And frequency adjustment component, when generation has the described switching signal of the described duty ratio that applies voltage of reply, adjust the carrier frequency of described switching signal, so that be lower than under the situation of described threshold value at the duty ratio of this switching signal, the pulse duration of this switching signal is more than the pulse duration of regulation.
In this case, described set parts can be fixed and pulse duration under adjusting the pulse duration situation of described switching signal is set described threshold value in for the duty ratio scope more than the pulse duration of regulation at the carrier frequency that makes described switching signal.
In addition, described frequency adjustment component can make described carrier frequency descend continuously along with the decline of described duty ratio.
And described frequency adjustment component can make described carrier frequency, and classification descends along with the decline of described duty ratio.
In addition, described frequency adjustment component can have magnetic hysteresis, so as described carrier frequency from the 1st frequency change during to than low the 2nd frequency of the 1st frequency the time and from described the 2nd frequency change to described the 1st frequency duty ratio different.
Motor control method of the present invention comes the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that is driven by inverter, according to this estimated result, the switching signal of pulse-width modulation is outputed to described inverter, control is to the voltage that applies of described motor, it is characterized in that, when generation has the described switching signal of the described duty ratio that applies voltage of reply, adjust the carrier frequency of described switching signal, so that the pulse duration of this switching signal is more than the pulse duration of regulation.
Motor control method of the present invention comes the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that is driven by inverter, according to this estimated result, the switching signal of pulse-width modulation is outputed to described inverter, control is to the voltage that applies of described motor, it is characterized in that: setting threshold in the duty ratio of described switching signal, when generation has the described switching signal of the described duty ratio that applies voltage of reply, duty ratio in this switching signal is lower than under the situation of described threshold value, adjust described carrier frequency, so that the pulse duration of this switching signal is more than the pulse duration of regulation.
Description of drawings
Fig. 1 is the circuit diagram of the 1st execution mode of expression motor control assembly of the present invention.
Fig. 2 is the refrigerant loop figure of air conditioner of the compressor of the expression motor of being furnished with Fig. 1 built-in.
Fig. 3 is the exemplary waveforms figure of phase voltage of the input terminal of expression motor, and Fig. 3 (a) is the U phase voltage waveform, and Fig. 3 (b) is the V phase voltage waveform, and Fig. 3 (c) is the W phase voltage waveform, and Fig. 3 (d) is the induction voltage waveform of three-phase.
Fig. 4 is that the carrier frequency of the reply duty ratio of expression the 1st execution mode reaches the key diagram that applies voltage to motor.
Fig. 5 is the key diagram of carrier frequency of the reply duty ratio of expression the 2nd execution mode.
Fig. 6 is the key diagram of expression as the carrier frequency of the reply duty ratio of variation.
Embodiment
Below, embodiments of the present invention are described with reference to the accompanying drawings.
[1] the 1st execution mode
Fig. 1 is the circuit diagram of the 1st execution mode of expression motor control assembly of the present invention.Fig. 2 is the refrigerant loop figure of air conditioner of the compressor of the expression motor of being furnished with Fig. 1 built-in.
As shown in Figure 2, air conditioner 10 has off-premises station 11 and indoor set 12, and the outdoor refrigerant pipe arrangement 14 of off-premises station 11 and the indoor refrigerant piping 15 of indoor set 12 link by linking pipe arrangement 24,25.
Off-premises station 11 is configured in outdoor.In outdoor refrigerant pipe arrangement 14, set compressor 16, simultaneously set accumulator 17, set cross valve 18, set outdoor heat converter 19 in these cross valve 18 sides in the discharge side of compressor 16 in the suction side of this compressor 16.In outdoor heat converter 19, will be from outdoor heat converter 19 to outdoor repeatedly outdoor fan 20 disposed adjacent of wind.This outdoor fan 20 is driven by indoor fan motor 20A.This outdoor fan 20 for example is the propeller fan.Compressor 16 is inverter driving ejector half compressors.In this compressor 16, built-in conduct is by the brushless DC motor 29 of the motor of inverter driving.
Indoor set 12 is set at indoor, sets indoor heat converter 21 and electric expansion valve 22 on indoor refrigerant piping 15 successively.On this indoor heat converter 21, will be from indoor fan 23 disposed adjacent of indoor heat converter 21 to indoor air-supply.This indoor fan 23 is driven by indoor fan motor 23A.This indoor fan 23 for example is cross flow one (Network ロ ス Off ロ an one) fan.
By switching the cross valve 18 of off-premises station 11, air conditioner 10 is set at cooling operation or warming operation.That is, when cross valve 18 being switched to the refrigeration side, cold-producing medium is mobile as the solid line arrow, and outdoor heat converter 19 becomes condenser, and indoor heat converter 21 becomes evaporator and becomes cooling operation state, 21 pairs of indoor refrigeration of the indoor heat converter of indoor set 12.And when cross valve 18 being switched to the heating side, cold-producing medium is mobile as dotted arrow, and indoor heat converter 21 becomes condenser, and outdoor heat converter 19 becomes evaporator and becomes warming operation state, 21 pairs of indoor heatings of the indoor heat converter of indoor set 12.
As shown in Figure 1, the brushless DC motor 29 that is built in the above-mentioned compressor 16 is three phase electric machines, and the stator 30 of being furnished with stator winding 30u, 30v and 30w is arranged, and the rotor 31 of being furnished with permanent magnet.This brushless DC motor 29 is driven by the motor control assembly 100 of being furnished with the control part 34 that inverter 32, rotor position detection circuit 33 and microcomputer constitute.Usually, the brushless DC motor 29 of compressor 16 carries out revolution control according to the air-conditioning load.
Above-mentioned inverter 32 for example is that transistor 38u, 38v, 38w, 38x, 38y and 38z as 6 switch elements are carried out the inverter that three phase bridge connects.Between each emitter terminal 39 and each collector terminal 40 of these transistors 38u, 38v, 38w, 38x, 38y and 38z, connect fly-wheel diode 42.
And inverter 32 moves by each base terminal 41 that will be input to transistor 38u, 38v, 38w, 38x, 38y, 38z from the switching signal (hereinafter referred to as ' pwm switching signal ') of the pulse-width modulation of PWM (Pulse Width Modulation) terminal 35 output of control part 34.
Action by this inverter 32, conversion the direct current power of alternating electromotive force of AC power (not shown) three-phase ac power of pulse-width modulation that has been transformed into acceptance with fixed frequency and voltage, to stator winding 30u, the 30v of brushless DC motor 29, alternating voltage Vu, Vv, the Vw that 30w applies three-phase.Here, Vu represents the U phase voltage, and Vv represents the V phase voltage, and Vw represents the W phase voltage.
In the present embodiment, motor control assembly 100 drives brushless DC motor 29 in the 120 degree energising rectangular wave drive modes that inverter 32 is controlled, so that the alternating voltage of three-phase is switched on 120 degree in brushless DC motor 29.
Here, transistor 38u, 38v and 38w are called the upper arm transistor group of inverter 32, transistor 38x, 38y and 38z are called the underarm transistor group of inverter 32.And it is right that transistor 38u and 38x, transistor 38v and 38y, transistor 38w and 38z form respectively, and tie point separately is connected respectively to stator winding 30u, 30v, the 30w of the brushless DC motor 29 of Y-connection.
The induced voltage of the nothing energising phase of the input terminal voltage of rotor position detection circuit 33 detection brushless DC motors 29 outputs to control part 34 with the signal of representing rotor 31 positions.
This rotor position detection circuit 33 is furnished with comparator 51 and photoelectrical coupler 52.The input terminal 51a of comparator 51 is connected to U phase, the V phase of brushless DC motor 29, the input terminal (lead-out terminal of the U phase of inverter 32, V phase, W phase) of W phase by each resistance 53,54,55.In addition, on input terminal 51b, connect the reference voltage power supply 56 of the reference voltage V ref that generates direct current.The lead-out terminal 51c of comparator 51 is connected to the input terminal 52a of photoelectrical coupler 52 by resistance 57, and the lead-out terminal 52b of photoelectrical coupler 52 is connected to the input terminal 36 of control part 34.
In addition, control part 34 is obtained the phase place that respectively applies voltage mutually that be applied on the brushless DC motor 29 according to the position of coming estimated rotor from the output signal of rotor position detection circuit 33 according to this estimated result.
Then, control part 34 is according to the duty ratio of the frequency of obtaining that applies voltage, pwm switching signal and apply the phase place of voltage, generates pwm switching signal, outputs to inverter 32 by PWM terminal 35.
Fig. 3 is the exemplary waveforms figure of phase voltage of the input terminal of expression brushless DC motor 29.Fig. 3 (a) is the U phase voltage waveform, and Fig. 3 (b) is the V phase voltage waveform, and Fig. 3 (c) is the W phase voltage waveform, and Fig. 3 (d) is the induction voltage waveform of three-phase.
For example, with reference to Fig. 3 (a) when illustrating, in the one-period of U phase voltage Vu, be provided with pwm switching signal and be imported into inverter 32, apply Ta, Tc during the energising of 120 degree electrical degrees of voltage on the brushless DC motor 29, and pwm switching signal is not input to inverter 32 and becomes Tb, Td during the nothings energising of the 60 degree electrical degrees of not having the energising phase.During having energising, these among Ta, the Td, do not produce the induced voltage of the position of reply rotor 31.Shown in Fig. 3 (b), V phase voltage Vv compares its phase deviation 120 degree with U phase voltage Vu, and shown in Fig. 3 (c), W phase voltage Vw compares its phase deviation 120 degree with V phase voltage Vv.And the induced voltage that three-phase adds up to, the voltage waveform that promptly produces on the input terminal 51a of the comparator 51 of rotor position detection circuit 33 are the triangular wave of pulse type shown in Fig. 3 (d).
Output to the carrier frequency of pwm switching signal of inverter 32 and pulse duration and roughly the same as the frequency and the pulse duration of the pulse-like voltage of induced voltage performance from control part 34.Therefore, if the carrier frequency varies of pwm switching signal, then the frequency as the pulse-like voltage of induced voltage performance changes similarly, if the pulse width variation of pwm switching signal, then the pulse duration of induced voltage changes similarly.For example, if the pulse duration of pwm switching signal shortens, then the pulse duration of induced voltage shortens similarly.
If the pulse duration of the pulse duration of input ratio regulation (for example, 5[μ s]) short, the rotor position detection circuit 33 that then has comparator 51 and photoelectrical coupler 52 can not be followed the tracks of the input signal of input terminal 51a because of the response characteristic of circuit.That is, if the input signal of input terminal 51a, be that the pulse duration of pwm switching signal is shorter than the pulse duration (for example, 5[μ s]) of regulation, then rotor position detection circuit 33 can not respond input, the output signal instability.Therefore, with regard to control part 34 position of estimated rotor 31 correctly, must be more than the pulse duration of regulation (for example, 5[μ s]) to the input signal (pulse) of this rotor position detection circuit 33.
In the present embodiment, control part 34 is adjusted the carrier frequency of pwm switching signal, so that when generation has the pwm switching signal of the pulse duration that applies voltage of reply brushless DC motor 29, the duty ratio of pwm switching signal is more than the pulse duration of regulation (for example, 5[μ s]).
Specifically, when the key diagram that applies voltage of the carrier frequency of the reply duty ratio that reference is shown in Figure 4 and expression brushless DC motor 29 described, at first, control part 34 is setting threshold A in the duty ratio of pwm switching signal.
Here, threshold value A being set in the carrier frequency B that makes pwm switching signal fixes (for example, 5[kHz]) and adjusts in the above duty ratio scope of the pulse duration that pulse duration under the pulse duration situation of pwm switching signal reaches regulation (for example, 5[μ s]).
For example, be 5[kHz at the carrier frequency B of pwm switching signal], the duty ratio of pwm switching signal is 5[%] time because pulse duration is 10[μ s], so threshold value A for example is set at 5[%].
Then, control part 34 is adjusted carrier frequency B, so that when generation has the pwm switching signal of the duty ratio that applies voltage (line voltage or phase voltage) C of tackling brushless DC motor 29, when the duty ratio of pwm switching signal is lower than threshold value A, the pulse duration that prevents pwm switching signal than the pulse duration of regulation (for example, 5[μ s]) short, can reach more than the pulse duration of regulation.
More particularly, control part 34 descends carrier frequency B along with the decline of duty ratio continuously, so that when generation has the pwm switching signal of the duty ratio that applies voltage (line voltage or phase voltage) C of tackling brushless DC motor 29, duty ratio at pwm switching signal (for example is lower than threshold value A, 5[%]) time, promptly than threshold value A (for example at the duty ratio of the pwm switching signal that generates, 5[%]) in the little duty ratio scope X time, the pulse duration that prevents pwm switching signal than the pulse duration of regulation (for example, 5[μ s]) short, can reach more than the pulse duration of regulation.
For example, when control part 34 is lower than threshold value A at the duty ratio of the pwm switching signal that generates, the pulse duration of pwm switching signal (for example is fixed on the above pulse duration of the pulse duration (for example, 5[μ s]) of regulation, 10[μ s]), along with the decline of duty ratio descends carrier frequency B continuously.At this moment, fixing pulse duration can be set for duty ratio is the pulse duration same widths of threshold value A (for example, 5[%]).
Here, even same duty ratio, if carrier frequency B descends, then the pulse duration of pwm switching signal is also elongated.For example, in that to generate duty ratio be 5[%] pwm switching signal the time, be 5[kHz at carrier frequency B '] time, pulse duration is 10[μ s].At carrier frequency B ' is 2.5[kHz] time pulse width be 20[μ s].That is, along with the decline of carrier frequency B ', the pulse duration of pwm switching signal is elongated.
Therefore, according to this 1st execution mode, during DC voltage rising that control part 34 applies on inverter 32, or when reducing the revolution of brushless DC motor 29, in order to reduce the voltage that applies to brushless DC motor 29, control to when being lower than threshold value A at duty ratio pwm switching signal, the pulse duration of input signal that expression is input to the induced voltage of rotor position detection circuit 33 is not less than the pulse duration of regulation, even, also can stablize the estimated rotor position so reduce the control that applies voltage to brushless DC motor 29.
In addition, when control part 34 has the pwm switching signal of the duty ratio that applies voltage C of tackling brushless DC motor 29 in generation, duty ratio at pwm switching signal (for example surpasses threshold value A, 5[%]) time, promptly when the duty ratio of the pwm switching signal that generates is in than the big duty ratio scope Y of threshold value A (for example, 5[%]), because the pulse duration of switching signal unlike the pulse duration of stipulating (for example, 5[μ s]) short, institute is so that carrier frequency B fixes (for example, 5[kHz]).
Here, control part 34 is controlled, so that when driving brushless DC motor 29, revolution is not 0.That is, control part 34 is for fear of applying voltage at 0[V] near, be provided with the minimum voltage that applies that on brushless DC motor 29, applies, when driving brushless DC motor 29, control, so that be not less than this minimum voltage that applies.Therefore, be not 0[V owing to apply voltage] or at 0[V] near, descend to heavens so prevent carrier frequency.Therefore, can stablize the estimated rotor position.
[2] the 2nd execution modes
In above-mentioned the 1st execution mode, the situation that control part 34 descends carrier frequency B along with the decline of duty ratio continuously has been described, and in this 2nd execution mode, control part makes along with the decline of duty ratio carrier frequency be classified to descend.Have, the formation of system is identical with Fig. 1 and Fig. 2 of the 1st execution mode again, thereby omits explanation.
Fig. 5 is the key diagram of the carrier frequency of expression reply duty ratio.
At first, same with Fig. 4 of the 1st execution mode, control part 34 is pressed the duty ratio setting threshold A (for example, 5[%]) of pwm switching signal.
Then, control part 34 makes carrier frequency B ' be classified to descend along with the decline of duty ratio, so that when generation has the pwm switching signal of the duty ratio that applies voltage (line voltage or phase voltage) C of tackling brushless DC motor 29, when the duty ratio of pwm switching signal is lower than threshold value A, promptly than threshold value A (for example at the duty ratio of the pwm switching signal that generates, 5[%]) in the little duty ratio scope X time, the pulse duration that prevents pwm switching signal than the pulse duration of regulation (for example, 5[μ s]) short, can reach more than the pulse duration of regulation.
Specifically, control part 34 makes carrier frequency B ' be classified to along with the decline of duty ratio descend, and drops to the 2nd frequency B2 lower than the 1st frequency B1 (for example, 2.5[kHz]) from the 1st frequency B1 (for example, 5[kHz]).For example, when the duty ratio of pwm switching signal is lower than threshold value A, be the boundary with this threshold value A, carrier frequency B ' is dropped to the 2nd frequency B2 lower than the 1st frequency B1 (for example, 2.5[kHz]) from the 1st frequency B1 (for example, 5[kHz]).
Therefore, during the DC voltage rising that on inverter 32, applies, or when reducing the revolution of brushless DC motor 29, in order to reduce the voltage that applies to brushless DC motor 29, control to when being lower than threshold value A at duty ratio pwm switching signal, by being classified to reduce carrier frequency B ', thereby the pulse duration of pwm switching signal increases, the pulse duration of input signal that expression is input to the induced voltage of rotor position detection circuit 33 is not less than the pulse duration of regulation, even, also can stablize the estimated rotor position so reduce the control that applies voltage to brushless DC motor 29.
Here, control part 34 has magnetic hysteresis (differential) Δ and controls, so as carrier frequency B ' from the 1st frequency change to than low the 2nd frequency B2 of the 1st frequency B1 the time, and when the 2nd frequency B2 changes to the 1st frequency all differences of duty ratio.
Specifically, control part 34 has the magnetic hysteresis Δ and controls, so that the duty ratio A when the 1st frequency B1 changes to the 2nd frequency B2 is lower than the duty ratio A ' that changes to the 1st frequency B1 from the 2nd frequency B2.
Thus, in the border that carrier frequency B ' classification is switched, prevent to produce swing.Thus, can more stable estimated rotor position.
At this moment, set the magnetic hysteresis Δ of duty ratio A and duty ratio A ', so that apply voltage (line voltage or phase voltage) during with respect to duty ratio A, the voltage that applies during duty ratio A ' reaches the specified multiple (for example, 1.5 times) that does not cause swing.
In addition, reach 0[V for fear of applying voltage] near, the minimum voltage that applies that is applied on the brushless DC motor 29 is set, when driving brushless DC motor 29, control, so that be not less than this minimum voltage that applies, so pulse duration does not shorten terrifically, can stablize the estimated rotor position.
In the above description, as the control that carrier frequency B ' is dropped to the 2nd frequency B2 lower from the 1st frequency B1 classification along with the decline of duty ratio than the 1st frequency B1, illustrated with the threshold value A to be the boundary, with carrier frequency B ' from only the descend situation of the 2nd frequency B2 of one-level of the 1st frequency B, but it is for example shown in Figure 6, can be the boundary also, its multistage along with the decline of duty ratio (for example, two-stage) is descended by threshold value A.In this case, in Fig. 6, reduce duty ratio A " situation under, carrier frequency B ' drops to frequency B3 from frequency B2, and this moment, B2 was the 1st frequency, B3 is the 2nd frequency.And, also can have magnetic hysteresis and control, so that the duty ratio A when the 1st frequency B2 changes to the 2nd frequency B3 " lower than the duty ratio A that changes to the 1st frequency B2 from the 2nd frequency B3.
In addition, in the above description, the situation of the motor of motor control assembly Driven Compressor has been described, but as long as come the estimated rotor position according to induced voltage under no transducer control mode, which kind of motor can adopt all.For example, can under situations such as driving outdoor fan motor and indoor fan motor, adopt.
According to the present invention, even reduce the control that applies voltage, the position that also can stablize estimated rotor to motor.
Claims (8)
1. motor control assembly, come the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that drives by inverter, according to this estimated result, the switching signal of pulse-width modulation is outputed to described inverter, control is to the voltage that applies of described motor, it is characterized in that this motor control assembly comprises:
The frequency adjustment component when generation has the described switching signal of the described duty ratio that applies voltage of reply, is adjusted the carrier frequency of described switching signal, so that the pulse duration of this switching signal is more than the pulse duration of regulation.
2. motor control assembly, come the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that drives by inverter, according to this estimated result, the switching signal of pulse-width modulation is outputed to described inverter, control is to the voltage that applies of described motor, it is characterized in that this motor control assembly comprises:
Set parts, setting threshold in the duty ratio of described switching signal; And
The frequency adjustment component, when generation has the described switching signal of the described duty ratio that applies voltage of reply, adjust the carrier frequency of described switching signal, so that be lower than under the situation of described threshold value at the duty ratio of this switching signal, the pulse duration of this switching signal is more than the pulse duration of regulation.
3. motor control assembly as claimed in claim 2 is characterized in that:
Described set parts is fixed and pulse duration under adjusting the pulse duration situation of described switching signal is set described threshold value in for the duty ratio scope more than the pulse duration of regulation at the carrier frequency that makes described switching signal.
4. as any one described motor control assembly of claim 1 to 3, it is characterized in that:
Described frequency adjustment component makes described carrier frequency descend continuously along with the decline of described duty ratio.
5. as any one described motor control assembly of claim 1 to 3, it is characterized in that:
Described frequency adjustment component makes described carrier frequency, and classification descends along with the decline of described duty ratio.
6. motor control assembly as claimed in claim 5 is characterized in that:
Described frequency adjustment component has magnetic hysteresis, so as described carrier frequency from the 1st frequency change during to than low the 2nd frequency of the 1st frequency the time and from described the 2nd frequency change to described the 1st frequency duty ratio different.
7. motor control method, come the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that drives by inverter,, the switching signal of pulse-width modulation is outputed to described inverter according to this estimated result, control is characterized in that the voltage that applies of described motor:
When generation has the described switching signal of the described duty ratio that applies voltage of reply, adjust the carrier frequency of described switching signal, so that the pulse duration of this switching signal is more than the pulse duration of regulation.
8. motor control method, come the position of estimated rotor according to the induced voltage of the non-energising phase of the motor that drives by inverter,, the switching signal of pulse-width modulation is outputed to described inverter according to this estimated result, control is characterized in that the voltage that applies of described motor:
Setting threshold in the duty ratio of described switching signal, when generation has the described switching signal of the described duty ratio that applies voltage of reply, duty ratio in this switching signal is lower than under the situation of described threshold value, adjust described carrier frequency, so that the pulse duration of this switching signal is more than the pulse duration of regulation.
Applications Claiming Priority (3)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP048699/03 | 2003-02-26 | ||
| JP048699/2003 | 2003-02-26 | ||
| JP2003048699A JP4197974B2 (en) | 2003-02-26 | 2003-02-26 | Motor control device and motor control method |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN1543056A true CN1543056A (en) | 2004-11-03 |
| CN1282300C CN1282300C (en) | 2006-10-25 |
Family
ID=33114591
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CNB2004100059995A Expired - Fee Related CN1282300C (en) | 2003-02-26 | 2004-02-24 | Motor control device and method |
Country Status (3)
| Country | Link |
|---|---|
| JP (1) | JP4197974B2 (en) |
| KR (1) | KR20040076789A (en) |
| CN (1) | CN1282300C (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101233676B (en) * | 2005-08-26 | 2011-05-11 | 罗姆股份有限公司 | Motor driven unit, motor drive method and cooling apparatus using the unit |
| CN103023395A (en) * | 2011-09-20 | 2013-04-03 | 日立汽车系统株式会社 | Brushless motor drive device |
| CN101584110B (en) * | 2007-01-19 | 2013-08-28 | 因勒纪汽车系统研究公司 | Method and system for controlling operation of pump |
| CN104359184A (en) * | 2014-09-30 | 2015-02-18 | 海信科龙电器股份有限公司 | Carrier frequency conversion control method and controller |
Families Citing this family (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR100904426B1 (en) | 2007-09-11 | 2009-06-26 | 주식회사 하이닉스반도체 | Circuit of internal voltage generation |
| JP5496517B2 (en) * | 2008-03-26 | 2014-05-21 | 株式会社ミツバ | Motor control circuit |
| JP5772029B2 (en) * | 2011-02-08 | 2015-09-02 | アイシン精機株式会社 | Sensorless brushless motor drive device |
| JP7296913B2 (en) * | 2020-04-10 | 2023-06-23 | 三菱電機株式会社 | pulse width modulation controller |
-
2003
- 2003-02-26 JP JP2003048699A patent/JP4197974B2/en not_active Expired - Fee Related
-
2004
- 2004-02-24 CN CNB2004100059995A patent/CN1282300C/en not_active Expired - Fee Related
- 2004-02-25 KR KR1020040012449A patent/KR20040076789A/en not_active Application Discontinuation
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101233676B (en) * | 2005-08-26 | 2011-05-11 | 罗姆股份有限公司 | Motor driven unit, motor drive method and cooling apparatus using the unit |
| CN101584110B (en) * | 2007-01-19 | 2013-08-28 | 因勒纪汽车系统研究公司 | Method and system for controlling operation of pump |
| CN103023395A (en) * | 2011-09-20 | 2013-04-03 | 日立汽车系统株式会社 | Brushless motor drive device |
| CN104359184A (en) * | 2014-09-30 | 2015-02-18 | 海信科龙电器股份有限公司 | Carrier frequency conversion control method and controller |
| CN104359184B (en) * | 2014-09-30 | 2017-02-15 | 海信科龙电器股份有限公司 | Carrier frequency conversion control method and controller |
Also Published As
| Publication number | Publication date |
|---|---|
| JP2004260919A (en) | 2004-09-16 |
| KR20040076789A (en) | 2004-09-03 |
| JP4197974B2 (en) | 2008-12-17 |
| CN1282300C (en) | 2006-10-25 |
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