CN1470089A - 对多反射面天线的电磁波的发射/接收源的改进 - Google Patents
对多反射面天线的电磁波的发射/接收源的改进 Download PDFInfo
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Abstract
本发明涉及一种卡塞格伦型多反射面天线的电磁波发射/接收源,该天线包括在第一频带工作的纵向辐射装置(12)和在第二频带工作的n个行波型的辐射元件(11)的阵列,n个辐射元件对称地布置在纵向辐射装置的周围,阵列和纵向辐射装置有近似一致的相位中心,其特征在于n个辐射元件的阵列由多边形横截面的波导来激励。该发明特别应用于在C频带、Ku频带、Ka频带工作的卫星通信系统。
Description
技术领域
本发明涉及一种发射(T)/接收(R)源天线,以后称为T/R源,它可被放置于天线系统的焦点,更为明确的是放在卡塞格伦双反射面天线的焦点上。这种T/R源的一个可能应用是在使用C频带、Ku频带、Ka频带的卫星通信系统中。
背景技术
在2000年6月9日以Thomson Multimedia的名义提出的、标题为“Perfectionnement aux antennes-source d’émission/réception d’ondesélectromagnétiques”[对电磁波的发射/接收源天线的改进]的法国专利申请00/07424已经提出了一种混合T/R源,它由螺旋体阵列组成,由印制馈电电路激励该螺旋体阵列,该阵列围绕纵向辐射天线,例如螺旋体或者“聚苯乙烯棒(polyrod)”。
为了使发射源和接收源间的交互作用最小化,使用螺旋体阵列来接收和使用纵向辐射源来发射是有利的。然而,在接收时,印制馈电电路的损耗在链路估算具有双重效果。这是因为减小了天线指标G/T比,因为,一方面天线增益G的减小,而另一方面由于馈电电路的消耗损失导致的噪声温度T的增加。从这个观点来说,专利申请00/07424提出的解决方案能够使用螺旋体阵列,更好的是使用贴片(patch)阵列来提高天线的G/T比。
而且,在法国专利申请00/07424中,在基板上蚀刻有螺旋体的印制馈电电路,基板包含天线的接收电路,并且它垂直于螺旋体的辐射轴放置。这样,在卡塞格伦结构中,为了避免由低噪声阻塞(LNB)产生的阻塞,需要把双反射面系统的焦点放在主反射面的顶点。这种对卡塞格伦系统在几何上的约束需要使用非常有方向性的源,这样的源有增加天线系统旁瓣电平的效果。
如以图形的方式显示了包括主反射面1、源2和面对源2的辅反射面3的卡塞格伦结构的图1所示,这是因为旁瓣主要产生于:i)辅反射面3的衍射。衍射后的能量有一个以分贝(dB)表示等于(G-Edge)的绝对电平。G是基本上由它的方向性定义的主要源的增益。对于双反射面系统的最优化运行,边缘(Edge)大约是20dB。由衍射导致的旁瓣电平大约为(G-Edge)的值;ii)由同样的源2辐射的旁瓣I,它不与辅反射面3相交。如果主要源有以分贝表示的旁瓣电平SLL,则由主要源的旁瓣导致的天线系统旁瓣的绝对电平等于(G-SLL)。
减少卡塞格伦系统的旁瓣的一种方法是降低G。可是,如图2所示,为了降低G和保持最优化的边缘(Edge)值(大约为20dB),天线系统的焦点2′必须位于主反射面1和辅反射面3之间。
本发明的目的是通过提供T/R源结构来补救这个问题,该结构的相位中心在主反射面和辅反射面之间,在双反射面天线系统的运行中不会导致阻塞。这样,它就可能减小天线系统的旁瓣。
此外,降低主要源的旁瓣电平(SLL)同时使天线系统的旁瓣被减小。
本发明也提出了一种新颖的T/R源结构,该结构使得发射/接收源的旁瓣被减小。
此外,与基于均匀透镜的聚焦系统相反,双反射面天线系统有精确定义的焦点,同时,对于T/R源,需要它们的相位中心完全一致。
这样,本发明也提出了一种T/R源结构,该结构使得发射和接收源的相位中心完全一致。
发明内容
本发明的主题是一种卡塞格伦型多反射面天线的电磁波发射/接收(T/R)源,该天线包括在第一频带工作的纵向辐射装置和在第二频带工作的n个行波型辐射元件的阵列,n个辐射元件对称地布置在纵向辐射装置的周围,该阵列和纵向辐射装置有近似公共的相位中心,其特征在于n个辐射元件的阵列由矩形横截面的波导来激励。
根据一个实施例,n个辐射元件的阵列是圆形阵列,并且波导形成了“菠萝片”形状的空腔。在这种情况下,波导具有的尺寸如下,其中D是圆形阵列的平均直径:
D=nλg/2,其中n表示辐射元件的个数,λg表示导波在工作频率时的波长。
λg=λ0[εr-(λ0/λc)2]-1/2,其中,λc是对于TE01基本模式的矩形波导的截止波长,λ0是在真空中的波长,εr是填充波导的电介质的介电常数;和
λc=2a(εr)1/2,其中a是矩形波导的宽度。
为了获得源的良好方向性,把D选择为1.3λ0<D<1.9λ0。
连接在接收电路上(低噪声放大器(LNA),混频器)的探针通过同轴电缆激励以上的矩形波导。
而且,对于发射,纵向辐射天线可以或者由圆形或矩形波导激励的聚苯乙烯棒形成,或者由同轴电缆激励的长螺旋体形成,所说的螺旋体位于阵列的中心,它具有一种后空腔,这可能会:
1)减小纵向辐射天线的旁瓣和后瓣;
2)使发射源和接收源的相位中心一致;和
3)改善发射源和接收源之间在隔离方面的性能。
最后,为了减小螺旋体阵列的旁瓣,另一个圆锥形的空腔围绕所说的阵列。
附图说明
通过阅读以下给出的不同实例描述,本发明更进一步的特定和优点将会变得明显。该描述参照附图给出,其中:
图1是依照先前的技术卡塞格伦系统的图形表示,它已经被描述过;
图2是与图1相对应的图形表示,解释了本发明打算解决的问题中的一个,它也已经被描述过。
图3是依照本发明,包括源的卡塞格伦系统的图形表示;
图4a和图4b依照本发明分别显示了一个实施例的源系统剖视和俯视图。
图5是在图4的系统中使用的螺旋体的详细剖视图。
图6是给出了矩形波导耦合到螺旋体的结果作为频率函数的曲线。
图7是与图4a一样的视图,显示了为仿真提出的系统。
图8、图9和图10是给出了图7的源系统执行的仿真结果曲线。
图11显示了依照本发明的源系统的另一个实例。
为了简化问题,同样的元件在图中采用同样的参考数字。
具体实施方式
参照图3到图11,现在将描述本发明的不同实施例。
图3图示了构成本发明的主题的T/R源10的剖视图,T/R源被放置在双反射面天线系统的焦点,该天线系统位于两个反射面1和3之间。
发射/接收源天线构成了本发明的主题,与较传统的使用波导技术的方法比较,它受益于以下优势,即:
减小了的尺寸,减少了的重量和降低了的花费,同时由于两个信道间的物理隔离使得在发射和接收信道间有好的电隔离。
此外,与在法国专利申请00/07424中描述的进行比较,得出:
i)使得由螺旋体阵列组成的源的损耗进一步降低,这是由于它使用单模的矩形波导使馈电电路具有非常低的损耗,该损耗已知为最小的损耗,同时它的长度平均减小到圆形阵列直径的一半;
ii)对于卡塞格伦型双反射天线非常高旁瓣的问题它提出了低成本的解决方法:通过使混合源系统的相位中心放置在主反射面和辅反射面之间;和
通过减小主要发射和接收源的旁瓣;
iii)它使得发射和接收源的相位中心完全一致,这样使主要源在发射和接收中都被最优化地定位。
参照图4到图10,现在将更详细地描述本发明优选的实施例。
图4a和图4b分别显示了构成本发明主题的源系统的剖视图和俯视图。在这个特定的情况下:
行波型的n个辐射元件的阵列由8个螺旋体11组成。它们被放置在直径为D的圆的圆周上,并在第二频带工作。它们安装在“菠萝片”状波导15的上面15a上;
位于阵列中间的纵向辐射天线是“聚苯乙烯棒”12。
如图4a和图7所示,后空腔13和14是圆锥形的,它们用来减少在“聚苯乙烯棒”和螺旋体阵列两个情况下旁瓣的辐射。
同轴电缆16激励形状为“菠萝片”的矩形波导15。辐射螺旋体11通过探针17反过来耦合到矩形波导的空腔。
对于螺旋体的最优化激励,该螺旋体放置在最大场平面(即开路平面)中波导横截面的中间。
图5显示了在12GHz激励的螺旋体11的细节和尺寸,螺旋体装在多边形模截面的波导15的上面,更明确的是具有尺寸a和b的矩形横截面的上面。
图6a给出了仿真,仿真显示了依照本发明矩形波导耦合到螺旋体的结果,和在12GHz中心频率时,在对于端口A1(图6a)的4个螺旋体(如11-2、11-3、11-4、11-5)情况下,波导空腔的适配。
这样,矩形波导15的尺寸如下:
(I)(在阵列由8个螺旋体11组成的情况下;λg在工作频率时导波的波长;
λc=2a(εr)1/2,a是矩形波导的宽度;
εr=填充波导的电介质的介电常数;
而且为了辅反射面的最优化照射,主源的方向性在-20分贝时在+/-20°和+/-30°之间变化。对于平均直径D得到这些方向性的值,这样:
(III);λ0是在真空中的波长。
对于由源的方向性固定的D,使用等式(I)和(II)来推导λg和λ0之间的关系。通过考虑等式(II)中的这个关系,从中可以推导出a的值。为了最小化矩形波导的损耗,选择矩形波导的高度b等于它的宽度的一半,例如b是a/2。
总之,为了减小损耗和成本,把波导选择为空(εr=1)。可是,如果波导是非常宽的,或者如果需要在中间清除较多的空间来定位聚苯乙烯棒12和它的后空腔13,在波导中填充介电常数εr>1的电介质就足够了。波导的宽度以因数(εr)-1/2来减少。
在度量外部空腔的尺寸时,调整参数Δ、α和h来减小螺旋体阵列的旁瓣。
在内部空腔13的情况下,通过矩形波导15的尺寸给出了直径dc,更明确的是通过它的宽度a来给出。如图7所示,这样的深度d使得“聚苯乙烯”棒12的相位中心FP(它位于聚苯乙烯棒长度的1/3处)与螺旋体阵列11的相位中心FH一致(即,在螺旋体阵列的中间和螺旋体长度的1/3处)。这样,参考图7,从位于深度为d的圆锥体空腔底面上的中心的原点出发,点FP位于大约LP/3的高度,其中LP是从圆点测量的聚苯乙烯棒12的总长度。为了使相位中心一致,点FH必须和FP在同一高度上,这对应于等式:
d+LH/3=LP/3,即,d=(LP-LH)/3;
其中,LH是每一个螺旋体11的长度。
那些精于此项技术的人已知的传统公式给出了以纵向模式在中心频率工作的每个螺旋体11的尺寸和作为期望方向性的函数的中间介质的尺寸。
最后,可以修改中间的聚苯乙烯棒的后空腔的形状。因此,除了圆锥的形状13,后空腔可以有圆柱的或者相似的形状。
图7显示了构成本发明主题的发射/接收源的一个特定实施例。发射部分由介质天线12形成,并在14GHz到14.5GHz频带工作。接收部分在11.7GHz到12.5GHz频带工作,它由8个螺旋体11的阵列形成,螺旋体位于直径D=42 mm的圆上,即,大约1.7λ0,其中λ0表示在接收频带的中心频率的真空波长,即,λ0=24.7mm。
对于该实例,首先,已优化了介质天线12的形状,已仿真了三种类型的内部空腔(即圆柱空腔,有陷波器的圆柱空腔,和圆锥形空腔),它们都具有深度d=30mm(即,大约(LP-LH)/3=(110-30)/3=26.6mm),这样使两个源的相位中心一致。对于这种配置,圆锥形的空腔给出了最好的结果。图8给出了在指定的频带(14GHz到14.5GHz)螺旋体的适配和在空腔面前得到的辐射模式。
然后对于螺旋体的旁瓣优化外部圆锥形空腔14的角度α和高度h。α=45°和h=25mm是得到的最佳结果。图9显示了仿真适配曲线和对于这些α和h得到的辐射模式的结果。可以注意到在外部空腔面前的旁瓣级别的显著减小。
最后,图10显示了八个螺旋体阵列的辐射模式,所有的螺旋体长度为30mm并在直径D=42mm,即大约1.7λ0的圆上均匀地分开,其中表示在接收频带的中心频率真空中的波长。
由外部空腔优化接收源的旁瓣得出了最优化值h=25mm和α=40°。这些与优化发射源的旁瓣得到的结果(h=25mm和α=45°)略有不同。这些是考虑在发射模式上较紧的约束在优选的发射源情况下得到的值。
图11显示了纵向辐射源的可选的实施例。在这种情况下,由安装在圆锥形空间13上的螺旋体12形成了源12,源12通过探针17耦合到馈线Tx。
在显示的实例中,发射和接收源的极化是圆形的,可能意义相同,可能意义相反。
对于精于该技术的人是明显的,螺旋体12’可以定位在圆柱形空腔中,象聚苯乙烯棒那样。
本发明在不脱离所附权利要求申明的范畴的情况下在许多方面都可以修改。
Claims (9)
1.一种卡塞格伦型多反射面天线的电磁波发射/接收(T/R)源,该天线包括在第一频带工作的纵向辐射装置(12,12’)和在第二频带工作的n个行波型的辐射元件(11)的阵列,n个辐射元件对称地布置在纵向辐射装置的周围,该阵列和纵向辐射装置有近似一致的相位中心,其特征在于n个辐射元件的阵列由多边形横截面的波导(15)来激励。
2.根据权利要求1所述的源,其特征在于n个辐射元件的阵列是圆形阵列,波导形成了“菠萝片”形状的空腔。
3.根据权利要求1和2所述的源,其特征在于波导(15)具有尺寸以至于D是圆形阵列的平均直径:
D=nλg/2,其中n表示辐射元件的个数,λg表示导波在工作频率时的波长;
λg=λ0[εr-(λ0/λc)2]-1/2,其中,λc是对于TE01基本模式的矩形波导的截止波长,λ0是在真空中的波长,εr是填充波导的电介质的介电常数;和
λc=2a(εr)1/2,其中a是矩形波导的宽度。
4.根据权利要求3所述的源,其特征在于把D选择为:
1.3λ0<D<1.9λ0。
5.根据权利要求1到4之一所述的源,其特征在于用介电常数.εr≥1的电介质填充波导。
6.根据权利要求1到5之一所述的源,其特征在于行波型的辐射元件是螺旋体(11)。
7.根据权利要求1到3的任一个所述的源,其特征在于纵向辐射装置由纵向辐射介质棒或者“聚苯乙烯棒”(12)组成,它的轴与辐射轴一致,所述的棒由包括波导的装置来激励。
8.根据权利要求1到3之一所述的源,其特征在于纵向辐射装置由设备(12’)以螺旋体的形式组成,它的轴与辐射轴一致,所述设备由包括同轴电缆的装置来激励。
9.根据权利要求7和8任一个所述的源,其特征在于减小了旁瓣的空腔(14)围绕纵向辐射装置。
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GB9900411D0 (en) * | 1999-01-08 | 1999-02-24 | Cambridge Ind Ltd | Multi-frequency antenna feed |
US6320553B1 (en) * | 1999-12-14 | 2001-11-20 | Harris Corporation | Multiple frequency reflector antenna with multiple feeds |
-
2001
- 2001-10-11 AU AU2001295677A patent/AU2001295677A1/en not_active Abandoned
- 2001-10-11 DE DE60103653T patent/DE60103653T2/de not_active Expired - Lifetime
- 2001-10-11 US US10/398,834 patent/US6861998B2/en not_active Expired - Fee Related
- 2001-10-11 KR KR10-2003-7004642A patent/KR20030040513A/ko not_active Application Discontinuation
- 2001-10-11 CN CNB018172288A patent/CN1254883C/zh not_active Expired - Fee Related
- 2001-10-11 WO PCT/FR2001/003132 patent/WO2002031920A1/fr active IP Right Grant
- 2001-10-11 EP EP01976390A patent/EP1325537B1/fr not_active Expired - Lifetime
- 2001-10-11 MX MXPA03002670A patent/MXPA03002670A/es active IP Right Grant
- 2001-10-11 ES ES01976390T patent/ES2222394T3/es not_active Expired - Lifetime
- 2001-10-11 JP JP2002535203A patent/JP4090875B2/ja not_active Expired - Lifetime
Cited By (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN101911389A (zh) * | 2007-12-05 | 2010-12-08 | 宇沃德有限公司 | 采用双极化用螺旋馈源的轴向移位椭圆天线系统 |
CN108768500A (zh) * | 2018-05-25 | 2018-11-06 | 北京无线电测量研究所 | 一种通信卫星转发器 |
CN108768500B (zh) * | 2018-05-25 | 2021-01-22 | 北京无线电测量研究所 | 一种通信卫星转发器 |
Also Published As
Publication number | Publication date |
---|---|
MXPA03002670A (es) | 2003-06-24 |
EP1325537B1 (fr) | 2004-06-02 |
JP4090875B2 (ja) | 2008-05-28 |
WO2002031920A1 (fr) | 2002-04-18 |
CN1254883C (zh) | 2006-05-03 |
DE60103653D1 (de) | 2004-07-08 |
ES2222394T3 (es) | 2005-02-01 |
US20040021612A1 (en) | 2004-02-05 |
US6861998B2 (en) | 2005-03-01 |
KR20030040513A (ko) | 2003-05-22 |
JP2004511940A (ja) | 2004-04-15 |
AU2001295677A1 (en) | 2002-04-22 |
DE60103653T2 (de) | 2005-06-09 |
EP1325537A1 (fr) | 2003-07-09 |
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