CN117525880A - Coupling resonator decoupling network applied to mutual coupling inhibition of multiple antenna units - Google Patents
Coupling resonator decoupling network applied to mutual coupling inhibition of multiple antenna units Download PDFInfo
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- 238000005859 coupling reaction Methods 0.000 title claims abstract description 55
- 230000005764 inhibitory process Effects 0.000 title claims abstract description 10
- 230000005855 radiation Effects 0.000 claims abstract description 67
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/52—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure
- H01Q1/521—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas
- H01Q1/523—Means for reducing coupling between antennas; Means for reducing coupling between an antenna and another structure reducing the coupling between adjacent antennas between antennas of an array
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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- H—ELECTRICITY
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Abstract
The invention discloses a coupling resonator decoupling network applied to mutual coupling inhibition of multiple antenna units, which comprises the following components: the antenna comprises a radiation antenna array, a transmission line structure with the characteristic impedance identical to the antenna port impedance, a parasitic structure, a four-port CRDN structure and a single branch matching network; the radiation antenna array and the parasitic structure are printed on the first dielectric substrate; the transmission line structure, the four-port CRDN structure and the single branch matching network are printed on the second medium substrate; the real part of the transadmittance of the radiation antenna is converted into 0 in a preset frequency band by controlling the sizes of the transmission line structure and the parasitic structure at the same time, and the imaginary part of the transadmittance of the four-port CRDN structure and the imaginary part of the transadmittance of the radiation antenna can be mutually offset in the preset frequency band, so that the inhibition of different coupling between the radiation antennas is realized. By adopting the technical scheme of the invention, the coupling inhibition of the tightly placed antenna array can be realized without occupying too large volume; and without increasing the cross-sectional height of the antenna.
Description
Technical Field
The invention belongs to the technical field of antennas, and particularly relates to a coupling resonator decoupling network applied to mutual coupling inhibition of multiple antenna units.
Background
MIMO (Multiple-Input Multiple-Output) antenna systems have the ability to significantly increase the channel capacity of a wireless communication system. However, multi-antenna systems are currently moving towards miniaturization and integration, which means that more and more antennas will be integrated into more and more compact devices, which inevitably will pull the physical distance of the antennas closer, so that there is a stronger coupling between the antennas. The coupling between antennas can significantly reduce various key parameters of the multi-antenna system, such as gain, efficiency, etc.
For the problem of coupling suppression between multiple antenna units, a number of decoupling methods have been proposed, and common decoupling methods include electromagnetic bandgap structures (Electromagnetic Band-gap, EBG), metamaterial cladding or decoupling network structures. However, EBG structures are not suitable for suppressing coupling between antennas with close placement because they need to be periodically arranged between antenna elements, which generally requires a large volume. The metamaterial cladding is usually placed at a certain height above the antenna, which achieves good decoupling performance at the cost of increasing the profile height of the antenna. Furthermore, decoupling networks are of great interest due to their clear design theory and low profile height, but most decoupling networks today only suppress the coupling between two antennas.
In the prior art, the following defects exist: for the problem of coupling suppression between multiple antenna units, a decoupling network method can be adopted under the premise of not occupying a large volume and not increasing the height of the antenna section. However, most decoupling networks today only suppress the coupling between two antennas. As the number of antennas increases, there are multiple coupling paths between antennas, and thus, a targeted decoupling network needs to be used for different coupling paths, which increases the difficulty and complexity of designing the decoupling network.
Disclosure of Invention
The invention aims to solve the technical problem of providing a coupling resonator decoupling network applied to mutual coupling inhibition of multiple antenna units, which does not occupy too large volume and can be suitable for coupling inhibition of tightly placed antenna arrays; and without increasing the cross-sectional height of the antenna.
In order to achieve the above purpose, the present invention adopts the following technical scheme:
a coupled resonator decoupling network for multi-antenna element mutual coupling rejection, comprising: the antenna comprises a radiation antenna array, a transmission line structure with the characteristic impedance identical to the antenna port impedance, a parasitic structure, a four-port CRDN structure and a single branch matching network;
the radiation antenna array and the parasitic structure are printed on the first dielectric substrate;
the transmission line structure, the four-port CRDN structure and the single-branch matching network are printed on a second medium substrate;
the real part of the transadmittance of the radiation antenna is converted into 0 in a preset frequency band by controlling the sizes of the transmission line structure and the parasitic structure at the same time, and the imaginary part of the transadmittance of the four-port CRDN structure and the imaginary part of the transadmittance of the radiation antenna can be mutually offset in the preset frequency band, so that the inhibition of different coupling between the radiation antennas is realized. The matching bandwidth of the radiating antenna can be further optimized by the single-branch matching network.
Preferably, the radiating antenna array includes four radiating antennas respectively arranged at intervals along the first direction and the second direction, and forms a 2×2 antenna array. The first radiation antenna has a polarization direction which is +45 degrees with respect to the second direction, the second radiation antenna and the first radiation antenna are centrally symmetrical with respect to the first direction, and the third radiation antenna and the first radiation antenna and the second radiation antenna are centrally symmetrical with respect to the second direction.
Preferably, the geometric centers of any two adjacent radiation antennas are spaced apart by 0.35λ 0 ，λ 0 Wavelength of electromagnetic wave in vacuum when the radiation antenna works at 3.5GHz of central frequency。
Preferably, there is co-polarized coupling and cross-polarized coupling between the radiating antennas, on the order of-10 dB and-15.6 dB, respectively.
Preferably, there is a diagonal admittance and an adjacent-edge admittance between the radiating antennas.
Preferably, the radiation antenna array further includes: a feed post; one end of the feed column is connected with the radiation antenna, penetrates through the first dielectric substrate, and the other end of the feed column is connected with a transmission line with the characteristic impedance identical to the antenna port impedance.
Preferably, the four-port CRDN structure is composed of four closely spaced and identical square-open resonators, and the desired imaginary value of the transadmittance is obtained by controlling the position of the resonator slot.
Preferably, the adjacent radiating antennas have a center-to-center spacing D and a length L R The length of the feed position 5 of the radiation antenna from the edge is L D The method comprises the steps of carrying out a first treatment on the surface of the The length of the parasitic element is L P Width W P The method comprises the steps of carrying out a first treatment on the surface of the The sum of the lengths of the introduced transmission lines is L F1 +L F2 +L F3 The method comprises the steps of carrying out a first treatment on the surface of the In the four-port CRDN structure, the open resonator has a length L C Width W C The position of the resonator slot is offset from the center by a distance L S The length of the grooved part of the resonator is G 3 The method comprises the steps of carrying out a first treatment on the surface of the The gaps between the split resonators are G along the first direction and the second direction respectively 2 And G 1 The method comprises the steps of carrying out a first treatment on the surface of the The specific corresponding parameters are as follows:
D＝30mm,L R ＝12.2mm,L D ＝7.1mm,L P ＝27mm,W P ＝2mm,L F1 ＝1.3mm,L F2 ＝4.1mm,L F3 ＝8.6m
m,L C ＝4.2mm,W C ＝0.3mm,G 1 ＝0.2mm,G 2 ＝0.1mm,L S ＝0.8mm,G 3 ＝0.15mm。
the invention comprises a radiation antenna array, a transmission line structure with a section of characteristic impedance identical to the impedance of an antenna port, a parasitic structure, a four-port CRDN structure and a single branch matching network; the radiating antenna array comprises four radiating antennas, wherein at least two different types of coupling are present; the transmission line structure and the parasitic structure act together to enable the real parts of two different transadmittances between the radiation antennas to be close to 0 in a certain frequency band; the four-port CRDN structure is used for providing at least two imaginary parts of different admittances and is used for canceling the imaginary parts of the different admittances between the radiation antennas; by the design, the real part and the imaginary part of the admittance of two different types between the four radiation antennas are close to zero, so that the coupling is reduced; the single branch matching network is used for further expanding the matching bandwidth of the antenna; the antenna has the advantages of simple design process, low cost, stable structure, mature processing technology and suitability for large-scale mass production; meanwhile, the invention improves the isolation between the antennas in a limited space, is suitable for a compact multi-antenna decoupling system, has low profile and expansibility, and can be popularized to different antenna types and other frequency bands.
Drawings
In order to more clearly illustrate the technical solutions of the embodiments of the present application, the following brief description of the drawings of the embodiments will make it apparent that the drawings in the following description relate only to some embodiments of the present application and are not limiting of the present application.
Fig. 1 is a schematic perspective view of a coupled resonator decoupling network for multi-antenna element mutual coupling suppression in accordance with an embodiment of the present invention;
FIG. 2 is a schematic perspective view of the structure of FIG. 1 in a top view;
FIG. 3 is a schematic view of the structure of FIG. 1 in a top view of a first dielectric substrate;
fig. 4 is a schematic view of the second dielectric substrate in top view and a partial enlarged view of the four-port CRDN of the structure shown in fig. 1;
fig. 5 is a perspective view of a comparative radiating antenna array (reference antenna array);
fig. 6 is a schematic perspective view of the antenna after the transmission line and parasitic element structures are introduced on the basis of the comparative antenna array of fig. 5;
FIG. 7 is a schematic top view of the structure of FIG. 6, showing the structure in a top view, with the first dielectric substrate and the second dielectric substrate being shown, respectively;
fig. 8 is a graph of reflection coefficient contrast of a radiating antenna array in an embodiment of the present application with a reference antenna array in the comparative example of fig. 5, wherein the "pre-decoupling" corresponds to the comparative example and the "post-decoupling" corresponds to an embodiment of the present application;
fig. 9 is a graph comparing isolation of a radiating antenna array in an embodiment of the present application with that of a reference antenna array in the comparative example of fig. 5, wherein the "before decoupling" corresponds to the comparative example and the "after decoupling" corresponds to the embodiment of the present application;
fig. 10 is a graph comparing the real part of the transadmittance of the reference antenna array in the comparative example of fig. 5 with that of the antenna of fig. 6, wherein,corresponding to the proportion of->Corresponding to the comparative example, only a section of transmission line structure with characteristic impedance equal to that of the antenna port is introduced, < >>Corresponding to the antenna shown in fig. 6, i.e. two structures of a transmission line and a parasitic element are introduced on the basis of a comparative example, the subscript 12 indicates between 1 port and 2 port, and the subscript 14 indicates between 1 port and 4 port;
fig. 11 is an illustration of the imaginary part sizes of three different transadmittances of the antenna of fig. 6 and the four-port CRDN of fig. 4, respectively, wherein,corresponding to the transadmittance between port 1 and port 2 of the antenna shown in fig. 6, +.>Corresponding to the transadmittance between ports 1 and 2 in the four-port CRDN shown in fig. 4, the other subscript 13 indicates between ports 1 and 3, and 14 indicates between ports 1 and 4;
fig. 12 is a radiation pattern contrast plot of the radiation antenna array in the embodiment of the present application and the reference antenna array in the comparative example of fig. 5 at the 3.5GHz frequency point, wherein the "before decoupling" corresponds to the comparative example and the "after decoupling" corresponds to the embodiment of the present application;
fig. 13 is a graph comparing the overall efficiency of the radiating antenna array in an embodiment of the present application with the reference antenna array in the comparative example of fig. 5, wherein the "before decoupling" corresponds to the comparative example and the "after decoupling" corresponds to an embodiment of the present application;
fig. 14 is an ECC comparison diagram of a radiating antenna array in an embodiment of the present application with a reference antenna array in the comparison example of fig. 5, wherein the "before decoupling" corresponds to the comparison example and the "after decoupling" corresponds to an embodiment of the present application;
wherein F1-first direction, F2-second direction;
the antenna comprises a first radiation antenna, a second radiation antenna, a third radiation antenna, a fourth radiation antenna, a feeding position of the first radiation antenna, a 6-metal stratum, a 7-parasitic structure, a transmission line structure with the same 8-section characteristic impedance as the characteristic impedance of the antenna, a 9-four-port CRDN structure, a 10-single branch matching network, a 11-first dielectric substrate and a 12-second dielectric substrate.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
In order that the above-recited objects, features and advantages of the present invention will become more readily apparent, a more particular description of the invention will be rendered by reference to the appended drawings and appended detailed description.
Example 1:
as shown in fig. 1 to 4, an embodiment of the present invention provides a coupled resonator decoupling network for mutual coupling suppression of multiple antenna elements, including: a first metal layer, a first dielectric substrate 11, a second dielectric substrate 12 and a metal stratum 6 from top to bottom.
The first metal layer includes: the radiating antenna array and the parasitic structure 7 are, among other things,
the radiating antenna array includes: four closely spaced radiating antennas, here exemplified by simple patch antennas. More specifically, the four radiation antennas are arranged at intervals along the first direction and the second direction, the first radiation antenna 1 has a polarization direction of +45° with respect to the second direction, the second radiation antenna 2 is central-symmetrical with respect to the first direction with respect to the radiation antenna 1, and the third and fourth radiation antennas 3 and 4 are central-symmetrical with respect to the first and second radiation antennas 1 and 2. The distance between the geometric centers of any two adjacent radiation antennas is 0.35 lambda 0 ，λ 0 Electromagnetic waves are at a wavelength in vacuum when the radiating antenna is operated at a center frequency of 3.5 GHz. The parasitic structure 7 comprises four parasitic elements, each arranged in the vicinity of the radiating antenna.
Further, co-polarized coupling and cross-polarized coupling exist between the radiation antennas, which are about-10 dB and-15.6 dB respectively; wherein the coupling S between the first radiating antenna 1 and the fourth radiating antenna 4 14 For co-polarized coupling, a coupling S between the second radiating antenna 2 and the third radiating antenna 3 23 Is co-polarized coupling; coupling S between a first radiating antenna 1 and a second radiating antenna 2 12 For cross-polarization coupling, a coupling S between the third radiating antenna 3 and the fourth radiating antenna 4 34 For cross-polarization coupling, a coupling S between the first radiating antenna 1 and the third radiating antenna 3 13 For cross-polarization coupling, a coupling S between the second radiating antenna 2 and the fourth radiating antenna 4 24 Is cross-polarization coupling.
Further, there are diagonal admittances and adjacent-edge admittances between the radiating antennas; wherein the transadmittance S between the first radiating antenna 1 and the fourth radiating antenna 4 14 For diagonal transadmittance, transadmittance S between the second radiation antenna 2 and the third radiation antenna 3 23 Is the diagonal admittance; admittance S of 2 between the first radiating antenna 1 and the second radiating antenna 12 For the admittance of adjacent sides, the admittance S between the third radiating antenna 3 and the fourth radiating antenna 4 34 For adjacent-side admittance, a first radiation antenna 1 and a third radiation antenna 3Interadmittance S 13 For the admittance of adjacent sides, the admittance S between the second radiating antenna 2 and the fourth radiating antenna 4 24 Is the admittance of adjacent edges.
The second metal layer includes: a transmission line structure 8, a four-port CRDN structure 9 and a single branch matching network 10; the transmission line structure 8 is a transmission line with characteristic impedance identical to the port impedance of the antenna connected in series to the ports of the four radiating antennas. The four port CRDN structure 9 includes four identical closely spaced square-open resonators.
Further, the radiation antenna array further includes: a feed post; one end of the feed column is connected with the radiation antenna, penetrates through the first dielectric substrate, and the other end of the feed column is connected with a transmission line with the characteristic impedance identical to the antenna port impedance.
The metal formation 6 may be a metal sheet and may be soldered with a test connector for connecting to an antenna test device.
The PCB board adopted by the first dielectric substrate is a Rogers4350 substrate, the thickness is 4.5mm, and the dielectric constant is 3.66. The PCB board adopted by the second dielectric substrate is also a Rogers4350 substrate, and the thickness is 0.508mm. The first metal layer is printed on the upper layer 11 of the first dielectric substrate, and the second metal layer and the metal layer 6 are respectively printed on the upper layer and the lower layer of the second dielectric substrate 12.
In the embodiment of the invention, as shown in fig. 1 and 2, since the transadmittance of the four-port CRDN structure 9 is purely imaginary, in order to achieve decoupling, the real part of the transadmittance of the radiating antenna must first be made to approach 0 in the required frequency band by other means. The real part of the transadmittance of the radiation antenna is converted to the vicinity of 0 in the required frequency band by stringing a section of transmission line at the ports of the four radiation antennas and introducing parasitic structures in the vicinity of the four radiation antennas. Next, by designing the four-port CRDN structure 9, a mutual cancellation of the imaginary parts of the transadmittances with the radiating antennas is achieved. Meanwhile, in order to further expand the matching bandwidth of the antenna, a single stub matching network 10 is designed.
In a specific implementation, as shown in fig. 3 and 4, the adjacent radiating antennas have a center-to-center spacing D,the length of the radiation antenna is L R The length of the feed position of the radiation antenna from the edge is L D . The length of the parasitic element is L P Width W P . The sum of the lengths of the introduced transmission lines is L F1 +L F2 +L F3 . In the four-port CRDN structure, the open resonator has a length L C Width W C The position of the resonator slot is offset from the center by a distance L S The length of the grooved part of the resonator is G 3 . Meanwhile, along the first direction and the second direction, the gaps between the split resonators are G respectively 2 And G 1 . The specific corresponding parameters are as follows:
D＝30,L R ＝12.2,L D ＝7.1,L P ＝27,W P ＝2,L F1 ＝1.3,L F2 ＝4.1,L F3 ＝8.6,L C ＝4.2,W C ＝0.3,
G 1 ＝0.2,G 2 ＝0.1,L S ＝0.8,G 3 =0.15 (unit: mm).
In contrast, fig. 5 shows a perspective view of a structure including only the radiating antenna array as the reference antenna array in the comparative example. Meanwhile, fig. 6 and 7 show a perspective structural view and a plan view of the antenna after the transmission line and the parasitic structure are introduced, on the basis of fig. 5. Meanwhile, in fig. 7, the length L of the introduced transmission line F And the transmission line L in FIG. 4 F1 ，L F2 ，L F3 The sum of the three is equal, i.e. L F ＝L F1 +L F2 +L F3 ＝14mm。
Referring to fig. 8, fig. 8 shows a reflection coefficient comparison diagram of the radiation antenna array shown in fig. 1 and the reference antenna array of the comparative example shown in fig. 5, and it can be seen that the reference antenna array in the comparative example can cover the 3.41-3.6GHz band and the radiation antenna array in the embodiment can cover the 3.45-3.56GHz band on the premise that the reflection coefficient is lower than-10 dB.
Referring again to fig. 9, fig. 9 shows a comparison of isolation between the radiating antenna array shown in fig. 1 and the reference antenna array of the comparative example shown in fig. 5, and it can be seen that the frequency ranges are 3.45-3.56GHzS in comparative example 12 And S is 13 Such cross-polarized coupling is-16.8 dB, which in embodiments can be reduced to-25 dB. In the comparative example, S 14 Such co-polarized coupling is-10.3 dB, which in embodiments can be reduced to-23.5 dB.
Referring again to fig. 10, fig. 10 shows a real part comparison of the transadmittance of the reference antenna array in the comparative example of fig. 5 and the antenna shown in fig. 6. It can be seen that in the 3.4-3.6GHz band, in the comparative reference antenna array,between 0.002 and 0.006, < >>Between-0.008 and 0.008, where the real part of the transadmittance of both types is far from the 0 target. After introducing a transmission line structure with the same characteristic impedance as the antenna port impedance, the antenna port impedance is reduced>Between-0.004 and-0.003, < >>Between 0.001 and 0.003, the object that the real part of the transadmittance approaches 0 is still not met. Continuing to introduce parasitic structures, it can be seen that +.>Between 0.0008 and 0.001, < > and->Between-0.0008 and 0, the real part of the admittance of both types is almost around 0. And (3) injection: re represents the real part.
Referring again to fig. 11, fig. 11 shows the imaginary magnitudes of three different transadmittances for the antenna of fig. 6 and the four-port CRDN structure of fig. 4, respectively. It can be seen that the imaginary parts of the three different transadmittances of the antenna shown in fig. 6 are all positive values and the imaginary parts of the three different transadmittances provided by the four-port CRDN are all negative values, so that mutual cancellation can be achieved.
Referring again to fig. 12, fig. 12 shows a radiation pattern comparison of the radiation antenna array shown in fig. 1 with the reference antenna array in the comparative example of fig. 5 at the 3.5GHz frequency point. It can be seen that in the comparative example of fig. 5, the radiation pattern of the antenna is depressed, and in the embodiment of the present invention, the depression of the radiation pattern of the antenna is recovered, compared to the comparative example of fig. 5.
Referring again to fig. 13, fig. 13 shows a graph of the overall efficiency of the radiating antenna array of fig. 1 versus the reference antenna array of the comparative example of fig. 5. From this figure, it can be seen that the overall efficiency of the embodiment of the present invention is significantly improved in the 3.45-3.56GHz band, compared to the comparative example of fig. 5.
Referring again to fig. 14, fig. 14 shows a comparison of ECC of the radiating antenna array shown in fig. 1 with the reference antenna array in the comparative example of fig. 5. From this figure, it can be seen that the ECC between the ports in the embodiment of the present invention is significantly reduced compared to the comparative example of fig. 5.
The above embodiments are merely illustrative of the preferred embodiments of the present invention, and the scope of the present invention is not limited thereto, but various modifications and improvements made by those skilled in the art to which the present invention pertains are made without departing from the spirit of the present invention, and all modifications and improvements fall within the scope of the present invention as defined in the appended claims.
Claims (8)
1. A coupled resonator decoupling network for multi-antenna element mutual coupling rejection, comprising: the antenna comprises a radiation antenna array, a transmission line structure with the characteristic impedance identical to the antenna port impedance, a parasitic structure, a four-port CRDN structure and a single branch matching network;
the radiation antenna array and the parasitic structure are printed on the first dielectric substrate;
the transmission line structure, the four-port CRDN structure and the single-branch matching network are printed on a second medium substrate;
the real part of the transadmittance of the radiation antenna is converted into 0 in a preset frequency band by controlling the sizes of the transmission line structure and the parasitic structure at the same time, and the imaginary part of the transadmittance of the four-port CRDN structure and the imaginary part of the transadmittance of the radiation antenna can be mutually offset in the preset frequency band, so that the inhibition of different coupling between the radiation antennas is realized.
2. The decoupling network of coupled resonators for multi-antenna element mutual coupling suppression as defined in claim 1, wherein said radiating antenna array comprises four radiating antennas arranged at intervals along a first direction and a second direction, respectively, forming a 2 x 2 antenna array; the first radiation antenna has a polarization direction of +45° with respect to the second direction, the second radiation antenna is center-symmetrical with respect to the first direction, and the third radiation antenna are center-symmetrical with respect to the second direction.
3. The coupled resonator decoupling network for multi-antenna element mutual coupling suppression as claimed in claim 2, wherein the distance between the geometric centers of any two adjacent radiating antennas is 0.35λ 0 ，λ 0 Electromagnetic waves are at a wavelength in vacuum when the radiating antenna is operated at a center frequency of 3.5 GHz.
4. A coupled resonator decoupling network for use in multi-antenna element mutual coupling suppression as claimed in claim 3, wherein there is co-polarized coupling and cross-polarized coupling between radiating antennas, on the order of-10 dB and-15.6 dB, respectively.
5. The coupled resonator decoupling network of claim 4, wherein there is a diagonal admittance and an adjacent-edge admittance between the radiating antennas.
6. The coupled resonator decoupling network for use in multi-antenna element mutual coupling suppression of claim 5, said radiating antenna array further comprising: a feed post; one end of the feed column is connected with the radiation antenna, penetrates through the first dielectric substrate, and the other end of the feed column is connected with a transmission line with the characteristic impedance identical to the antenna port impedance.
7. The decoupling network of coupled resonators for multi-antenna element mutual coupling suppression as defined in claim 6, wherein said four port CRDN structure is comprised of four closely spaced and identical square-split resonators, with the desired imaginary value of the mutual admittance being obtained by controlling the position of the resonator slots.
8. The decoupling network of claim 7, wherein adjacent radiating antennas have a center-to-center spacing D and a length L R The length of the feed position of the radiation antenna from the edge is L D The method comprises the steps of carrying out a first treatment on the surface of the The length of the parasitic element is L P Width W P The method comprises the steps of carrying out a first treatment on the surface of the The sum of the lengths of the introduced transmission lines is L F1 +L F2 +L F3 The method comprises the steps of carrying out a first treatment on the surface of the In the four-port CRDN structure, the open resonator has a length L C Width W C The position of the resonator slot is offset from the center by a distance L S The length of the grooved part of the resonator is G 3 The method comprises the steps of carrying out a first treatment on the surface of the The gaps between the split resonators are G along the first direction and the second direction respectively 2 And G 1 The method comprises the steps of carrying out a first treatment on the surface of the The specific corresponding parameters are as follows:
D＝30mm,L R ＝12.2mm,L D ＝7.1mm,L P ＝27mm,W P ＝2mm,L F1 ＝1.3mm,L F2 ＝4.1mm,L F3 ＝8.6m
m,L C ＝4.2mm,W C ＝0.3mm,G 1 ＝0.2mm,G 2 ＝0.1mm,L S ＝0.8mm,G 3 ＝0.15mm。
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Citations (16)
| Publication number | Priority date | Publication date | Assignee | Title |
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