CN114172365A - Voltage drive circuit and printer - Google Patents
Voltage drive circuit and printer Download PDFInfo
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- CN114172365A CN114172365A CN202111498114.XA CN202111498114A CN114172365A CN 114172365 A CN114172365 A CN 114172365A CN 202111498114 A CN202111498114 A CN 202111498114A CN 114172365 A CN114172365 A CN 114172365A
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- 239000003990 capacitor Substances 0.000 claims abstract description 200
- 238000007599 discharging Methods 0.000 claims abstract description 81
- 239000007921 spray Substances 0.000 claims description 9
- 229910044991 metal oxide Inorganic materials 0.000 claims description 4
- 150000004706 metal oxides Chemical class 0.000 claims description 4
- 239000004065 semiconductor Substances 0.000 claims description 4
- 230000009466 transformation Effects 0.000 description 11
- 238000010586 diagram Methods 0.000 description 6
- 230000000694 effects Effects 0.000 description 4
- 238000000034 method Methods 0.000 description 3
- 238000007639 printing Methods 0.000 description 3
- 238000007641 inkjet printing Methods 0.000 description 2
- 230000000903 blocking effect Effects 0.000 description 1
- 238000004043 dyeing Methods 0.000 description 1
- 238000005516 engineering process Methods 0.000 description 1
- 238000005259 measurement Methods 0.000 description 1
- 230000000737 periodic effect Effects 0.000 description 1
- 230000008707 rearrangement Effects 0.000 description 1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
- H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps
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Abstract
The invention discloses a voltage driving circuit and a printer. The voltage driving circuit includes: the boost-buck driving module comprises a charging constant current source, a discharging constant current source and a load capacitor; a first end of the charging constant current source is connected with a power supply signal, a second end of the charging constant current source is electrically connected with a first electrode of the load capacitor, and a second electrode of the load capacitor is grounded; the first end of the discharging constant current source is electrically connected with the first electrode of the load capacitor, and the second end of the discharging constant current source is grounded; the first electrode of the load capacitor is electrically connected with the first power input end of the load, and the second power input end of the load is grounded. In other words, according to the embodiment of the invention, the voltage change slope of the power supply in the charging state and the discharging state is controlled to be stable by the voltage boosting and reducing driving module, so that the stability of the voltage change slope output by the voltage driving circuit is improved.
Description
Technical Field
The embodiment of the invention relates to computer technology, in particular to a voltage driving circuit and a printer.
Background
Along with the development of industry, more and more electronic product demands are filling the market, and the traditional printing dyeing is gradually replaced by industrial inkjet printing, but the requirement of the industrial inkjet printing nozzle on the change slope of voltage is higher, the change slope of voltage needs to be ensured to be stable, and the rapid change of voltage needs to be ensured, wherein the slew rate of a driving power supply circuit is required to reach more than 35V/uS.
The high-pressure nozzle driving plate in the prior art adopts negative feedback switch adjustment, so that the slew rate can reach more than 35V/uS, but the voltage change slope is unstable, and periodic jitter occurs, so that the ink jet effect is poor, and a high-quality printing task cannot be completed.
Disclosure of Invention
The embodiment of the invention provides a voltage driving circuit and a printer, which are used for improving the stability of the voltage change slope output by the voltage driving circuit.
In a first aspect, an embodiment of the present invention provides a voltage driving circuit, including: the boost-buck driving module comprises a charging constant current source, a discharging constant current source and a load capacitor;
the first end of the charging constant current source is connected with a power supply signal, the second end of the charging constant current source is electrically connected with the first electrode of the load capacitor, the second electrode of the load capacitor is grounded, the charging constant current source comprises a first constant current MOS (metal oxide semiconductor) tube, and the load capacitor is in a charging state by controlling the first constant current MOS tube;
the first end of the discharge constant current source is electrically connected with the first electrode of the load capacitor, the second end of the discharge constant current source is grounded, the discharge constant current source comprises a second constant current MOS (metal oxide semiconductor) tube, and the load capacitor is in a discharge state by controlling the second constant current MOS tube;
the first electrode of the load capacitor is electrically connected with a first power input end of a load, and a second power input end of the load is grounded.
Further, the ratio of the capacitance value of the load capacitor to the capacitance value of the load is greater than or equal to 10.
Furthermore, the voltage driving circuit further comprises a power supply control module, and a first output end of the power supply control module is used for sending out a charging control signal;
the charging constant current source comprises a first grid driving chip and a first constant current MOS tube;
a first input end of the first gate driving chip is electrically connected with a first output end of the power control module, and the first output end of the first gate driving chip is used for sending a first gate driving signal according to the charging control signal;
the first output end of the first gate driving chip is electrically connected with the gate of the first constant current MOS tube, the drain of the first constant current MOS tube is used for accessing the power supply signal, the power supply input end of the first gate driving chip is electrically connected with the power supply signal, and the first gate driving signal is used for controlling the first constant current MOS tube to be in a conducting state or a stopping state;
and the source electrode of the first constant current MOS tube is electrically connected with the first electrode of the load capacitor, and the first constant current MOS tube is used for charging the load capacitor in a conducting state.
Further, a second output end of the power control module is used for sending a discharge control signal;
the discharge constant current source comprises a second grid driving chip and a second constant current MOS tube;
the input end of the second grid driving chip is electrically connected with the second output end of the power supply control module, and the second grid driving chip is used for sending a second grid driving signal according to the discharge control signal;
the output end of the second gate driving chip is electrically connected with the gate of the second constant current MOS tube, and the second gate driving signal is used for controlling the second constant current MOS tube to be in a conducting state or a stopping state;
the drain electrode of the second constant current MOS tube is electrically connected with the first electrode of the load capacitor, the source electrode of the second constant current MOS tube is grounded, and the second constant current MOS tube and the load capacitor form a discharge loop.
Further, the device also comprises a feedback module, wherein the feedback module comprises a first resistor, a second resistor and a processing unit;
the first end of the first resistor is electrically connected with a first electrode of the load capacitor, the second end of the first resistor is electrically connected with the first end of the second resistor, the second end of the second resistor is grounded, and the first end of the processing unit is electrically connected with the second end of the first resistor and is used for acquiring the voltage values of the first resistor corresponding to the first moment and the second moment when the load capacitor is in a charging state and the voltage values of the first resistor corresponding to the third moment and the fourth moment when the load capacitor is in a discharging state;
the processing unit is used for determining the voltage change slope of the load capacitor in a charging state and the voltage change slope of the load capacitor in a discharging state according to the voltage value of the second end of the first resistor.
Further, the feedback module further includes a comparator, a negative input end of the comparator is electrically connected to the second end of the first resistor, a positive input end of the comparator is electrically connected to a reference voltage output end of the processing unit, an output end of the comparator is electrically connected to the first end of the processing unit, the reference voltage output end of the processing unit is configured to output a charging reference voltage value at the first time and the second time when the load capacitor is in a charging state, and the reference voltage output end of the processing unit is configured to output a discharging reference voltage value at the third time and the fourth time when the load capacitor is in a discharging state;
the processing unit is used for determining the voltage change slope of the load capacitor in a charging state and the voltage change slope of the load capacitor in a discharging state according to the logic value of the output end of the comparator.
Further, the first gate driving chip is further configured to adjust a voltage value corresponding to the first gate driving signal when a voltage change slope of the load capacitor in the charging state does not conform to a first preset voltage change slope.
Further, the second gate driving chip is further configured to adjust a voltage value corresponding to the second gate driving signal when a voltage change slope of the load capacitor in the discharging state does not coincide with a second preset voltage change slope.
Further, the charging constant current source further comprises a bootstrap capacitor, a diode and a third resistor;
an anode of the diode is electrically connected with a first output end of the power control module, a cathode of the diode is electrically connected with a second input end of the first gate driving chip, a first electrode of the bootstrap capacitor is electrically connected with a second input end of the first gate driving chip, a second electrode of the bootstrap capacitor is electrically connected with a second output end of the first gate driving chip, and a second electrode of the bootstrap capacitor is electrically connected with a first electrode of the load capacitor;
the first end of the third resistor is electrically connected with the first output end of the first gate driving chip, and the second end of the third resistor is electrically connected with the first electrode of the load capacitor.
In a second aspect, an embodiment of the present invention further provides a printer, where the printer includes a voltage driving circuit;
the printer further comprises a high-voltage spray head, a first power supply input end of the high-voltage spray head is electrically connected with a first electrode of the load capacitor, and a second power supply input end of the high-voltage spray head is grounded.
In the technical scheme provided by the embodiment of the invention, the load capacitor is in a charging state, the current provided by the charging constant current source for the load capacitor is a constant value, and the voltage transformation rate of the first electrode of the load capacitor is a constant value. The load capacitor is in a discharging state, the current provided by the discharging constant current source for the load capacitor is a constant value, the voltage transformation rate of the first electrode of the load capacitor is a constant value, and the voltage of the first electrode of the load capacitor provides a power supply signal for the load.
Drawings
Fig. 1 is a schematic structural diagram of a voltage driving circuit according to an embodiment of the present invention;
fig. 2 is another schematic structural diagram of a voltage driving circuit according to an embodiment of the invention;
FIG. 3 is a schematic diagram of another embodiment of a voltage driving circuit;
FIG. 4 is a flow chart illustrating a control method of the voltage driving circuit according to an embodiment of the present invention;
fig. 5 is a schematic structural diagram of a printer according to an embodiment of the present invention.
Detailed Description
The present invention will be described in further detail with reference to the accompanying drawings and examples. It is to be understood that the specific embodiments described herein are merely illustrative of the invention and are not limiting of the invention. It should be further noted that, for the convenience of description, only some of the structures related to the present invention are shown in the drawings, not all of the structures.
Fig. 1 is a schematic structural diagram of a voltage driving circuit according to an embodiment of the present invention, and as shown in fig. 1, the voltage driving circuit includes: the buck-boost driving module 1, wherein the buck-boost driving module 1 includes a charging constant current source 100, a discharging constant current source 200 and a load capacitor C2; a first end 100a of the charging constant current source 100 is connected with a power supply signal, a second end 100b of the charging constant current source 100 is electrically connected with a first electrode of a load capacitor C2, and a second electrode of the load capacitor C2 is grounded; a first end 200a of the discharging constant current source 200 is electrically connected to a first electrode of the load capacitor C2, and a second end 200b of the discharging constant current source 200 is grounded; a first electrode of the load capacitor C2 is electrically connected to a first power input terminal of the load capacitor C0, and a second power input terminal of the load capacitor C0 is grounded.
Optionally, the first end 100a of the charging constant current source 100 is electrically connected to the first power source E1 for receiving a power signal.
Specifically, the first electrode of the load capacitor C2 of the voltage driving circuit provides a power signal to the load capacitor C0, and the load capacitor C0 may be, for example, a high-voltage head in a printer.
The capacity Q of the load capacitor C2 satisfies the formula (1):
q & CU & It formula (1)
Wherein Q is the capacity Q of the load capacitor C2, C is the capacitance value of the load capacitor C2, I is the charging current or discharging current of the load capacitor C2, and t is the charging time or discharging time of the load capacitor C2.
The voltage transformation ratio of the first electrode of the load capacitor C2 satisfies the formula (2):
the load capacitor C2 is in a charging state, the current I provided by the charging constant current source 100 to the load capacitor C2 is a constant value, and the voltage transformation ratio of the first electrode of the load capacitor C2 is a constant value. The load capacitor C2 is in a discharging state, the current I provided by the discharging constant current source 200 to the load capacitor C2 is a constant value, and the voltage transformation ratio of the first electrode of the load capacitor C2 is a constant value.
In the technical scheme provided by the embodiment of the invention, the load capacitor C2 is in a charging state, the current I provided by the charging constant current source 100 for the load capacitor C2 is a constant value, and the voltage transformation ratio of the first electrode of the load capacitor C2 is a constant value. The load capacitor C2 is in a discharging state, the current I supplied by the discharging constant current source 200 to the load capacitor C2 is a constant value, the voltage transformation rate of the first electrode of the load capacitor C2 is a constant value, and the voltage of the first electrode of the load capacitor C2 supplies a power supply signal to the load capacitor C0, so that the change slope of the voltage applied to the load capacitor C0 by the voltage driving circuit is a constant value no matter whether the load capacitor C2 is in a charging state or a discharging state, and the stability of the change slope of the voltage output by the voltage driving circuit is improved.
Optionally, referring to fig. 1, the ratio of the capacitance of the load capacitor C2 to the capacitance of the load capacitor C0 is greater than or equal to 10.
Specifically, when the ratio of the capacitance value of the load capacitor C2 of the voltage driving circuit to the capacitance value of the load capacitor C0 is greater than or equal to 10, and when the capacitance value of the load capacitor C0 changes, the influence on the voltage division change of the load capacitor C2 can be ignored, and thus the stability of the voltage change slope output by the voltage driving circuit is improved. For example, when the load capacitor C0 is a nozzle of a printer, the impact on the ink ejection effect of the printer is reduced, and the ink ejection effect is improved. The load capacitor C2 and the load capacitor C0 are connected in parallel.
Optionally, referring to fig. 2, the voltage driving circuit further includes a power control module 2, where a first output end 2a of the power control module is configured to send a charging control signal; the charging constant current source 100 comprises a first gate driving chip 10 and a first constant current MOS transistor Q1; a first input end 10a of the first gate driving chip 10 is electrically connected with a first output end 2a of the power control module 2, and a first output end 10b of the first gate driving chip 10 is used for sending a first gate driving signal according to the charging control signal; the first output end 10b of the first gate driving chip 10 is electrically connected with the gate of the first constant current MOS transistor Q1, the drain of the first constant current MOS transistor Q1 is used for accessing a power signal, the power input end 10c of the first gate driving chip is connected with the power signal E1, and the first gate driving signal is used for controlling the first constant current MOS transistor Q1 to be in a conducting state or a cut-off state; the source of the first constant current MOS transistor Q1 is electrically connected to the first electrode of the load capacitor C2, and the first constant current MOS transistor Q1 is configured to charge the load capacitor in the on state.
Specifically, the first output end 2a of the power control module 2 sends a charging control signal to the first input end 10a of the first gate driver chip 10, and the first gate driver chip 10 receives the charging control signal and generates a first gate driver signal according to the charging control signal. A first gate driving signal is sent to the gate of the first constant current MOS transistor Q1 through the first output terminal 10b of the first gate driving chip 10, so that the first constant current MOS transistor Q1 is in a conducting state. The first constant current MOS transistor Q1 in the on state generates a gate-source voltage UGS, a turn-on voltage UGS (th), and a drain-source voltage UDS. When the drain-source voltage UDS is greater than or equal to the difference between the gate-source voltage UGS and the start voltage UGS (th), and the gate-source voltage UGS is greater than or equal to the start voltage UGS (th), the first constant current MOS transistor Q1 is forced to enter a constant current region, so that the load capacitor C2 is in a charging state, the charging constant current source 100 provides a constant current I for the load capacitor C2, and according to the formula (1) and the formula (2), the voltage transformation rate of the first electrode of the load capacitor C2 is a constant value, thereby improving the stability of the voltage change slope output by the voltage driving circuit.
Optionally, referring to fig. 2, the second output terminal 2b of the power control module 2 is configured to send a discharge control signal; the discharging constant current source 200 includes a second gate driving chip 20 and a second constant current MOS transistor Q2; the input end 20a of the second gate driving chip 20 is electrically connected to the second output end 2b of the power control module 2, and the second gate driving chip 20 is configured to send a second gate driving signal according to the discharge control signal; the output end 20b of the second gate driving chip 20 is electrically connected to the gate of the second constant current MOS transistor Q2, and the second gate driving signal is used to control the second constant current MOS transistor Q2 to be in a conducting state or a blocking state; the drain of the second constant current MOS transistor Q2 is electrically connected to the first electrode of the load capacitor C2, the source of the second constant current MOS transistor is grounded, and the second constant current MOS transistor Q2 and the load capacitor C2 form a discharge circuit.
Specifically, the second output end 2b of the power control module 2 sends a discharge control signal to the first input end 20a of the second gate driver chip 20, and the second gate driver chip 20 receives the discharge control signal and generates a second gate driver signal according to the discharge control signal. The first gate driving signal is sent to the gate of the second constant current MOS transistor Q2 through the first output terminal 20b of the second gate driving chip 20, so that the first constant current MOS transistor Q2 is in a conducting state, and a discharge loop is formed. The second constant current MOS transistor Q2 in the on state generates a gate-source voltage UGS, a turn-on voltage UGS (th), and a drain-source voltage UDS. When the drain-source voltage UDS of the second constant current MOS transistor Q2 is greater than or equal to the difference between the gate-source voltage UGS and the start voltage UGS (th), and the gate-source voltage UGS is greater than or equal to the start voltage UGS (th), the second constant current MOS transistor Q2 is forced to enter a constant current region, so that the load capacitor C2 is in a discharge state, the discharge current I provided by the discharge constant current source 200 to the load capacitor C2 is a constant value, and according to the formula (1) and the formula (2), the voltage transformation rate of the first electrode of the load capacitor C2 is a constant value, thereby improving the stability of the voltage change slope output by the voltage driving circuit.
Optionally, referring to fig. 2, the voltage driving circuit further includes a feedback module 3, where the feedback module 3 includes a first resistor R3, a second resistor R4, and a processing unit 300; a first end of the first resistor R3 is electrically connected to a first electrode of the load capacitor C2, a second end of the first resistor R3 is electrically connected to a first end of the second resistor R4, a second end of the second resistor R4 is grounded, and a first end of the processing unit 300 is electrically connected to a second end of the first resistor R3, and is configured to collect voltage values of the first resistor R3 corresponding to a first time and a second time when the load capacitor C2 is in a charging state, and voltage values of a second end of the first resistor R3 corresponding to a third time and a fourth time when the load capacitor C2 is in a discharging state; the processing unit 300 is configured to determine a voltage change slope of the load capacitor in a charging state and a voltage change slope of the load capacitor in a discharging state according to the voltage value of the second terminal of the first resistor R3.
Illustratively, the load capacitor C2 is in an initial power-up state, which is denoted as a first time t1, and the voltage value of the second end of the first resistor R3 is 0V, which is denoted as a first voltage value V1. When the charging constant current source 100 finishes charging the load capacitor C2, the time is denoted as a second time t2, and at this time, the voltage value of the second end of the first resistor R3 is denoted as a second voltage value V2.
The voltage change slope K1 of the load capacitor C2 in the charging state satisfies the formula (3):
when the charging of the load capacitor C2 is completed, the discharging constant current source 200 and the load capacitor C2 form a discharging loop, and the time is denoted as a third time t3, and at this time, the voltage value of the second end of the first resistor R3 is denoted as a second voltage value V3. When the discharging of the load capacitor C2 is completed, the voltage value at the second end of the first resistor R3 is 0V, which is denoted as a fourth voltage value V4, and this time is denoted as a fourth time t 4.
The voltage change slope K2 of the load capacitor C2 in the discharging state satisfies the formula (4):
it should be noted that, in the embodiment of the present invention, the first time t1 is not limited to the initial power-on time of the selected load capacitor C2, and the second time t2 is not limited to the charging completion time of the selected load capacitor C2. The third time t3 is not limited to the charging completion time of the load capacitor C2, and the fourth time is not limited to the discharging completion time of the load capacitor C2.
According to the technical solution provided by the embodiment of the present invention, the processing unit 300 is configured to determine, according to the voltage values of the second end of the first resistor R3 at different times, the voltage change slope of the load capacitor C2 in the charging state and the voltage change slope in the discharging state through the formula (3) and the formula (4), and compare the voltage change slope of the load capacitor C2 in the charging state and the voltage change slope in the discharging state with the preset voltage change slope in the charging state and the preset voltage change slope in the discharging state, so that when the voltage change slope of the load capacitor C2 in the charging state and the voltage change slope in the discharging state are determined through the formula (3) and the formula (4), and the voltage change slope in the charging state and the voltage change slope in the discharging state are not equal to the preset voltage change slope in the charging state and the preset voltage change slope in the discharging state, even if the charging current I of the charging constant current source 100 and the discharging current I of the discharging constant current source 200 are adjusted, the voltage change slope in the load capacitor C2 in the charging state and the discharging state are adjusted in time .
Optionally, referring to fig. 3, the feedback module 3 further includes a comparator 400, a negative input terminal of the comparator 400 is electrically connected to the second terminal of the first resistor R3, a positive input terminal of the comparator 400 is electrically connected to a reference voltage output terminal of the processing unit 300, an output terminal of the comparator 400 is electrically connected to the first terminal of the processing unit 300, the reference voltage output terminal of the processing unit 300 is configured to output the charging reference voltage value at the first time and the second time when the load capacitor C2 is in the charging state, and the reference voltage output terminal of the processing unit 300 is configured to output the discharging reference voltage value at the third time and the fourth time when the load capacitor C2 is in the discharging state; the processing unit 300 is configured to determine a voltage change slope K1 of the load capacitor C2 in a charging state and a voltage change slope K2 in a discharging state according to a logic value of the output terminal of the comparator 300,
specifically, the charging voltage values of the first resistor R3 at the first time t1 and the second time t2 received by the negative input terminal of the comparator 400 are compared with the charging reference voltage value output by the processing unit 300, and the logic value of the comparator 400 is transmitted to the processing unit 300, and the processing unit 300 determines the voltage change slope of the charging state according to the logic value of the comparator. The charging voltage values of the first resistor R3 at the third time t3 and the fourth time t4 in the discharging state received according to the negative input terminal of the comparator 400 are compared with the charging reference voltage value output by the processing unit 300, and the logic value of the comparator 400 is transmitted to the processing unit 300, and the processing unit 300 determines the voltage change slope of the charging state and the voltage change slope of the discharging state according to the logic value of the comparator. When the processing unit 300 determines that the voltage change slope of the charging state and the voltage change slope of the discharging state are respectively compared with the preset voltage change slope of the charging state and the preset voltage change slope of the discharging state according to the logic value of the comparator, and when the processing unit 300 determines that the voltage change slope of the charging state and the voltage change slope of the discharging state are respectively not equal to the preset voltage change slope of the charging state and the preset voltage change slope of the discharging state according to the logic value of the comparator, even if the charging current I of the charging constant current source 100 and the discharging current I of the discharging constant current source 200 are adjusted, the voltage change slope of the load capacitor C2 in the charging state and the voltage change slope in the discharging state are adjusted in time.
Illustratively, in the initial power-up state, the time is denoted as a first time t1, and at this time, the voltage value of the second end of the first resistor R3 is 0V, which is denoted as a first voltage value V1. When the charging constant current source 100 finishes charging the load capacitor C2, the time is denoted as a second time t2, and at this time, the voltage value of the second end of the first resistor R3 is denoted as a second voltage value V2. The reference voltage output terminal of the processing unit 300 is configured to output the charging reference voltage value at the first time t1 and the second time t2 when the load capacitor C2 is in the charging state, which is the preset voltage value of the second terminal of the first resistor R3 when the load capacitor C2 is at the completion of charging.
Illustratively, when the charging of the load capacitor C2 is completed, the discharging constant current source 200 and the load capacitor C2 form a discharging loop, and the time is denoted as a third time t3, and at this time, the voltage value of the second end of the first resistor R3 is denoted as a second voltage value V3. When the discharging of the load capacitor C2 is completed, the voltage value at the second end of the first resistor R3 is 0V, which is denoted as a fourth voltage value V4, and this time is denoted as a fourth time t 4. The reference voltage output terminal of the processing unit 300 is configured to output a discharging reference voltage value at a third time t3 and a fourth time t4 when the load capacitor C2 is in a charging state, where the discharging reference voltage value is a preset voltage value 0V at the second terminal of the first resistor R3 when the load capacitor C2 is at the completion of discharging.
It should be noted that, in the embodiment of the present invention, the first time t1 is not limited to the initial power-on time of the selected load capacitor C2, and the second time t2 is not limited to the charging completion time of the selected load capacitor C2. The third time t3 is not limited to the charging completion time of the load capacitor C2, and the fourth time is not limited to the discharging completion time of the load capacitor C2. As the second time t2 changes, the charging reference voltage value at the reference voltage output terminal of the processing unit 300 also changes. As the fourth time t4 changes, the discharge reference voltage value at the reference voltage output terminal of the processing unit 300 also changes.
Optionally, the first gate driving chip 10 is further configured to adjust a voltage value corresponding to the first gate driving signal when a voltage change slope of the load capacitor C2 in the charging state does not conform to a first preset voltage change slope.
Specifically, the first preset voltage change slope may be understood as a preset voltage change slope of the load capacitor C2 in the charging state according to actual requirements, and is used for comparing the preset voltage change slope with the voltage change slope of the current load capacitor C2 in the charging state in real time to determine that the voltage change slope of the current load capacitor C2 in the charging state needs to be adjusted. When the load capacitor C2 output by the feedback module 3 is in a state where the charging voltage change slope is not equal to the first preset voltage change slope, the voltage value corresponding to the first gate driving signal is determined to be adjusted according to the difference between the first preset voltage change slope and the charging voltage change slope of the load capacitor C2. And adjusting the load capacitor to be in a charging voltage change slope to a first preset voltage change slope according to the voltage value corresponding to the first gate driving signal.
Optionally, the second gate driving chip 20 is further configured to adjust a voltage value corresponding to the second gate driving signal when a voltage change slope of the load capacitor C2 in the discharging state does not conform to a second preset voltage change slope.
Specifically, the second preset voltage change slope may be understood as a preset voltage change slope of the load capacitor C2 in a discharging state according to actual requirements, and is used for comparing the preset voltage change slope with the voltage change slope of the current load capacitor C2 in the discharging state in real time to determine that the voltage change slope of the current load capacitor C2 in the discharging state needs to be adjusted. When the voltage change slope of the load capacitor C2 in the discharging state output by the feedback module 3 does not match the second preset voltage change slope, the voltage value corresponding to the second gate driving signal is determined and adjusted according to the difference between the second preset voltage change slope and the voltage change slope of the load capacitor C2 in the discharging state. And adjusting the load capacitor to be in a charging voltage change slope to a second preset voltage change slope according to the voltage value corresponding to the second grid driving signal.
Optionally, referring to fig. 2, the charging constant current source 100 further includes a bootstrap capacitor C1, a diode D1, and a third resistor R1; an anode of the diode D1 is electrically connected to the first output end 2a of the power control module 2, a cathode of the diode D1 is electrically connected to the second input end 10D of the first gate driving chip 10, a first electrode of the bootstrap capacitor C1 is electrically connected to the second input end 10D of the first gate driving chip 10, a second electrode of the bootstrap capacitor C1 is electrically connected to the second output end 10e of the first gate driving chip 10, and a second electrode of the bootstrap capacitor C1 is electrically connected to the first electrode of the load capacitor C2; a first terminal of the third resistor R1 is electrically connected to the first output terminal 10b of the first gate driver chip 10, and a second terminal of the third resistor R1 is electrically connected to the first electrode of the load capacitor C2.
In a specific implementation, the bootstrap capacitor C1, the diode D1 and the third resistor R1 are used to form a bootstrap circuit for boosting the voltage of the first output terminal 10b of the first gate driver chip 10.
Fig. 4 is a flowchart illustrating a control method of the voltage driving circuit according to an embodiment of the present invention. The method comprises the following steps:
It should be noted that the first preset voltage change slope may be understood as a voltage change slope of the load capacitor C2 in a charging state preset according to actual requirements. The second preset voltage change slope can be understood as a preset voltage change slope of the load capacitor C2 in a discharging state according to actual requirements.
And step 120, measuring the voltage change slope of the load capacitor in the charging state.
And step 130, measuring the voltage change slope of the load capacitor in the discharge state.
According to the technical scheme provided by the embodiment of the invention, the voltage change slope of the load capacitor C2 in the charging state and the voltage change slope of the load capacitor C2 in the discharging state are obtained through measurement by the feedback module 3, and when the voltage change slope of the load capacitor C2 in the charging state and the voltage change slope of the load capacitor C2 in the discharging state do not accord with the first preset voltage change slope and the second preset voltage change slope respectively, even if the charging current I of the charging constant current source 100 and the discharging current I of the discharging constant current source 200 are adjusted, the voltage change slope of the load capacitor C2 in the charging state and the voltage change slope in the discharging state are adjusted in time.
Fig. 5 is a schematic structural diagram of a printer according to an embodiment of the present invention, and as shown in fig. 5, the printer includes: the voltage driving circuit of any of the above technical solutions; the printer also comprises a high-voltage spray head 4, wherein a first power supply input end of the high-voltage spray head 4 is electrically connected with a first electrode of a load capacitor C2, and a second power supply input end of the high-voltage spray head 4 is grounded.
In the technical scheme provided by the embodiment of the invention, the load capacitor C2 is in a charging state, the charging constant current source 100 provides the load capacitor C2 with a constant current I, and the voltage transformation ratio of the first electrode of the load capacitor C2 is a constant value. The load capacitor C2 is in a discharging state, the discharging constant current source 200 provides the load capacitor C2 with a current I which is a constant value, the voltage transformation rate of the first electrode of the load capacitor C2 is a constant value, and the voltage of the first electrode of the load capacitor C2 provides a power supply signal for the load, so that the change slope of the voltage applied to the high-voltage nozzle 4 by the voltage driving circuit is a constant value no matter the capacitor is in a charging state or a discharging state, the stability of the voltage change slope output by the voltage driving circuit is improved, the voltage change slope of the nozzle of the printer is promoted to be stable, and the printing effect of the printer is ensured.
It is to be noted that the foregoing is only illustrative of the preferred embodiments of the present invention and the technical principles employed. It will be understood by those skilled in the art that the present invention is not limited to the particular embodiments described herein, but is capable of various obvious changes, rearrangements and substitutions as will now become apparent to those skilled in the art without departing from the scope of the invention. Therefore, although the present invention has been described in greater detail by the above embodiments, the present invention is not limited to the above embodiments, and may include other equivalent embodiments without departing from the spirit of the present invention, and the scope of the present invention is determined by the scope of the appended claims.
Claims (10)
1. A voltage driving circuit, comprising: the boost-buck driving module comprises a charging constant current source, a discharging constant current source and a load capacitor;
the first end of the charging constant current source is connected with a power supply signal, the second end of the charging constant current source is electrically connected with the first electrode of the load capacitor, the second electrode of the load capacitor is grounded, the charging constant current source comprises a first constant current MOS (metal oxide semiconductor) tube, and the load capacitor is in a charging state by controlling the first constant current MOS tube;
the first end of the discharge constant current source is electrically connected with the first electrode of the load capacitor, the second end of the discharge constant current source is grounded, the discharge constant current source comprises a second constant current MOS (metal oxide semiconductor) tube, and the load capacitor is in a discharge state by controlling the second constant current MOS tube;
the first electrode of the load capacitor is electrically connected with a first power input end of a load, and a second power input end of the load is grounded.
2. The voltage driving circuit of claim 1, wherein a ratio of a capacitance of the load capacitor to a capacitance of the load is greater than or equal to 10.
3. The voltage driving circuit according to claim 1, further comprising a power control module, wherein a first output terminal of the power control module is configured to send out a charging control signal;
the charging constant current source comprises a first grid driving chip and a first constant current MOS tube;
a first input end of the first gate driving chip is electrically connected with a first output end of the power control module, and the first output end of the first gate driving chip is used for sending a first gate driving signal according to the charging control signal;
the first output end of the first gate driving chip is electrically connected with the gate of the first constant current MOS tube, the drain of the first constant current MOS tube is used for accessing the power supply signal, the power supply input end of the first gate driving chip is electrically connected with the power supply signal, and the first gate driving signal is used for controlling the first constant current MOS tube to be in a conducting state or a stopping state;
and the source electrode of the first constant current MOS tube is electrically connected with the first electrode of the load capacitor, and the first constant current MOS tube is used for charging the load capacitor in a conducting state.
4. The voltage driving circuit of claim 3, wherein the second output terminal of the power control module is configured to send a discharge control signal;
the discharge constant current source comprises a second grid driving chip and a second constant current MOS tube;
the input end of the second grid driving chip is electrically connected with the second output end of the power supply control module, and the second grid driving chip is used for sending a second grid driving signal according to the discharge control signal;
the output end of the second gate driving chip is electrically connected with the gate of the second constant current MOS tube, and the second gate driving signal is used for controlling the second constant current MOS tube to be in a conducting state or a stopping state;
the drain electrode of the second constant current MOS tube is electrically connected with the first electrode of the load capacitor, the source electrode of the second constant current MOS tube is grounded, and the second constant current MOS tube and the load capacitor form a discharge loop.
5. The voltage driving circuit of claim 4, further comprising a feedback module comprising a first resistor, a second resistor, and a processing unit;
the first end of the first resistor is electrically connected with the first electrode of the load capacitor, the second end of the first resistor is electrically connected with the first end of the second resistor, the second end of the second resistor is grounded, and the first end of the processing unit is electrically connected with the second end of the first resistor and is used for acquiring the voltage values of the second end of the first resistor corresponding to the first moment and the second moment when the load capacitor is in a charging state and the voltage values of the first resistor corresponding to the third moment and the fourth moment when the load capacitor is in a discharging state;
the processing unit is used for determining the voltage change slope of the load capacitor in a charging state and the voltage change slope of the load capacitor in a discharging state according to the voltage value of the second end of the first resistor.
6. The voltage driving circuit according to claim 5, wherein the feedback module further comprises a comparator, a negative input terminal of the comparator is electrically connected to the second terminal of the first resistor, a positive input terminal of the comparator is electrically connected to the reference voltage output terminal of the processing unit, an output terminal of the comparator is electrically connected to the first terminal of the processing unit, the reference voltage output terminal of the processing unit is configured to output the charging reference voltage value at the first time and the second time when the load capacitor is in the charging state, and the reference voltage output terminal of the processing unit is configured to output the discharging reference voltage value at the third time and the fourth time when the load capacitor is in the discharging state;
the processing unit is used for determining the voltage change slope of the load capacitor in a charging state and the voltage change slope of the load capacitor in a discharging state according to the logic value of the output end of the comparator.
7. The voltage driving circuit of claim 5, wherein the first gate driving chip is further configured to adjust a voltage value corresponding to the first gate driving signal when a voltage change slope of the load capacitor in the charging state does not conform to a first preset voltage change slope.
8. The voltage driving circuit of claim 5, wherein the second gate driving chip is further configured to adjust a voltage value corresponding to the second gate driving signal when a voltage change slope of the load capacitor in the discharging state does not conform to a second preset voltage change slope.
9. The voltage driving circuit according to claim 3, wherein the charging constant current source further comprises a bootstrap capacitor, a diode, and a third resistor;
an anode of the diode is electrically connected with a first output end of the power control module, a cathode of the diode is electrically connected with a second input end of the first gate driving chip, a first electrode of the bootstrap capacitor is electrically connected with a second input end of the first gate driving chip, a second electrode of the bootstrap capacitor is electrically connected with a second output end of the first gate driving chip, and a second electrode of the bootstrap capacitor is electrically connected with a first electrode of the load capacitor;
the first end of the third resistor is electrically connected with the first output end of the first gate driving chip, and the second end of the third resistor is electrically connected with the first electrode of the load capacitor.
10. A printer comprising the voltage drive circuit of any one of claims 1 to 9;
the printer further comprises a high-voltage spray head, a first power supply input end of the high-voltage spray head is electrically connected with a first electrode of the load capacitor, and a second power supply input end of the high-voltage spray head is grounded.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202111498114.XA CN114172365A (en) | 2021-12-09 | 2021-12-09 | Voltage drive circuit and printer |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN202111498114.XA CN114172365A (en) | 2021-12-09 | 2021-12-09 | Voltage drive circuit and printer |
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| Application Number | Title | Priority Date | Filing Date |
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| CN202111498114.XA Pending CN114172365A (en) | 2021-12-09 | 2021-12-09 | Voltage drive circuit and printer |
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Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH08336969A (en) * | 1995-04-14 | 1996-12-24 | Seiko Epson Corp | Ink-jet head driving device |
| JP2002344297A (en) * | 2001-05-17 | 2002-11-29 | Denso Corp | Driver of electric load |
| CN109062304A (en) * | 2018-05-31 | 2018-12-21 | 北京励芯泰思特测试技术有限公司 | A kind of constant current load circuit and a kind of electronic load and related system |
| CN109309992A (en) * | 2018-10-26 | 2019-02-05 | 苏州菲达旭微电子有限公司 | A kind of ripple-free LED circuit of half pressure power supply |
| CN111434106A (en) * | 2017-11-29 | 2020-07-17 | 松下半导体解决方案株式会社 | Solid-state imaging device and AB-class super-source follower |
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2021
- 2021-12-09 CN CN202111498114.XA patent/CN114172365A/en active Pending
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPH08336969A (en) * | 1995-04-14 | 1996-12-24 | Seiko Epson Corp | Ink-jet head driving device |
| JP2002344297A (en) * | 2001-05-17 | 2002-11-29 | Denso Corp | Driver of electric load |
| CN111434106A (en) * | 2017-11-29 | 2020-07-17 | 松下半导体解决方案株式会社 | Solid-state imaging device and AB-class super-source follower |
| CN109062304A (en) * | 2018-05-31 | 2018-12-21 | 北京励芯泰思特测试技术有限公司 | A kind of constant current load circuit and a kind of electronic load and related system |
| CN109309992A (en) * | 2018-10-26 | 2019-02-05 | 苏州菲达旭微电子有限公司 | A kind of ripple-free LED circuit of half pressure power supply |
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