CN113922101A - Wide-angle RCS (radar cross section) shrinkage reduction super surface based on radar wave absorption and scattering cancellation technology - Google Patents
Wide-angle RCS (radar cross section) shrinkage reduction super surface based on radar wave absorption and scattering cancellation technology Download PDFInfo
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- CN113922101A CN113922101A CN202111342357.4A CN202111342357A CN113922101A CN 113922101 A CN113922101 A CN 113922101A CN 202111342357 A CN202111342357 A CN 202111342357A CN 113922101 A CN113922101 A CN 113922101A
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/24—Polarising devices; Polarisation filters
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q15/00—Devices for reflection, refraction, diffraction or polarisation of waves radiated from an antenna, e.g. quasi-optical devices
- H01Q15/24—Polarising devices; Polarisation filters
- H01Q15/242—Polarisation converters
Abstract
The invention belongs to the technical field of antenna RCS (radar cross section) shrinkage reduction, and particularly relates to a wide-angle RCS shrinkage reduction super surface based on radar wave absorption and scattering cancellation technology, which is characterized in that: the antenna comprises an upper-layer dielectric substrate (2), a metal floor (1) and a lower-layer dielectric substrate (3), wherein radiation metal patches (11) are distributed on the upper surface of the upper-layer dielectric substrate (2), a microstrip feeder network (10) is distributed on the lower surface of the lower-layer dielectric substrate (3), and a wide-angle RCS (radar cross section) reduction super-surface antenna array (4) is formed by combining the upper-layer dielectric substrate (2), the metal floor (1) and the lower-layer dielectric substrate (3) from top to bottom in sequence. The invention is different from the conception of the prior art, and the super-surface design is carried out by combining the radar wave absorption and scattering cancellation technologies, so that the good shrinkage reduction effect can be realized in the wide-angle electromagnetic wave incidence range.
Description
Technical Field
The invention belongs to the technical field of antenna RCS (radar cross section) reduction, and particularly relates to a wide-angle RCS reduction super surface based on radar wave absorption and scattering cancellation technology, which can be used for a radar system with higher requirements on scattering characteristics.
Background
The Radar Cross Section (RCS) is the most critical concept in radar stealth technology, and it represents a physical quantity of the intensity of the echo generated by a target under the irradiation of radar waves. With the continuous development of radar detection technology, radar stealth technology plays an increasingly important role in modern electronic information systems, and particularly in the field of secure communication, how to reduce the RCS characteristics of the platform itself and an antenna installed on the platform becomes important.
The RCS reduction modes in practical scenarios that have been widely studied and applied at present include: an electromagnetic wave absorbing structure, a polarization rotating super surface, an artificial magnetic conductor, a diffuse scattering super surface and other RCS shrinkage super surfaces. The RCS reduction design method of the microstrip antenna based on the dual-polarization Van Atta array is provided in a patent published by the university of Western's electronics science and technology' of 'low RCS microstrip antenna based on the dual-polarization Van Atta array', and comprises a radiation unit, a coaxial feeder line and a 2 x 2 dual-polarization square matrix improved based on the dual-polarization Van Atta array, wherein the designed improved 2 x 2 dual-polarization square matrix consists of four dual-polarization array elements which are symmetrically distributed about the center of the radiation unit, and two pairs of microstrip connecting lines for connecting the two array elements which are symmetrical about the center of the radiation unit. Because the two pairs of microstrip connecting lines have the same electrical length, the polarizations of the electromagnetic waves reflected by the two adjacent metal patches are opposite, polarization cancellation is formed, and the characteristic of low radar scattering cross section is realized. However, this structure has the disadvantages of poor stability of the reduction angle and relatively narrow reduction angle of the incident electromagnetic wave.
Disclosure of Invention
Aiming at the defects of the prior art, the invention provides a wide-angle RCS (radar cross section) reduction super surface based on radar wave absorption and scattering cancellation technology, and can realize a good RCS reduction effect in an extremely wide electromagnetic wave incident angle.
In order to achieve the purpose, the invention designs a wide-angle RCS (radar wave absorption and scattering cancellation) shrinkage reducing super surface based on a radar wave absorption and scattering cancellation technology, which is characterized in that: the antenna comprises an upper-layer dielectric substrate 2, a metal floor 1 and a lower-layer dielectric substrate 3, wherein a radiating metal patch 11 is distributed on the upper surface of the upper-layer dielectric substrate 2, a microstrip feeder network 10 is distributed on the lower surface of the lower-layer dielectric substrate 3, and a wide-angle RCS (radar cross section) reduction super-surface antenna array 4 is formed by combining the upper-layer dielectric substrate 2, the metal floor 1 and the lower-layer dielectric substrate 3 from top to bottom in sequence;
the wide-angle RCS reduced super-surface antenna array 4 includes a first microstrip dual-polarized antenna array 41 formed by an upper dielectric substrate 2 and 4 radiating metal patches 11 thereon, a lower dielectric substrate 3 opposite to the lower dielectric substrate 3, 2 microstrip feeder networks 10 thereon, and a metal floor 1 therebetween, and a second microstrip dual-polarized antenna array 42 formed by the upper dielectric substrate 2 and 4 radiating metal patches 11 thereon adjacent to the first microstrip dual-polarized antenna array 41, the lower dielectric substrate 3 opposite to the lower dielectric substrate 3, 2 microstrip feeder networks 10 thereon, and the metal floor 1 therebetween;
the upper dielectric substrate 2 and 2 radiating metal patches 11 of the first microstrip dual-polarized antenna array 41, the lower dielectric substrate 3 opposite below, 1 microstrip feeder network 10 above the first microstrip dual-polarized antenna array, and the metal floor 1 with an I-shaped or rectangular slot 5 etched therebetween form a first microstrip dual-polarized antenna sub-array 411, and two radiating metal patches 11 adjacent to the first microstrip dual-polarized antenna sub-array 411 and 1 microstrip feeder network 10 opposite below form a second microstrip dual-polarized antenna sub-array 412;
wherein: the radiating metal patch 11 of the first microstrip dual-polarized antenna subarray 411 is located on the upper surface of the upper-layer dielectric substrate 2, the metal floor 1 etched with the I-shaped or rectangular slot 5 is located on the lower surface of the upper-layer dielectric substrate 2, the microstrip feed line network 10 is located on the lower surface of the lower-layer dielectric substrate 3, the microstrip feed line network 10 includes a T-shaped or rectangular microstrip feed line 9, a microstrip phase-shifting power divider 7 and a lumped ohmic resistor 6, the T-shaped or rectangular microstrip feed line 9 is respectively connected with branch ports of the microstrip phase-shifting power divider 7, and a combining port of the microstrip phase-shifting power divider 7 is connected to two ends of the lumped ohmic resistor 6. By adjusting the arrangement interval and arrangement layout of the first microstrip dual-polarized antenna sub-array 411 and the second microstrip dual-polarized antenna sub-array 412, the wide-angle RCS reduction super-surface antenna array 4 can realize the reduction characteristic of RCS within a wide angle.
The wide-angle RCS reduction super-surface antenna array 4 is formed by a first microstrip dual-polarized antenna array 41 and a second microstrip dual-polarized antenna array 42 in an N multiplied by M checkerboard type staggered arrangement array mode, wherein N is more than or equal to 2, M is more than or equal to 2, and N and M are integers;
the second microstrip dual-polarized antenna array 42 is obtained by rotating the first microstrip dual-polarized antenna array 41 by 90 ° along the array center thereof.
The second microstrip dual-polarized antenna sub-array 412 is obtained by rotating the first microstrip dual-polarized antenna sub-array 411 by 180 degrees along the center of the array and translating along the horizontal direction.
The shape of the radiating metal patch 11 may be circular, square or rectangular, and the length of the radiating metal patch 11 is Lg：0.25λ0≤Lg≤0.3λ0Width Wg：0.25λ0≤Wg≤0.3λ0Wherein λ is0And reducing the vacuum wavelength corresponding to the central working frequency of the super-surface antenna array 4 for the wide-angle RCS.
The I-shaped or rectangular gap 5 is composed of a first I-shaped rectangular gap 51, a second I-shaped rectangular gap 52, a third I-shaped rectangular gap 53 and a fourth I-shaped rectangular gap 54, the first I-shaped rectangular gap 51 and the second I-shaped rectangular gap 52 are perpendicular to each other, and the third I-shaped rectangular gap 53 and the fourth I-shaped rectangular gap 54 are perpendicular to each other.
The T-shaped or rectangular microstrip feed line 9 is composed of a first T-shaped or rectangular microstrip feed line 91A, a second T-shaped or rectangular microstrip feed line 91B, a third T-shaped or rectangular microstrip feed line 92A and a fourth T-shaped or rectangular microstrip feed line 92B, the first T-shaped or rectangular microstrip feed line 91A and the second T-shaped or rectangular microstrip feed line 91B are perpendicular to each other, and the third T-shaped or rectangular microstrip feed line 92A and the fourth T-shaped or rectangular microstrip feed line 92B are perpendicular to each other.
The microstrip phase-shifting power divider 7 comprises a first microstrip phase-shifting power divider 71 and a second microstrip phase-shifting power divider 72, the type of the power divider can be a wilkinson power divider or a T-type power divider, the ports of the first microstrip phase-shifting power divider 71 comprise a combining port 71A, a first branch port 71B and a second branch port 71C, and the phase difference between the ports of the first branch port 71B and the second branch port 71C of the first microstrip phase-shifting power divider 71 is theta1：60°≤θ1The phase difference of the third branch port 72B and the fourth branch port 72C of the second microstrip phase-shifting power divider 72 is theta2：θ2＝θ1The second microstrip phase-shifting power divider 72 is rotated by the first microstrip phase-shifting power divider 71 along 180-degree mirror symmetry of the center thereof and along the vertical directionAnd obtaining the direction translation.
The first microstrip dual-polarized antenna sub-array 411 is composed of a first microstrip dual-polarized antenna 4111, a second microstrip dual-polarized antenna 4112, a first microstrip phase-shifting power divider 71, a second microstrip phase-shifting power divider 72 and a collective ohmic resistor 6, a first T-shaped or rectangular microstrip feeder line 91A and a second T-shaped or rectangular microstrip feeder line 91B of a T-shaped or rectangular microstrip feeder line (9) are respectively connected with a first branch port 71B and a second branch port 71C of the first microstrip phase-shifting power divider 71, a third T-shaped or rectangular microstrip feeder line 92A and a fourth T-shaped or rectangular microstrip feeder line 92B of the T-shaped or rectangular microstrip feeder line (9) are respectively connected with a first branch port 72B and a second branch port 72C of the second microstrip phase-shifting power divider 72, the collective combining port 71A of the first microstrip phase-shifting power divider 71 and the ohmic combining port 72A of the second microstrip phase-shifting power divider 72 are connected with both ends of the ohmic resistor 6, the resistance value of the lumped resistor 6 is Re：0.1R0≤Re≤2R0Wherein R is0＝50Ω。
The first microstrip dual-polarized antenna 4111 includes a metal patch 11, an upper dielectric substrate 2, a lower dielectric substrate 3, a metal floor 1 with a first I-shaped or rectangular slot 51 and a second I-shaped or rectangular slot 52 etched thereon, a first T-shaped or rectangular microstrip feed line 91A, and a second T-shaped or rectangular microstrip feed line 91B, wherein the metal patch 11 is printed on the upper surface of the upper dielectric substrate 2, the metal floor 1 with the first I-shaped or rectangular slot 51 and the second I-shaped or rectangular slot 52 etched thereon is printed on the lower surface of the upper dielectric substrate 2, and the first T-shaped or rectangular microstrip feed line 91A and the second T-shaped or rectangular microstrip feed line 91B are printed on the lower surface of the lower dielectric substrate 3.
The second microstrip dual-polarized antenna 4112 is obtained by rotating the first microstrip dual-polarized antenna 4111 along the 180-degree mirror symmetry of the center of the antenna itself and translating along the vertical direction.
The length of the first microstrip dual-polarized antenna sub-array 411 is La：0.9λ0≤La≤1.5λ0Width of Wa：Wa＝0.5LaDielectric constant of the upper dielectric substrate 2 is ε1：1.8≤ε1Less than or equal to 3.55, thickness of H1：0.016λ0≤H1≤0.08λ0The dielectric constant of the lower dielectric substrate 3 is epsilon2：6.5≤ε2Less than or equal to 15, thickness of H2：0.008λ0≤H2≤0.038λ0The length of the wide-angle RCS reduced super-surface antenna array 4 is L2：M*La-0.05λ0≤L2≤M*La+0.25λ0Width of W2：N*La-0.05λ0≤W2≤N*La+0.25λ0Wherein λ is0The vacuum wavelength corresponding to the center operating frequency.
Compared with the prior art, the invention has the following advantages:
1. the invention connects 4T-shaped or rectangular microstrip feed lines of 2 microstrip dual-polarized antennas with branch ports of 2 microstrip phase-shifting power dividers, the combination ports of the 2 microstrip phase-shifting power dividers are connected with two ends of a lumped ohmic resistor, can simultaneously receive theta-polarized and phi-polarized incident electromagnetic waves, the received incident electromagnetic waves are emitted from the corresponding microstrip dual-polarized antennas in a co-polarized and cross-polarized mode, the polarization directions of partial emergent electromagnetic waves are opposite, and the scattering cancellation is formed, meanwhile, when the received electromagnetic waves pass through the lumped resistor on the microstrip feed lines, the intensity of the emergent electromagnetic waves is reduced due to the loss of the resistor. Through mutually combining radar wave absorption and scattering cancellation technologies, the radar wave absorption and scattering cancellation technologies jointly act on emergent electromagnetic waves, and finally the characteristic of low radar scattering cross section of the metal platform is achieved.
2. The invention improves the angle stability of the super surface by adding the lumped resistance and optimizing the microstrip dual-polarized antenna, and can realize the effect of reducing the scattering cross section of the radar within the wide-angle electromagnetic wave incidence range of +/-70 degrees.
Drawings
FIG. 1 is a schematic view of the overall structure of embodiment 1 of the present invention;
FIG. 2 is a schematic top view of the structure of embodiment 1 of the present invention;
fig. 3 is a schematic top view of a microstrip dual-polarized antenna sub-array according to embodiment 1 of the present invention;
fig. 4 is a schematic diagram of a metal patch of a microstrip dual-polarized antenna sub-array according to embodiment 1 of the present invention;
fig. 5 is a schematic diagram of a metal floor with two sets of H-shaped or rectangular slots etched in a microstrip dual-polarized antenna sub-array according to embodiment 1 of the present invention;
fig. 6 is a schematic diagram of a microstrip feeder network in which lumped ohmic resistors are loaded in microstrip dual-polarized antenna sub-arrays according to embodiment 1 of the present invention;
FIG. 7 is a schematic view of the overall structure of embodiment 4 of the present invention;
FIG. 8 is a schematic top view of the structure of embodiment 4 of the present invention;
FIG. 9 is a schematic view of the overall structure of embodiment 5 of the present invention;
FIG. 10 is a schematic top view of the structure of embodiment 5 of the present invention;
FIG. 11 is a graph comparing single station RCS versus frequency for example 1 of the present invention and a reference metal plate;
the comparison graph of single-station RCS with frequency change under the vertical irradiation of theta-polarized electromagnetic waves of the reference metal floor is shown in FIG. 11 (a);
the comparison graph of the single station RCS with the frequency change of the reference metal floor under the vertical irradiation of phi polarized electromagnetic waves is shown in FIG. 11 (b);
fig. 12 is a comparative graph of dual-station RCS as a function of azimuth angle when incident electromagnetic waves irradiate the surface of the antenna array at an oblique incidence of-70 ° with the same frequency in example 1 of the present invention and a reference metal plate.
Detailed Description
To explain the technical contents, structural features, and objects and effects of the present invention in detail, the embodiments will be described in conjunction with the detailed drawings:
example 1
Referring to fig. 1, the embodiment of the invention includes an upper dielectric substrate 2, a metal floor 1, and a lower dielectric substrate 3, wherein a radiation metal patch 11 is distributed on the upper surface of the upper dielectric substrate 2, and a microstrip feeder network 10 is distributed on the lower surface of the lower dielectric substrate 3; the wide-angle RCS reduction super-surface antenna array 4 is formed by combining an upper dielectric substrate 2, a metal floor 1 and a lower dielectric substrate 3 from top to bottom in sequence.
Referring to fig. 2, the wide-angle RCS reduced super-surface antenna array 4 includes a first microstrip dual-polarized antenna array 41 including an upper dielectric substrate 2 and 4 radiating metal patches 11 thereon, a lower dielectric substrate 3 opposite to the lower dielectric substrate 3 below, 2 microstrip feeder networks 10 thereon, and a metal floor 1 therebetween, and a second microstrip antenna array 42 including the upper dielectric substrate 2 and 4 radiating metal patches 11 thereon, the lower dielectric substrate 3 opposite to the lower dielectric substrate 11 below, and 2 microstrip feeder networks 10 thereon, and the dual-polarized metal floor 1 therebetween, which are adjacent to the first microstrip dual-polarized antenna array 41; the first microstrip dual-polarized antenna array 41 and the second microstrip dual-polarized antenna array 42 are arrayed in an N × M checkerboard arrangement, where N is greater than or equal to 2, M is greater than or equal to 2, N and M are integers, where N is 2, M is 2, and the length L of the wide-angle RCS reduction super-surface antenna array 4 is L2Is 60mm, width W2Is 60 mm.
Dielectric constant ε of the upper dielectric substrate 21Is 2.2, thickness H1Is 1.524 mm.
Dielectric constant ε of lower dielectric substrate 32Is 10.2, thickness H2Is 0.635mm, and the wide-angle RCS reduces the vacuum wavelength lambda corresponding to the central working frequency of the super-surface antenna array 40Is 31.25 mm.
The upper dielectric substrate 2 and 2 radiating metal patches 11 in the first microstrip dual-polarized antenna array 41, the lower dielectric substrate 3 opposite below, 1 microstrip feeder network 10 above and the metal floor 1 with an I-shaped or rectangular slot 5 etched therebetween form a first microstrip dual-polarized antenna sub-array 411, and two radiating metal patches 11 adjacent to the first microstrip dual-polarized antenna sub-array 411 and one microstrip feeder network 10 opposite below form a second microstrip dual-polarized antenna sub-array 412;
the radiating metal patch 11 of the first microstrip dual-polarized antenna subarray 411 is located on the upper surface of the upper-layer dielectric substrate 2, the metal floor 1 etched with the I-shaped or rectangular slot 5 is located on the lower surface of the upper-layer dielectric substrate 2, the microstrip feed line network 10 is located on the lower surface of the lower-layer dielectric substrate 3, the microstrip feed line network 10 includes a T-shaped or rectangular microstrip feed line 9, a microstrip phase-shifting power divider 7 and a lumped ohmic resistor 6, the T-shaped or rectangular microstrip feed line 9 is respectively connected with branch ports of the microstrip phase-shifting power divider 7, and a combining port of the microstrip phase-shifting power divider 7 is connected to two ends of the lumped ohmic resistor 6.
Referring to fig. 3, the first microstrip dual-polarized antenna sub-array 411 is composed of a first microstrip dual-polarized antenna 4111, a second microstrip dual-polarized antenna 4112, a first microstrip phase-shifting power divider 71, a second microstrip phase-shifting power divider 72 and a collective ohmic resistor 6, the first microstrip dual-polarized antenna 4111 includes a metal patch 11, an upper dielectric substrate 2, a lower dielectric substrate 3, a metal floor 1 with a first I-shaped or rectangular slot 51 and a second I-shaped or rectangular slot 52 etched thereon, a first T-shaped or rectangular microstrip feed line 91A and a second T-shaped or rectangular microstrip feed line 91B, wherein the metal patch 11 is printed on the upper surface of the upper-layer dielectric substrate 2, the metal floor 1 with the first I-shaped or rectangular slot 51 and the second I-shaped or rectangular slot 52 etched is printed on the lower surface of the upper-layer dielectric substrate 2, and the first T-shaped or rectangular microstrip feed line 91A and the second T-shaped or rectangular microstrip feed line 91B are printed on the lower surface of the lower-layer dielectric substrate 3. The second microstrip dual-polarized antenna 4112 is obtained by rotating the first microstrip dual-polarized antenna 4111 along the 180-degree mirror symmetry of the antenna center and translating along the vertical direction.
The length L of the first microstrip dual-polarized antenna array 411aIs 30mm in width WaIs 15 mm.
Referring to fig. 4, the radiating metal patch 11 has a square shape and a length LgIs 8.9mm and has a width WgIs 8.9 mm.
Referring to fig. 5, the I-shaped or rectangular slot 5 is composed of a first I-shaped rectangular slot 51, a second I-shaped rectangular slot 52, a third I-shaped rectangular slot 53 and a fourth I-shaped rectangular slot 54, wherein the first I-shaped rectangular slot 51 and the second I-shaped rectangular slot 52 are perpendicular to each other, and the third I-shaped rectangular slot 53 and the fourth I-shaped rectangular slot 54 are perpendicular to each other.
Referring to fig. 6, the T-shaped or rectangular microstrip feed line 9 is composed of a first T-shaped or rectangular microstrip feed line 91A, a second T-shaped or rectangular microstrip feed line 91B, a third T-shaped or rectangular microstrip feed line 92A and a fourth T-shaped or rectangular microstrip feed line 92B, the first T-shaped or rectangular microstrip feed line 91A and the second T-shaped or rectangular microstrip feed line 91B are perpendicular to each other, and the third T-shaped or rectangular microstrip feed line 92A and the fourth T-shaped or rectangular microstrip feed line 92B are perpendicular to each other.
The microstrip phase-shifting power divider 7 comprises a first microstrip phase-shifting power divider 71 and a second microstrip phase-shifting power divider 72, the selected power divider is a Wilkinson power divider, and the phase difference between the first branch port 71B and the second branch port 71C of the first microstrip phase-shifting power divider 71 is theta1Is 72 degrees, the port phase difference of the third branch port 72B and the fourth branch port 72C of the second microstrip phase-shifting power divider 72 is θ2Is 72 deg..
A first T-shaped or rectangular microstrip feeder line 91A and a second T-shaped or rectangular microstrip feeder line 91B of the T-shaped or rectangular microstrip feeder line 9 are respectively connected with a first branch port 71B and a second branch port 71C of the first microstrip phase-shifting power divider 71, a third T-shaped or rectangular microstrip feeder line 92A and a fourth T-shaped or rectangular microstrip feeder line 92B of the T-shaped or rectangular microstrip feeder line 9 are respectively connected with a first branch port 72B and a second branch port 72C of the second microstrip phase-shifting power divider 72, a combination port 71A of the first microstrip phase-shifting power divider 71 and a combination port 72A of the second microstrip phase-shifting power divider 72 are connected with two ends of the lumped ohmic resistor 6, and the resistance value of the lumped resistor 6 is ReIs 50 ohms.
Example 2
The structure of this embodiment is the same as that of embodiment 1, and the following parameters are adjusted:
dielectric constant ε of the upper dielectric substrate 21Is 2.2, thickness H1Is 1.5 mm.
Dielectric constant ε of lower dielectric substrate 32Is 10.2, thickness H2Is 0.5 mm.
Length L of metal patch 11gIs 8.7mm and has a width WgIs 8.7 mm.
Resistance value R of lumped ohmic resistor 6eIs 75 ohms.
Example 3
The structure of this embodiment is the same as that of embodiment 1, and the following parameters are adjusted:
dielectric constant ε of the upper dielectric substrate 21Is 2.0, thickness H1Is 1.2 mm.
The length L of the first microstrip dual-polarized antenna array 411aIs 40mm in width WaIs 20 mm.
Length L of metal patch 11gIs 9.1mm and has a width WgAnd 9.1 mm.
The port phase difference between the first branch port 71B and the second branch port 71C of the first microstrip phase-shifting power divider 71 is θ1Is 80 °, the port phase difference between the third branch port 72B and the fourth branch port 72C of the second microstrip phase-shifting power divider 72 is θ2Is 80 degrees.
Resistance value R of lumped ohmic resistor 6eIs 25 ohms.
Example 4
The structure of this embodiment is the same as that of embodiment 1, and the following parameters are adjusted:
referring to fig. 7 and 8, the wide-angle RCS reduced super-surface antenna array 4 is formed by a first microstrip dual-polarized antenna array 41 and a second microstrip dual-polarized antenna array 42 in an N × M checkerboard staggered arrangement, where N is greater than or equal to 2, M is greater than or equal to 2, N and M are integers, and N is greater than or equal to 3.
Wide angle RCS reduces the length L of the super-surface antenna array 42Is 90mm and has a width W2Is 90 mm.
Example 5
The structure of this embodiment is the same as that of embodiment 1, and the following parameters are adjusted:
referring to fig. 9 and 10, the wide-angle RCS reduced super-surface antenna array 4 is formed by a first microstrip dual-polarized antenna array 41 and a second microstrip dual-polarized antenna array 42 in an N × M checkerboard staggered arrangement, where N is greater than or equal to 2, M is greater than or equal to 2, N and M are integers, where N is 2, and M is 3.
Wide angle RCS reduces the length L of the super-surface antenna array 42Is 90mm and has a width W2Is 60 mm.
The technical effects of the present invention are further illustrated by the following simulation experiments in conjunction with example 1:
1. simulation conditions and contents:
1.1 with reference to figure 1 of the drawings,
the designed wide-angle RCS (radar wave absorption) shrinkage super surface based on the radar wave absorption and scattering cancellation technology comprises an upper medium substrate 2, a metal floor 1 and a lower medium substrate 3, wherein radiation metal patches 11 are distributed on the upper surface of the upper medium substrate 2, a microstrip feeder network 10 is distributed on the lower surface of the lower medium substrate 3, and a wide-angle RCS shrinkage super surface antenna array 4 is formed by combining the upper medium substrate 2, the metal floor 1 and the lower medium substrate 3 from top to bottom in sequence;
the wide-angle RCS reduced super-surface antenna array 4 is characterized in that a first microstrip dual-polarized antenna array 41 is formed by an upper dielectric substrate 2 and 4 radiating metal patches 11 on the upper dielectric substrate, a lower dielectric substrate 3 opposite to the lower dielectric substrate, 2 microstrip feeder networks 10 on the upper dielectric substrate, and a metal floor 1 between the lower dielectric substrate and the microstrip feeder networks, and a second microstrip dual-polarized antenna array 42 is formed by 4 radiating metal patches 11 adjacent to the first microstrip dual-polarized antenna array 41 and 2 microstrip feeder networks 10 opposite to the lower dielectric substrate;
the upper dielectric substrate 2 and 2 radiating metal patches 11 in the first microstrip dual-polarized antenna array 41, the lower dielectric substrate 3 opposite below, 1 microstrip feeder network 10 above and the metal floor 1 with an I-shaped or rectangular slot 5 etched therebetween form a first microstrip dual-polarized antenna sub-array 411, and two radiating metal patches 11 adjacent to the first microstrip dual-polarized antenna sub-array 411 and one microstrip feeder network 10 opposite below form a second microstrip dual-polarized antenna sub-array 412;
the radiating metal patch 11 of the first microstrip dual-polarized antenna subarray 411 is located on the upper surface of the upper-layer dielectric substrate 2, the metal floor 1 etched with the I-shaped or rectangular slot 5 is located on the lower surface of the upper-layer dielectric substrate 2, the microstrip feed line network 10 is located on the lower surface of the lower-layer dielectric substrate 3, the microstrip feed line network 10 includes a T-shaped or rectangular microstrip feed line 9, a microstrip phase-shifting power divider 7 and a lumped ohmic resistor 6, the T-shaped or rectangular microstrip feed line 9 is respectively connected with branch ports of the microstrip phase-shifting power divider 7, and a combining port of the microstrip phase-shifting power divider 7 is connected to two ends of the lumped ohmic resistor 6.
The wide-angle RCS reduced super-surface antenna array 4 is formed by a first microstrip dual-polarized antenna array 41 and a second microstrip dual-polarized antenna array 42 which are arrayed in an N multiplied by M checkerboard staggered mode, wherein N is more than or equal to 2, M is more than or equal to 2, N and M are integers, the second microstrip dual-polarized antenna array 42 is obtained by rotating the first microstrip dual-polarized antenna array 41 by 90 degrees along the center of the array, and the second microstrip dual-polarized antenna sub-array 412 is obtained by rotating the first microstrip dual-polarized antenna sub-array 411 by 180 degrees along the center of the array and translating along the horizontal direction.
1.2 simulation of wide angle RCS tapered super-surface based on radar wave absorption and scattering cancellation technique of example 1 with commercial simulation software ANSYS 2020R 2, the comparison graph of single station RCS with frequency change of example 1 and reference metal floor under perpendicular irradiation of theta polarized electromagnetic wave is shown in FIG. 11(a), and the comparison graph of single station RCS with frequency change of example 1 and reference metal floor under perpendicular irradiation of phi polarized electromagnetic wave is shown in FIG. 11 (b).
1.3 simulation calculations were performed on the two-station RCS of example 1 and the reference metal floor using the commercial simulation software ANSYS 2020R 2, and the comparative plot of the two-station RCS of example 1 and the reference metal floor as a function of azimuth angle for electromagnetic waves of the same frequency and at an oblique incidence of-70 ° is shown in fig. 10.
2. And (3) simulation results:
referring to fig. 11(a) and 11(b), the abscissa is frequency, the ordinate is single station RCS, when plane waves with theta and phi polarizations vertically irradiate the antenna array, compared with a reference metal floor, the radar scattering cross section of the antenna array in example 1 is reduced by more than 10dBsm within a frequency band of 9.26-10.1GHz, the maximum reduction amount reaches 15dBsm, and low radar cross section characteristics of the metal floor can be realized under the incident plane wave polarization conditions with theta and phi polarizations.
Referring to fig. 12, the abscissa is a phase angle, the ordinate is a two-station RCS, and when electromagnetic waves irradiate the antenna array and the surface of the reference metal floor at an oblique incidence angle of-70 ° with the same frequency, the two-station radar cross section can be reduced by more than 10dBsm compared with the reference metal floor, which shows that the low radar cross section characteristic of the reference metal floor is realized within a wide incidence angle range of ± 70 °.
The foregoing description is only a specific example of the present invention and should not be construed as limiting the invention in any way, and it will be apparent to those skilled in the art that various modifications and variations in form and detail can be made without departing from the principle and structure of the invention, but these modifications and variations will still fall within the scope of the appended claims.
Claims (12)
1. A wide-angle RCS (radar cross section) shrinkage reducing super surface based on radar wave absorption and scattering cancellation technology is characterized in that:
the antenna comprises an upper-layer dielectric substrate (2), a metal floor (1) and a lower-layer dielectric substrate (3), wherein radiation metal patches (11) are distributed on the upper surface of the upper-layer dielectric substrate (2), a microstrip feeder network (10) is distributed on the lower surface of the lower-layer dielectric substrate (3), and a wide-angle RCS (radar cross section) reduction super-surface antenna array (4) is formed by combining the upper-layer dielectric substrate (2), the metal floor (1) and the lower-layer dielectric substrate (3) from top to bottom in sequence;
the wide-angle RCS reduction super-surface antenna array (4) is characterized in that a first microstrip dual-polarized antenna array (41) is formed by an upper-layer dielectric substrate (2) and 4 radiating metal patches (11) in the wide-angle RCS reduction super-surface antenna array, a lower-layer dielectric substrate (3) opposite to the lower side, 2 microstrip feeder networks (10) on the lower side and a metal floor (1) between the upper-layer dielectric substrate and the lower-layer dielectric substrate, 4 radiating metal patches (11) adjacent to the first microstrip dual-polarized antenna array (41) and 2 microstrip feeder networks (10) opposite to the lower side form a second microstrip dual-polarized antenna array (42);
the upper-layer dielectric substrate (2) and the upper 2 radiating metal patches (11) in the first microstrip dual-polarized antenna array (41), the lower-layer dielectric substrate (3) opposite below, the upper 1 microstrip feeder network (10) and the metal floor (1) with the I-shaped slot (5) etched therebetween form a first microstrip dual-polarized antenna sub-array (411), and the upper-layer dielectric substrate (2) and the upper 2 radiating metal patches (11) in the first microstrip dual-polarized antenna sub-array (411) adjacent to the first microstrip dual-polarized antenna sub-array form a second microstrip dual-polarized antenna sub-array (412) with the lower-layer dielectric substrate (3) opposite below, the upper 1 microstrip feeder network (10) and the metal floor (1) with the I-shaped slot (5) etched therebetween;
wherein: a radiation metal patch (11) of a first microstrip dual-polarized antenna sub-array (411) is located on the upper surface of an upper-layer dielectric substrate (2), a metal floor (1) etched with an I-shaped slot (5) is located on the lower surface of the upper-layer dielectric substrate (2), a microstrip feed line network (10) is located on the lower surface of a lower-layer dielectric substrate (3), the microstrip feed line network (10) comprises a T-shaped or rectangular microstrip feed line (9), a microstrip phase-shifting power divider (7) and a lumped ohmic resistor (6), the T-shaped or rectangular microstrip feed line (9) is respectively connected with branch ports of the microstrip phase-shifting power divider (7), and combined ports of the microstrip phase-shifting power divider (7) are connected to two ends of the lumped ohmic resistor (6). By adjusting the arrangement interval and arrangement layout mode of the first microstrip dual-polarized antenna sub-array (411) and the second microstrip dual-polarized antenna sub-array (412), the wide-angle RCS reduction super-surface antenna array (4) can realize the reduction characteristic of RCS in a wide angle.
2. The radar-absorbing and scattering cancellation super surface based on the wide-angle RCS is characterized in that the wide-angle RCS reduction super surface antenna array (4) is formed by arraying a first microstrip dual-polarized antenna array (41) and a second microstrip dual-polarized antenna array (42) in an N x M checkerboard type staggered arrangement mode, wherein N is larger than or equal to 2, M is larger than or equal to 2, and N and M are integers.
3. The wide-angle RCS (radar absorbing and scattering cancellation) super-surface according to claim 1, wherein the second microstrip dual-polarized antenna array (42) is obtained by rotating the first microstrip dual-polarized antenna array (41) by 90 ° along the center of the array.
4. The wide-angle RCS (radar absorbing and scattering cancellation) super-surface according to claim 1, wherein the second microstrip dual-polarized antenna sub-array (412) is obtained by rotating the first microstrip dual-polarized antenna sub-array (411) by 180 degrees along the center of the array and translating the first microstrip dual-polarized antenna sub-array in the horizontal direction.
5. The wide-angle RCS (radar absorbing and scattering cancellation) super surface according to claim 1, wherein the radiating metal patch (11) is in the shape of a circle, a square or a rectangle, and the length of the radiating metal patch (11) is Lg：0.25λ0≤Lg≤0.3λ0Width Wg：0.25λ0≤Wg≤0.3λ0Wherein λ is0And reducing the vacuum wavelength corresponding to the central working frequency of the super-surface antenna array (4) for the wide-angle RCS.
6. The radar wave absorption and scattering cancellation technology-based wide-angle RCS (radar cross section) shrinkage super surface according to claim 1, wherein the I-shaped slits (5) are composed of a first I-shaped rectangular slit (51), a second I-shaped rectangular slit (52), a third I-shaped rectangular slit (53) and a fourth I-shaped rectangular slit (54), the first I-shaped rectangular slit (51) and the second I-shaped rectangular slit (52) are perpendicular to each other, and the third I-shaped rectangular slit (53) and the fourth I-shaped rectangular slit (54) are perpendicular to each other.
7. The radar absorbing and scattering cancellation technology-based wide-angle RCS tapered super-surface according to claim 1, wherein the T-shaped or rectangular microstrip feed line (9) is composed of a first T-shaped or rectangular microstrip feed line (91A), a second T-shaped or rectangular microstrip feed line (91B), a third T-shaped or rectangular microstrip feed line (92A) and a fourth T-shaped or rectangular microstrip feed line (92B), the first T-shaped or rectangular microstrip feed line (91A) and the second T-shaped or rectangular microstrip feed line (91B) are perpendicular to each other, and the third T-shaped or rectangular microstrip feed line (92A) and the fourth T-shaped or rectangular microstrip feed line (92B) are perpendicular to each other.
8. The wide-angle RCS (radar wave absorption and scattering cancellation) super-surface according to claim 1, wherein the microstrip phase-shifting power divider (7) comprises a first microstrip phase-shifting power divider (71) and a second microstrip phase-shifting power divider (72), the type of the power divider used can be a Wilkinson power divider or a T-type power divider, the ports of the first microstrip phase-shifting power divider (71) comprise a combining port (71A), a first branch port (71B) and a second branch port (71C), and the phase difference between the ports of the first branch port (71B) and the second branch port (71C) of the first microstrip phase-shifting power divider (71) is θ1：60°≤θ1Not more than 120 degrees, and the port of the second microstrip phase-shifting power divider (72) comprises a path combining endA port (72A), a third branch port (72B) and a fourth branch port (72C), and the phase difference between the third branch port (72B) and the fourth branch port (72C) of the second microstrip phase-shifting power divider (72) is theta2：θ2＝θ1The second microstrip phase-shifting power divider (72) is obtained by rotating the first microstrip phase-shifting power divider (71) along 180-degree mirror symmetry of the center of the first microstrip phase-shifting power divider and translating along the vertical direction.
9. The wide-angle RCS (radar absorbing and scattering cancellation) super-surface based on radar wave absorption and scattering cancellation technology according to claim 1, wherein the first microstrip dual-polarized antenna sub-array (411) is composed of a first microstrip dual-polarized antenna (4111), a second microstrip dual-polarized antenna (4112), a first microstrip phase-shifting power divider (71), a second microstrip phase-shifting power divider (72) and a total ohmic resistor (6), a first T-shaped or rectangular microstrip feed line (91A) and a second T-shaped or rectangular microstrip feed line (91B) of a T-shaped or rectangular microstrip feed line (9) are respectively connected with a first branch port (71B) and a second branch port (71C) of the first microstrip phase-shifting power divider (71), and a third T-shaped or rectangular microstrip feed line (92A) and a fourth T-shaped or rectangular microstrip feed line (92B) of the T-shaped or rectangular microstrip feed line (9) are respectively connected with a first branch port (72B) and a second branch port (72B) of the second microstrip power divider (72) C) The combining port (71A) of the first microstrip phase-shifting power divider (71) and the combining port (72A) of the second microstrip phase-shifting power divider (72) are connected with two ends of the lumped ohmic resistor (6), and the resistance value of the lumped resistor (6) is Re：0.1R0≤Re≤2R0Wherein R is0＝50Ω。
10. The wide-angle RCS tapered super-surface based on radar wave absorption and scattering cancellation technology of claim 9, the antenna is characterized in that the first microstrip dual-polarized antenna (4111) comprises a metal patch (11), an upper-layer dielectric substrate (2) and a lower-layer dielectric substrate (3) which are stacked and distributed from top to bottom, a metal floor (1) for etching a first I-shaped slot (51) and a second I-shaped slot (52), a first T-shaped or rectangular microstrip feeder line (91A) and a second T-shaped or rectangular microstrip feeder line (91B), the metal patch (11) is printed on the upper surface of the upper-layer dielectric substrate (2), the metal floor (1) with the first I-shaped slot (51) and the second I-shaped slot (52) etched is printed on the lower surface of the upper-layer dielectric substrate (2), and the first T-shaped or rectangular microstrip feeder line (91A) and the second T-shaped or rectangular microstrip feeder line (91B) are printed on the lower surface of the lower-layer dielectric substrate (3).
11. The radar absorbing and scattering cancellation based wide-angle RCS reduced super-surface according to claim 9, wherein the second microstrip dual polarized antenna (4112) is obtained by a first microstrip dual polarized antenna (4111) rotating in 180 ° mirror symmetry from its antenna center and translating in a vertical direction.
12. The wide-angle RCS (radar absorbing and scattering cancellation) super-surface according to claim 1, wherein the length L of the first microstrip dual-polarized antenna sub-array (411) isa：0.9λ0≤La≤1.5λ0Width Wa：Wa＝0.5LaDielectric constant ε of upper dielectric substrate (2)1：1.8≤ε1Less than or equal to 3.55, thickness H1：0.016λ0≤H1≤0.08λ0Dielectric constant ε of lower dielectric substrate (3)2：6.5≤ε2Less than or equal to 15, thickness H2：0.008λ0≤H2≤0.038λ0Said wide angle RCS reducing the length L of the super surface antenna array (4)2：M*La-0.05λ0≤L2≤M*La+0.25λ0Width W2：N*La-0.05λ0≤W2≤N*La+0.25λ0Wherein λ is0And reducing the vacuum wavelength corresponding to the central working frequency of the super-surface antenna array (4) for the wide-angle RCS.
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