CN113497560B - Control method of buck-boost converter - Google Patents

Control method of buck-boost converter Download PDF

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CN113497560B
CN113497560B CN202110837566.XA CN202110837566A CN113497560B CN 113497560 B CN113497560 B CN 113497560B CN 202110837566 A CN202110837566 A CN 202110837566A CN 113497560 B CN113497560 B CN 113497560B
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input
voltage
output
stage
switching tube
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CN113497560A (en
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不公告发明人
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Mornsun Guangzhou Science and Technology Ltd
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Mornsun Guangzhou Science and Technology Ltd
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention relates to the field of switching converters, in particular to a control method of a buck-boost converter, which comprises the following steps: according to the input voltage and the output voltage or the input voltage, the output voltage and the output current, the time of the input stage and the time of the output stage are dynamically adjusted, so that the peak value of the inductive current of the buck-boost circuit in the full input and output voltage range is smaller, the turn-off loss and the turn-on loss of the switching tube are reduced, and the output efficiency of the buck-boost converter in the wide input and output voltage range is improved.

Description

Control method of buck-boost converter
Technical Field
The invention relates to the field of switching converters, in particular to a control method of a buck-boost converter.
Background
The BUCK-BOOST BUCK-BOOST circuit can be used in the situation that the input voltage is greater than, equal to or less than the output voltage. Please refer to fig. 1 and fig. 2, a U.S. patent with patent number 10/214,859, entitled "BUCK-BOOST DC-DC SWITCHING power converter", discloses a control method of a BUCK-BOOST DC-DC switching power converter, which discloses a time control method of each stage of BUCK-BOOST, wherein the control of an input stage T1 and an input/output stage T2 introduces a partial voltage of an input voltage Vin and an output voltage Vo, and the partial voltage adopts a fixed partial voltage resistor. In the examples, two further optimization measures are given: 1. frequency conversion mode: the lengths of the input stage T1 and the input and output stage T2 are fixed, and the length of the clamping stage T4 is changed to adjust the output working voltage, as shown in FIG. 1; 2. frequency-fixed mode: the length of the input-output phase T1 is changed to adjust the voltage by fixing the period TFIX and the length of the input-output phase T2, as shown in fig. 2.
However, in the application of wide-input-output buck-boost, it is difficult to optimize the full-duty efficiency in any fixed stage, for example, in the above-mentioned variable-frequency mode, when the input voltage Vin is much smaller than the output voltage Vo, the input stage T1 time is longer to satisfy the output power, and if the input stage T1 is fixed, when the input voltage Vin is much larger than the output voltage Vo, the inductor current I flowing through the inductor L is within the fixed input stage T1 timeLThe peak will be very large, reducing the overall system efficiency.
In the constant frequency mode, when the input voltage Vin is much smaller than the output voltage Vo, the input stage T1 decreases with the decrease of the load, the input/output stage T2 is fixed, and when the input/output stage T2 ends, the inductor current flows backward, which results in abnormal sequential logic. The two control methods of the four-pipe BUCK-BOOST are not suitable for wide input and output application occasions.
IN U.S. patent No. 15/227,722 entitled "REDUCING SWITCHING loss IN POWER CONVERTERS", the measures to optimize the input phase T1 are further given: the input phase T1 is the inversion time TX of the input phase + the storage duration TS of the energy stored in the inductor, as shown in fig. 3, and is mainly characterized by: the minimum duration TSZ of the storage phase, that is, the time of the minimum input phase T1, may be set to ensure that, during a light load, the exciting current of the inductor can enable the switching tube S3 to achieve ZVS (zero voltage switching on) in the time of the minimum input phase T1, thereby achieving ZVS of all switching tubes over a wide range of loads. The patent only optimizes the input stage T1 in light load, and cannot realize efficient regulation in a wide input and output voltage range.
In U.S. patent No. 15/368,208 entitled CONTROL OF BUCK-BOOST POWER CONVERTER WITH INPUT VOLTAGE TRACKING, further measures are given to optimize the INPUT output stage T2: in very narrow input-output voltage applications, high efficiency in a narrow range is achieved by increasing the input-output period T2 time, as shown in fig. 4. The patent is only suitable for narrow-range application occasions, and efficient regulation in a wide input and output voltage range cannot be realized.
In summary, the conventional BUCK BOOST control method is not suitable for wide input/output voltage applications, and has the problems of abnormal timing logic and low efficiency in a wide input/output voltage range.
Disclosure of Invention
In view of the problems that the existing BUCK BOOST power converter control method has abnormal time sequence logic and cannot realize high efficiency in a full voltage range in the application occasions of wide input voltage Vin and wide output voltage Vo, the invention provides a control method of a BUCK-BOOST circuit, which ensures that the BUCK-BOOST circuit has normal time sequence logic and smaller inductive current peak value, reduces the conduction loss and turn-off loss of a power device in a wider input and output range by self-adaptive dynamic regulation of an input stage T1 and an input and output stage T2, and improves the overall efficiency.
In order to achieve the purpose, the invention adopts the following technical scheme:
a control method of a buck-boost converter is used for controlling the buck-boost converter, and a main power circuit of the buck-boost converter comprises an input end used for receiving an input voltage, an output end used for generating an output voltage, a switch assembly and an inductor; the switch assembly is provided with a switch tube Q1, a switch tube Q2, a switch tube Q3 and a switch tube Q4; the working time sequence of the main power circuit in one working period is divided into four stages, wherein the four stages are an input stage, an input-output stage, an output stage and a clamping stage in sequence; in the input stage, the switching tube Q1 and the switching tube Q4 are switched on, and the switching tube Q2 and the switching tube Q3 are switched off; in the input and output stage, the switching tube Q1 and the switching tube Q3 are switched on, and the switching tube Q2 and the switching tube Q4 are switched off; in the output stage, the switching tube Q2 and the switching tube Q3 are switched on, and the switching tube Q1 and the switching tube Q4 are switched off; in the clamping stage, the switching tube Q2 and the switching tube Q4 are switched on, and the switching tube Q1 and the switching tube Q3 are switched off, wherein the control method comprises the following steps:
when the input voltage is smaller than the output voltage, dynamically adjusting the time of the input stage and the time of the output stage according to the input voltage and the output voltage or according to the input voltage, the output voltage and the output current of the main power circuit, specifically: under the condition that the zero-voltage switching-on condition of the switching tube Q2 in the output stage is met, the current peak value of the inductor is reduced by reducing the time of the input stage and increasing the time of the input stage and the output stage;
when the input voltage is greater than or equal to the output voltage, dynamically adjusting the time of the input stage and the time of the output stage according to the input voltage and the output voltage or according to the input voltage, the output voltage and the output current of the main power circuit, specifically: under the condition that the zero-voltage switching-on condition of the switching tube Q3 in the input and output stage is met, the current peak value of the inductor is reduced by reducing the time of the input stage and increasing the time of the input and output stage.
Preferably, when the input voltage is smaller than the output voltage, the peak current value of the inductor is reduced by minimizing the time of the input phase and maximizing the time of the input and output phases under the condition that the zero-voltage turn-on condition of the switching tube Q2 can be realized in the output phase.
Preferably, when the input voltage is greater than or equal to the output voltage, the current peak value of the inductor is reduced by minimizing the time of the input stage and maximizing the time of the input stage under the condition that the zero-voltage turn-on condition of the switching tube Q3 can be realized in the input and output stage.
Preferably, the control signals of the input stage and the input/output stage are generated by combining a plurality of groups of voltage dividing resistors controlled by the input voltage and/or the output voltage in parallel.
Preferably, the control signals for the input stage and the input-output stage are generated by a combination of a plurality of sets of three-terminal controllers and fixed resistors controlled by the input voltage and the output voltage or by the input voltage, the output voltage and the output current of the main power circuit.
Preferably, the control signals of the input stage and the input/output stage are generated by adopting a plurality of groups of voltage-controlled constant current source conversion coefficients controlled by the input voltage and/or the output voltage, wherein the conversion coefficients of the voltage-controlled constant current source are a function, and variables in the function comprise the input voltage and/or the output voltage; or generating control signals of the input stage and the input and output stage by adopting a mode of a plurality of groups of voltage-controlled constant current source conversion coefficients controlled by input voltage, output voltage and output current of the main power circuit, wherein the conversion coefficients of the voltage-controlled constant current source are a function, and variables in the function comprise the input voltage, the output voltage and the output current of the main power circuit.
Preferably, the control signals for the input and output phases are generated by sampling the input and output voltages with a digital controller and generating a function on the input and/or output voltages with the digital controller.
Preferably, the first two or three parameters of the input voltage, the output voltage and the output current are sampled by using a digital controller, and the control signals for the input stage and the input-output stage are generated by a table look-up method.
Compared with the prior art, the invention has the following beneficial effects:
under any input and output working condition, relevant signals of the buck-boost controller are sampled, the sampled signals are not limited to parameters such as input voltage, output voltage and output current, the input stage and the input and output stage are dynamically adjusted in a self-adaptive mode, the current peak value of the inductor of the buck-boost circuit in the full input and output voltage range is small, therefore, turn-off loss and turn-on loss of a switch tube are reduced, and output efficiency of the buck-boost converter in the wide input and output voltage range is improved.
Drawings
Fig. 1 is a waveform diagram of an inductor current in a buck-boost frequency conversion mode in the prior art;
fig. 2 is a waveform diagram of the inductor current in the conventional buck-boost constant frequency mode;
fig. 3 is a waveform diagram of the inductor current at the input stage of the buck-boost buck optimization;
fig. 4 is a waveform diagram of the inductor current in the stage of optimizing input and output of the buck-boost buck boost;
FIG. 5 is a main power circuit diagram of the buck-boost converter of the present invention;
FIG. 6 is a timing logic diagram of a buck-boost converter according to the present invention;
FIG. 7 is a schematic diagram of a control circuit for an input stage of the buck-boost converter of the present invention;
FIG. 8 is a schematic diagram of a control circuit for the input/output stage of the buck-boost converter according to the present invention;
FIG. 9(a) is a waveform diagram of the inductor current when the input voltage is less than the output voltage according to the present invention;
FIG. 9(b) is a waveform diagram of the inductor current when the input voltage is equal to the output voltage according to the present invention;
FIG. 9(c) is a waveform diagram of the inductor current when the input voltage is greater than the output voltage according to the present invention;
fig. 10(a) is a schematic diagram of an input stage control circuit in embodiment 1 of the present invention;
fig. 10(b) is a schematic diagram of a control circuit in the input/output stage according to embodiment 1 of the present invention;
fig. 11(a) is a schematic diagram of a control circuit of an input stage in embodiment 2 of the present invention;
fig. 11(b) is a schematic diagram of a control circuit of an input/output stage in embodiment 2 of the present invention;
fig. 12(a) is a schematic diagram of a control circuit of an input stage according to embodiment 3 of the present invention;
fig. 12(b) is a schematic diagram of a control circuit of an input/output stage according to embodiment 3 of the present invention;
fig. 13(a) is a schematic diagram of a control circuit of an input stage according to embodiment 4 of the present invention;
fig. 13(b) is a schematic diagram of a control circuit in an input/output stage according to embodiment 4 of the present invention;
FIG. 14(a) is a schematic diagram of a control circuit of an input stage in embodiment 5 of the present invention;
fig. 14(b) is a schematic diagram of a control circuit of an input/output stage in embodiment 5 of the present invention;
FIG. 15 is a diagram illustrating a table lookup method in embodiment 5 of the present invention.
Detailed Description
The invention is described in detail below with reference to the figures and the specific embodiments.
Referring to fig. 5, fig. 5 is a main power circuit of a buck-boost converter according to the present invention. The main power circuit comprises an input end for receiving input voltage Vin, an input capacitor Cin for input filtering, an output end for generating output voltage Vo, an output capacitor Co for output filtering, a power supply common ground GND, a switch assembly and an inductor L. The switch component comprises a switch tube Q1, a switch tube Q2, a switch tube Q3 and a switch tube Q4.
Fig. 6 shows a sequential logic diagram of the main power circuit according to the present invention, the working sequence of the main power circuit in one working cycle is divided into four stages, and the four stages sequentially include an input stage T1, an input/output stage T2, an output stage T3, and a clamping stage T4.
In the input stage T1, the switching tube Q1 and the switching tube Q4 are turned on, and the switching tube Q2 and the switching tube Q3 are turned off; in the input and output stage T2, the switching tube Q1 and the switching tube Q3 are turned on, and the switching tube Q2 and the switching tube Q4 are turned off; in the output stage T3, the switching tube Q2 and the switching tube Q3 are turned on, and the switching tube Q1 and the switching tube Q4 are turned off; in the clamping stage T4, the switching tube Q2 and the switching tube Q4 are turned on, and the switching tube Q1 and the switching tube Q3 are turned off.
The time of the input stage T1 is controlled by the control signal generated by the input stage control circuit shown in fig. 7, and the control principle of the input stage T1 time is as follows: the starting time of the input stage T1 is determined by the starting time of each duty cycle, the ending time of the input stage T1 is determined by the control signal output by the comparator U1, the voltage input by the positive input terminal of the comparator U1 is the triangular wave voltage UC1, and the triangular wave voltage UC1 can be generated by charging the capacitor C1 by the controlled voltage-controlled constant current source U3. The controlled voltage-controlled constant current source U3 has its output current controlled by the input voltage or the input voltage and the output current.
The time of the input/output phase T2 is controlled by the control signal generated by the input/output phase control circuit shown in fig. 8, and the time control principle of the input/output phase T2 is as follows: the start time of the input/output stage T2 is determined by the end time of the input stage T1, the end time of the input/output stage T2 is determined by the control signal output by the comparator U2, the voltage at the positive input end of the comparator U2 is the triangular wave voltage UC2, and the triangular wave voltage UC2 can be generated by charging the capacitor C2 by the controlled voltage-controlled constant current source U4. The controlled voltage controlled constant current source U4 has an output current that is a function of the input voltage and the output voltage, or a function of the input voltage, the output voltage, and the output current.
The timing of the output phase T3 is adaptively controlled by negative current.
The time of the clamping stage T4 is controlled by a timer and the voltage of a switch tube Q4 terminal.
Referring to fig. 9(a) to 9(c), a method for controlling the buck-boost converter according to the present invention will be described. The core of the control method is to control the time of an input stage T1 and the time of an input/output stage T2, and the control method specifically comprises the following steps:
referring to fig. 9(a), when the input voltage Vin is smaller than the output voltage Vo, according to the collected values of the input voltage Vin and the output voltage Vo, or the values of the input voltage Vin, the output voltage Vo, and the output current Io, when the input-output phase T2 is completed, the inductor current IL flowing through the inductor L can dynamically adjust the time of the input phase T1 and the time of the input-output phase T2 under the condition that the output phase T3 switching tube Q2 is turned on at zero voltage.
The time for adjusting the input stage T1 and the input/output stage T2 is specifically: in one working cycle, under the condition that the zero-voltage switching-on condition of the switching tube Q2 in the output stage T3 is met, the current peak value of the inductor is reduced by reducing the time of the input stage T1 to the maximum extent, increasing the time of the input stage T2 to the maximum extent and reducing the time of the output stage T3 and the clamping stage T4 to the maximum extent.
The condition that the inductor current IL flowing through the inductor L can meet zero-voltage turn-on of the switching tube Q2 at the output stage T3 is specifically as follows: at the initial time of the output stage T3, the inductor current IL resonates with the junction capacitor COSS at the drain terminal of the switching transistor Q2, and the magnitude of the inductor current IL is required to meet the condition that the voltage at the drain terminal of the switching transistor Q2 is reduced to 0V or a lower threshold voltage, so as to meet the zero-voltage turn-on condition (ZVS) of the switching transistor Q2.
As can be seen from fig. 9(a), when the input voltage Vin is smaller than the output voltage Vo, compared with the inductor current curve represented by the dashed line (the curve of the prior art), the present invention effectively improves the efficiency of the buck-boost converter by decreasing the peak value of the inductor current IL in the input stage T1 and increasing the time of the input stage T2 (see the solid line portion) under the condition that the zero-voltage turn-on condition of the switching tube Q2 in the output stage T3 can be achieved.
Referring to fig. 9(b) and 9(c), when the input voltage Vin is greater than or equal to the output voltage Vo, according to the magnitudes of the input voltage Vin and the output voltage Vo, or the magnitudes of the input voltage Vin, the output voltage Vo, and the output current Io, when the input stage T1 is completed, the inductor current IL flowing through the inductor L can dynamically adjust the time of the input stage T1 and the time of the input stage T2 under the condition that the switch Q3 of the input-output stage T2 realizes zero-voltage turn-on.
The time for adjusting the input stage T1 and the input/output stage T2 is specifically: in a working cycle, under the condition that the zero-voltage switch-on condition of the switching tube Q3 in the input-output stage T2 is met, the time of the input stage T1 is reduced to the maximum extent, and the time of the input-output stage T2 is increased to the maximum extent, so that the current peak value of the inductor is reduced.
The inductor current IL flowing through the inductor L can satisfy the zero-voltage switching-on condition of the switching tube Q3 at the input and output stage T2, specifically: at the beginning of the input/output stage T2, at this time, the inductor current IL resonates with the junction capacitor COSS at the drain terminal of the switching tube Q3, and the magnitude of the inductor current IL should meet the condition that the voltage at the drain terminal of the switching tube Q3 is reduced to 0V or a lower threshold voltage, so as to meet the zero-voltage turn-on condition (ZVS) of the switching tube Q3.
As can be seen from fig. 9(b) and 9(c), when the input voltage Vin is equal to or greater than the output voltage Vo, compared with the inductor current curve represented by the dotted line (the prior art curve), the peak value of the inductor current IL is reduced by reducing the input period T1 and increasing the time of the input period T2 (see the solid line portion) under the condition that the zero-voltage turn-on condition of the switching tube Q3 in the input and output periods T2 and T3 is satisfied, so that the efficiency of the buck-boost converter is effectively improved.
Example one
Referring to fig. 10(a), fig. 10(a) is a schematic diagram of an input stage control circuit in embodiment 1 of the present invention,
the input stage control circuit comprises a first voltage-dividing resistor component, a first switch group, a voltage-controlled constant current source U3, a charging capacitor C1 and a comparator U1. Wherein, first divider resistance assembly includes: the voltage divider comprises a voltage dividing resistor combination consisting of a voltage dividing resistor R1_1 and a voltage dividing resistor R2_1, a voltage dividing resistor combination consisting of a voltage dividing resistor R1_2 and a voltage dividing resistor R2_2, and a voltage dividing resistor combination consisting of a voltage dividing resistor R1_ N and a voltage dividing resistor R2_ N.
Each divider resistor combination is correspondingly connected with each switch a1, a2.. AN in the first switch group, the output end of each switch a1, a2.. AN is connected with the positive input end of the voltage-controlled constant current source U3, the output end of the voltage-controlled constant current source U3 is connected with one end of the charging capacitor C1 and the positive input end of the comparator U1, the negative input end of the comparator U1 is connected with the output signal Verr of the error amplifier of the buck-boost converter, and the output end of the comparator U1 outputs a control signal for controlling the time of the input stage T1.
The working principle of the input stage control circuit is as follows: the input voltage Vin is segmented into N segments, wherein N can be any natural number, and the input voltage Vin can be divided into Vin1-Vin2, Vin2-Vin3,... so, Vin (N-1) -VinN.
Each voltage segment corresponds to one switch of a first switch group consisting of N switches a1, a2.. AN.
When the input voltage Vin is within the voltage range of Vin1-Vin2, the switch a1 is turned on, the switch a1 is connected with a group of voltage dividing resistors R1_1 and R2_1 of the input voltage Vin, and the values of the voltage dividing resistors R1_1 and R2_1 are the optimal solutions corresponding to the input voltage sections Vin1-Vin 2.
Similarly, when the input voltage Vin is within the voltage range of Vin12-Vin3, the switch a2 is turned on, the switch a2 is connected with a group of voltage dividing resistors R1_2 and R2_2 of the input voltage Vin, and the values of the voltage dividing resistors R1_2 and R2_2 are the optimal solutions corresponding to the input voltage section Vin2-Vin 3.
Similarly, when the input voltage Vin is within the voltage range of Vin (N-1) -Vin2(N), the switch AN is turned on, the switch AN is connected with a group of voltage dividing resistors R1_ N and R2_ N of the input voltage Vin, and the values of the voltage dividing resistors R1_ N and R2_ N are the optimal solutions corresponding to the input voltage section Vin (N-1) -Vin2 (N).
When the input stage control circuit works: the input of the voltage-controlled constant current source U3 is connected with the voltage of the input voltage Vin after being divided by the voltage dividing resistor of the matching voltage section, the output current of the voltage-controlled constant current source U3 charges the charging capacitor C1, and the voltage U at the two ends of the charging capacitor C1C1The positive input end of the comparator U1 is connected, the negative input end of the comparator U1 is connected with the output signal Verr of the error amplifier, and the time of the input stage T1 is equal to the voltage U at the two ends of the charging capacitor C1C1The time it takes to charge from 0V to the same voltage as output signal Verr.
Referring to fig. 10(b), fig. 10(b) is a schematic diagram of an input/output stage control circuit according to embodiment 1 of the present invention, where the input/output stage control circuit includes: second divider resistance component, third divider resistance component, second switch group, difference circuit U5, voltage-controlled constant current source U4, comparator U2 and charging capacitor C2, wherein, the second divider resistance component includes: a voltage dividing resistor combination consisting of a voltage dividing resistor R3_1 and a voltage dividing resistor R4_1, a voltage dividing resistor combination consisting of a voltage dividing resistor R3_2 and a voltage dividing resistor R4_2, and a voltage dividing resistor combination consisting of a voltage dividing resistor R3_ N and a voltage dividing resistor R4_ N; the third voltage dividing resistor component comprises a voltage dividing resistor R5 and a voltage dividing resistor R6.
Each voltage-dividing resistor combination in the second voltage-dividing resistor assembly is correspondingly connected with each switch B1, B2, n, BN in the second switch group, and the output end of each switch B1, B2, n, BN is connected with the positive input end of the difference circuit U5; the negative input terminal of the differential circuit U5 is connected to the connection point of the voltage-dividing resistor R5 and the voltage-dividing resistor R6 in the third voltage-dividing resistor component.
The input and output stage control circuit principle is as follows: and carrying out segmentation coefficient configuration on the input voltage Vin, and not segmenting the output voltage Vo. The input voltage Vin section coefficient configuration is to section an input voltage Vin, the input voltage Vin can be divided into N sections, N can be any natural number, and the input voltage Vin can be divided into Vin1-Vin2, Vin2-Vin3, Vin (N-1) -VinN.
Each voltage segment corresponds to a switch in a second switch group consisting of N switches B1, B2, · BN, respectively.
When the input voltage Vin is within the voltage range of Vin1-Vin2, the switch B1 is turned on, and the switch B1 is communicated with a group of voltage dividing resistors R3_1 and R4_1 of the input voltage Vin. Similarly, when the input voltage Vin is within the voltage range of Vin (N-1) -Vin2(N), the switch BN is turned on, and the switch BN is connected with a group of voltage dividing resistors R3_ N, R4_ N of the input voltage Vin.
When the input and output stage control circuit works: the input voltage Vin is connected to the positive input end of a differential circuit U5 after being divided by a voltage dividing resistor of a matched voltage section, the output voltage Vo is connected to the negative input end of the differential circuit U5 after being divided by a fixed resistor R5 and a resistor R6, the output voltage of the differential circuit U5 is connected to the input end of a voltage-controlled constant current source U4, the output current of the voltage-controlled constant current source U4 charges a charging capacitor C2, and the voltage U at the two ends of the charging capacitor C2C2Connected to the positive input of comparator U2, of comparator U2The negative input end is connected with the output signal Verr of the error amplifier, and the total time of the input stage T1 and the input and output stage T2 is equal to the voltage U at the two ends of the charging capacitor C2C2The time it takes to charge from 0V to the same voltage as the output signal Verr. In other words, the time of the input/output stage T2 is equal to the voltage U across the charging capacitor C2C2The voltage U across the charging capacitor C1 is subtracted from the time it takes to charge 0V to the same voltage as the output signal VerrC1The time it takes to charge from 0V to the same voltage as the output signal Verr.
In this embodiment, the relationship between the input voltage segment and the conducting switch is shown in table 1 below.
TABLE 1
Input voltage segmentation Conducting switch Conducting switch
Vin1——Vin2 A1 B1
Vin2——Vin3 A2 B2
...... ...... ......
VinN-1——VinN AN BN
The value of each voltage dividing resistor is the optimal solution corresponding to a certain input voltage segment, which can be understood as follows: in any input voltage segment, due to the values of the divider resistors R1_ N, R2_ N, R3_ N, R4_ N, R5 and R6, when the input voltage Vin is greater than or equal to the output voltage Vo, under the condition that the zero-voltage switching-on condition of the switch tube Q3 can be achieved in the input and output stage T2, the time of the input stage T1 is short, the time of the input and output stage T2 is long, and when the input voltage Vin is less than the output voltage Vo, under the condition that the zero-voltage switching-on condition of the switch tube Q2 in the output stage T3 can be achieved, the time of the input stage T1 is short, and the time of the input and output stage T2 is long, so that the peak value of the inductor current is reduced, and the output efficiency is improved.
The position relationship between the divider resistor and the switch group includes, but is not limited to, the following two ways:
1. all voltage dividing resistors and the first and second switch groups are integrated in the control IC, and the voltage dividing resistors are selected in the IC by detecting the magnitude of the input voltage Vin.
2. The divider resistor, the first switch group and the second switch group are respectively independent of the outside of the IC, an analog device is independently set up, and the divider resistor is selected on an analog circuit independent of the outside of the IC by detecting the magnitude of the input voltage Vin.
Example two
Referring to fig. 11(a), fig. 11(a) is a schematic diagram of AN input stage control circuit in embodiment 2 of the present invention, in this embodiment, the input stage control circuit is the same as the input stage control circuit in the first embodiment, each voltage segment corresponds to one switch in a first switch group, the first switch group is composed of N switches, the N switches are a1, a2, AN, and AN, which are not described in detail herein, and the difference between this embodiment and the first embodiment is that: the input/output stage control circuit in this embodiment is different from the first embodiment.
Referring to fig. 11(b), fig. 11(b) is a schematic diagram of an input/output stage control circuit according to a second embodiment of the present invention, in which the input/output stage control circuit operates on the principle of performing a piecewise coefficient configuration on the input voltage Vin and performing a piecewise coefficient configuration on the output voltage Vo.
The input voltage Vin section coefficient configuration is to section an input voltage Vin, the input voltage Vin can be divided into N sections, N can be any natural number, and the input voltage Vin can be divided into Vin1-Vin2, Vin2-Vin3, Vin (N-1) -VinN.
Each input voltage segment corresponds to one switch in a second switch group consisting of N switches B1, B2.
When the input voltage Vin is within the voltage range of Vin1-Vin2, the switch B1 is turned on, and the switch B1 is communicated with a group of voltage dividing resistors R3_1 and R4_1 of the input voltage Vin.
Similarly, when the input voltage Vin is within the voltage range of Vin (N-1) -Vin2(N), the switch BN is turned on, and the switch BN is connected to a group of voltage dividing resistors R3_ N, R4_ N of the input voltage Vin.
The output voltage Vo is segmented according to the segmentation coefficient configuration, the input voltage Vo can be divided into N segments, N can be any natural number, and the input voltage Vo can be divided into Vo0-Vo1, Vo1-Vo2, Vo (N-1) -VoN.
Each output voltage segment corresponds to one switch in a third switch group, which consists of N switches, which are C1, C2.
When the output voltage Vo is in the voltage range of Vo0-Vo1, the switch C1 is turned on, and the switch C1 is connected with a group of voltage dividing resistors R5_1 and R6_1 of the output voltage Vo.
Similarly, when the output voltage Vo is within the voltage range of Vo (N-1) -VoN, the switch CN is turned on, and the switch CN is connected with a group of voltage dividing resistors R5_ N, R6_ N of the output voltage Vo.
The relationship of the input voltage segments, the output voltage segments and the conducting switches is shown in table 2 below.
TABLE 2
Figure BDA0003177716010000101
Referring to fig. 11(b), the operating principle of the input/output stage control circuit in the second embodiment is as follows: the input voltage Vin is connected to the positive input end of a differential circuit U5 after being divided by a voltage dividing resistor of a matching voltage section, the output voltage Vo is connected to the negative input end of a differential circuit U5 after being divided by the voltage dividing resistor of the matching voltage section, the output voltage of the differential circuit U5 is connected to the input end of a voltage-controlled constant current source U4, the output current of the voltage-controlled constant current source U4 charges a charging capacitor C2, and the voltage U at the two ends of the charging capacitor C2C2The positive input end of a comparator U2 is connected, the negative input end of a comparator U2 is connected with an output signal Verr of an error amplifier, and the total time of an input stage T1 and an input-output stage T2 is equal to the voltage U at the two ends of a charging capacitor C2C2The time it takes to charge from 0V to the same voltage as the output signal Verr.
Compared with the first embodiment, the second embodiment segments the output voltage Vo, and can further subdivide the input voltage and the output voltage in a wide voltage application occasion, that is, a group of coefficients are adopted in a smaller voltage range segment, so that the peak current of the full working condition can be further reduced.
EXAMPLE III
Referring to fig. 12(a), fig. 12(a) is a schematic diagram of an input stage control circuit according to a third embodiment of the present invention. In this embodiment, the working principle of the input stage control circuit is to divide the input voltage Vin, one of the voltage dividing resistors is a fixed resistor R1, and the other is a three-terminal controller Z1. The three-terminal controller can be an MOS tube or a triode which works in a linear region and is connected with a control voltage U input to the three-terminal controller Z1Z1Because the resistance of the three-terminal controller Z1 changes linearly, the input voltage of the voltage-controlled constant current source U3 is the input voltage Vin and UZ1The output current of the voltage-controlled constant current source U3 charges the charging capacitor C1, and the voltage U at the two ends of the charging capacitor C1C1The positive input end of the comparator U1 is connected, the negative input end of the comparator U1 is connected with the output signal Verr of the error amplifier, and the time of the input stage T1 is equal to the voltage U at the two ends of the charging capacitor C1C1The time it takes to charge from 0V to the same voltage as the output signal Verr.
Referring to fig. 12(b), fig. 12(b) is a schematic diagram of an input/output stage control circuit in embodiment 3 of the present invention. The working principle of the input and output stage control circuit is as follows: the input voltage Vin is divided, one of the voltage dividing resistors is a fixed resistor R3, and the other one is a three-terminal controller Z2. The three-terminal controller Z2 can be a MOS tube or a triode working in a linear region along with a control voltage U input to the three-terminal controller Z2Z2Since the resistance of the three-terminal controller Z2 changes linearly, the positive input terminal of the differential circuit U5 is provided with the voltage Vin and the control voltage UZ2A function of (a); the output voltage Vo is divided, and one of the voltage dividing resistors is a fixed resistor R5, and the other one is a three-terminal controller Z3. The three-terminal controller Z3 can be a MOS tube or a triode working in a linear region and the like, and controls the voltage U along with the control voltageZ3The resistance of the three-terminal controller Z3 is linearly changed, so that the output voltages Vo and U are provided at the negative input end of the differential circuit U5Z3As a function of (c). The output of the differential circuit U5 is connected with the input end of the voltage-controlled constant current source U4, the output current of the voltage-controlled constant current source U4 charges the charging capacitor C2, and the voltage U at the two ends of the charging capacitor C2C2The positive input end of a comparator U2 is connected, the negative input end of a comparator U2 is connected with an output signal Verr of an error amplifier, and the total time of an input stage T1 and an input-output stage T2 is equal to the voltage U at the two ends of a charging capacitor C2C2The time it takes to charge from 0V to the same voltage as the output signal Verr.
Compared with the first embodiment and the second embodiment, in the third embodiment, the multi-component voltage resistor is replaced by one group of divided voltage, the fixed resistor and the three-terminal controllers Z1, Z2 and Z3 are used for dividing the voltage, and the divided voltages of the input voltage Vin and the output voltage Vo are compensated by adjusting the input voltages of the three-terminal controllers Z1, Z2 and Z3, so that the peak current of the full-working-condition inductor is reduced, and the output efficiency is improved.
Example four
Fig. 13(a) is a schematic diagram of an input stage control circuit in embodiment 4 of the present invention. The input stage control circuit comprises a voltage-controlled constant current source U3, a voltage-dividing resistor R1, a voltage-dividing resistor R2, a charging capacitor C1 and a comparator U1.
Three differences from the embodimentThe method comprises the following steps: in this embodiment, the sampling voltage-dividing resistor R2 replaces the three-terminal controller Z1 in the third embodiment, and the input voltage of the voltage-controlled constant current source U3 is the divided voltage of the input voltage Vin through the voltage-dividing resistors R1 and R2; the conversion coefficient K of the voltage-controlled constant current source U1 is a function, in which the variables are not limited to the input voltage Vin, the output voltage Vo, and the output current Io, and the conversion coefficient function K of the voltage-controlled constant current source U1 is one of the following functions: k ═ f (V)in)、k＝f(Vin,Vo) Or k ═ f (V)in,Vo,Io) But not limited to the above three functional relationships.
Fig. 13(b) is a schematic diagram of an input/output stage control circuit in embodiment 4 of the present invention. The input and output stage control circuit comprises voltage resistors R3-R6, a differential circuit U5, a voltage-controlled constant current source U4 and a comparator U2.
The difference from the embodiment is that: in this embodiment, the sampling voltage-dividing resistor R4 replaces the three-terminal controller Z2, the sampling voltage-dividing resistor R6 replaces the three-terminal controller Z3, the voltage at the positive input end of the differential circuit U5 is the divided voltage of the input voltage Vin through the voltage-dividing resistors R3 and R4, and the voltage at the negative input end of the differential circuit U3 is the divided voltage of the output voltage Vo through the voltage-dividing resistors R5 and R6; the conversion coefficient K of the voltage-controlled constant current source U4 is a function, in which the variables are not limited to the input voltage Vin, the output voltage Vo, and the output current Io, and the conversion coefficient function K of the voltage-controlled constant current source U4 is one of the following functions: k ═ f (V)in)、k＝f(Vin,Vo) Or k ═ f (V)in,Vo,Io) But not limited to the above three functional relationships.
Compared with the third embodiment, the fourth embodiment converts the multi-section resistor voltage division into the voltage-controlled constant current source U4 with variable coefficients, and can also realize that the peak value of the inductive current is pressed to the lowest under different working conditions, thereby improving the efficiency.
EXAMPLE five
Fig. 14(a) is a schematic diagram of an input stage control circuit in embodiment 5 of the present invention. The input stage control circuit comprises a digital controller 1, a voltage-controlled constant current source U3, a charging capacitor C1 and a comparator U1, wherein the positive input end of the voltage-controlled constant current source U3 is connected with the digital controller 1, the negative input end of the voltage-controlled constant current source U3 is connected with the ground, and the output end of the voltage-controlled constant current source U3 is respectively connected with the positive input ends of the charging capacitor C1 and the comparator U1; the negative input of comparator U1 is connected to the error amplifier output signal Verr.
The working principle of the input stage control circuit is that the digital controller 1 is used for self-adaptive coefficient adjustment, and the digital controller 1 is not limited to a single chip microcomputer or a DSP.
The digital controller 1 samples the relevant signals of the buck-boost controller, the sampling signals are not limited to the input voltage Vin, the output voltage Vo and the output current Io, and a function U of the input voltage of the voltage-controlled constant current source U1 is generated in the digital controller 1M1A function U of the input voltage of the voltage-controlled constant current source U3M1Is one of the following: u shapeM1＝f(Vin)、UM1＝f(Vin,Vo) Or UM1＝f(Vin,Vo,Io) But not limited to the above three functional relationships.
Fig. 14(b) is a schematic diagram of an input/output stage control circuit in embodiment 5 of the present invention. The input and output stage control circuit comprises a digital controller 2, a voltage-controlled constant current source U4 and a comparator U2, wherein the positive input end of a voltage-controlled constant current source U4 is connected with the digital controller 2, the negative input end of the voltage-controlled constant current source U4 is connected with the ground, and the output end of the voltage-controlled constant current source U4 is respectively connected with the positive input ends of a charging capacitor C2 and a comparator U2; the negative input of comparator U4 is connected to the output signal Verr of the error amplifier.
The working principle of the input and output stage control circuit is that the digital controller 2 is used for self-adaptive coefficient adjustment, and the digital controller 2 is not limited to a single chip microcomputer or a DSP.
The digital controller 2 samples the relevant signals of the buck-boost controller, the sampling signals are not limited to the input voltage Vin, the output voltage Vo and the output current Io, and a function U of the input voltage of the voltage-controlled constant current source U4 is generated in the controller 2M2The function U of the input voltage of the voltage-controlled constant current source U4M2Is not limited to UM2＝f(Vin)、UM2＝f(Vin,Vo) Or UM2＝f(Vin,Vo,Io)。
Compared with the first to the fourth embodiments, in the fifth embodiment, the full working condition is further subdivided by sampling the input voltage Vin, the output voltage Vo and the output current Io through the digital controller, so that the time peak value of the inductive current can be minimum in any working condition, and the output efficiency is improved.
In other embodiments, the digital controller output voltages UM1 and UM2 under any operating condition calculated in the fifth embodiment can be made into a table in the digital controller (refer to fig. 15), and the table is looked up according to the buck-boost controller related signals sampled by the digital controller in real time.

Claims (8)

1. A control method of a buck-boost converter is used for controlling the buck-boost converter, wherein a main power circuit of the buck-boost converter comprises an input end used for receiving an input voltage, an output end used for generating an output voltage, a switch assembly and an inductor; the switch assembly is provided with a switch tube Q1, a switch tube Q2, a switch tube Q3 and a switch tube Q4; the main power circuit is divided into four stages in the working time sequence of one working cycle, wherein the four stages are an input stage, an input-output stage, an output stage and a clamping stage in sequence; in the input stage, the switching tube Q1 and the switching tube Q4 are switched on, and the switching tube Q2 and the switching tube Q3 are switched off; in the input and output stage, the switching tube Q1 and the switching tube Q3 are turned on, and the switching tube Q2 and the switching tube Q4 are turned off; in the output stage, the switching tube Q2 and the switching tube Q3 are switched on, and the switching tube Q1 and the switching tube Q4 are switched off; in the clamping stage, the switching tube Q2 and the switching tube Q4 are turned on, and the switching tube Q1 and the switching tube Q3 are turned off, and the control method includes:
when the input voltage is smaller than the output voltage, dynamically adjusting the time of the input phase and the time of the output phase according to the input voltage and the output voltage or according to the input voltage, the output voltage and the output current of the main power circuit, specifically: under the condition that zero-voltage turn-on conditions of the switching tube Q2 can be realized in the output stage, the current peak value of the inductor is reduced by reducing the time of the input stage and increasing the time of the input stage and the output stage;
when the input voltage is greater than or equal to the output voltage, dynamically adjusting the time of an input phase and the time of an output phase according to the input voltage and the output voltage or according to the input voltage, the output voltage and the output current of the main power circuit, specifically: under the condition that the zero-voltage switching-on condition of the switching tube Q3 in the input and output stage is met, the time of the input stage is reduced, and the time of the input and output stage is increased, so that the current peak value of the inductor is reduced.
2. The method as claimed in claim 1, wherein when the input voltage is less than the output voltage, the peak current value of the inductor is reduced by minimizing the time of the input phase and maximizing the time of the input-output phase under the condition that the zero-voltage-turn-on condition of the switching tube Q2 in the output phase is satisfied.
3. The control method of the buck-boost converter according to claim 1, wherein when the input voltage is equal to or greater than the output voltage, the peak current value of the inductor is reduced by minimizing the time of the input phase and maximizing the time of the input-output phase under the condition that the zero-voltage-turn-on condition of the switching tube Q3 in the input-output phase is satisfied.
4. The method as claimed in claim 1, wherein the control signals for the input stage and the input/output stage are generated by combining a plurality of voltage dividing resistors controlled by the input voltage and/or the output voltage in parallel.
5. The method of claim 1, wherein the input stage and the input-output stage are controlled by a plurality of sets of three-terminal controllers and fixed resistors controlled by the input voltage and the output voltage or by the input voltage, the output voltage and the output current of the main power circuit.
6. The control method of the buck-boost converter according to claim 1, wherein the control signals of the input stage and the input-output stage are generated by using a plurality of groups of conversion coefficients of the voltage-controlled constant current source controlled by the input voltage and/or the output voltage, wherein the conversion coefficients of the voltage-controlled constant current source are a function, and the variables in the function comprise the input voltage and/or the output voltage; or generating the control signals of the input stage and the input and output stage by adopting a mode of a plurality of groups of voltage-controlled constant current source conversion coefficients controlled by the input voltage, the output voltage and the output current of the main power circuit, wherein the conversion coefficient of the voltage-controlled constant current source is a function, and variables in the function comprise the input voltage, the output voltage and the output current of the main power circuit.
7. The method of claim 1, wherein the input stage and the input-output stage are generated by sampling the input voltage and the output voltage with a digital controller and generating a function of the input voltage and/or the output voltage with the digital controller.
8. The method of claim 1, wherein the first two or three parameters of the input voltage, the output voltage, and the output current are sampled by a digital controller, and the control signals for the input stage and the input-output stage are generated by a table look-up method.
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CN111092549A (en) * 2019-11-27 2020-05-01 南京航空航天大学 Three-mode frequency conversion soft switching control method of four-tube Buck-Boost converter
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