CN112953226B - High-gain converter capable of being used for photovoltaic charging and control method thereof - Google Patents
High-gain converter capable of being used for photovoltaic charging and control method thereof Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/34—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering
- H02J7/35—Parallel operation in networks using both storage and other dc sources, e.g. providing buffering with light sensitive cells
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E10/00—Energy generation through renewable energy sources
- Y02E10/50—Photovoltaic [PV] energy
- Y02E10/56—Power conversion systems, e.g. maximum power point trackers
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Abstract
The invention belongs to the technical field of DC-DC boost conversion, and particularly relates to a high-gain converter and a control method thereofinThe positive electrodes of the two electrodes are connected; the negative pole of the input power supply, the source electrode of the first switch tube, the source electrode of the second switch tube, the negative pole of the first capacitor, the cathode of the second diode and the input filter capacitor CinThe negative electrodes are connected; the drain electrode of the first switch tube is connected with the other end of the first inductor and the anode of the first diode; the drain electrode of the second switch tube is connected with the other end of the second inductor and the anode of the second capacitor; the cathode of the first diode is connected with the anode of the first capacitor and one end of the output filter inductor; the cathode of the second capacitor is connected with the anode of the second diode, the cathode of the output filter capacitor and one end of the direct current load; the other end of the output filter inductor is connected with the anode of the output filter capacitor and the other end of the direct current load. The invention has the advantages of continuous input and output current, high voltage gain and the like.
Description
Technical Field
The invention belongs to a DC-DC boost conversion technology, and particularly relates to a high-gain converter for photovoltaic charging and a control method thereof.
Background
The roof distributed photovoltaic power generation system is utilized to slowly charge the electric automobile, so that the electric energy requirements of the electric automobile on duty and off duty in the urban area can be basically met, and zero-emission green traffic can be really realized. Since the terminal voltage of the photovoltaic cell is usually much lower than that of the power cell of the electric vehicle, a high-gain direct-current converter is required to be adopted as a main circuit topology for the photovoltaic slow charging system. In addition, the terminal voltage ripple of the photovoltaic cell affects the accuracy of MPPT control, so that MPPT efficiency is seriously reduced, and therefore, the output side of the MPPT is usually connected in parallel with a capacitor to filter the input current ripple of the photovoltaic charging converter and smooth the terminal voltage of the photovoltaic cell. Because the service environment of the photovoltaic charging facility is very severe (high temperature and insolation), the expected service life of the electrolytic capacitor is shortened sharply on the occasion, so that the input current of the photovoltaic charging converter must be continuous, the capacitance of the input end is greatly reduced, no electrolytic capacitor is realized, and the reliability of the system is improved. In addition, the internal resistance of the battery is generally less than the equivalent series resistance of the capacitor. If the output current of the photovoltaic charging converter has large pulsation, a large number of capacitors need to be connected in parallel at the output end of the photovoltaic charging converter, so that the charging current ripple is reduced, the heat productivity of the storage battery is reduced, and the service life of the storage battery is prolonged. However, the system cost and volume also increase significantly. For this reason, the output current of the photovoltaic charge converter must also be continuous.
The voltage gain of the switched capacitor Boost converter is (1+ D) times of that of the traditional Boost converter, and the input current and the output current are continuous, so that the performance requirement of the photovoltaic charging converter is met. However, this structure has the following problems: (1) under the condition of low input voltage, the current stress of the input inductor is large, and the current continuity can be ensured only by large inductance; (2) the input current has large pulse rate, large inductive current and serious loss. Fig. 1 shows a switched capacitor Boost converter with dual input inductors. The pulse rate of input current can be effectively reduced, and the average current stress of the switching tube is reduced, but the defects of more devices, complex structure, insufficient boosting capacity, high voltage stress and the like exist.
Disclosure of Invention
In view of the above, the present invention provides a high gain converter for photovoltaic charging and a control method thereof. The high-gain converter provided by the invention is based on the double-inductance switch capacitor Boost converter shown in figure 1, and two Boost diodes (D) are removed3、D4) (ii) a First switch tube S1And a second switching tube S2The initial phases of the driving signals are still 180 degrees different from each other, but the first switch tube S1Duty ratio d of1And a second switching tube S2Duty ratio d of2And satisfying the constraint relation:
and with d1Are control variables. High gain provided by the inventionThe converter has the following advantages: (1) the input and output currents are continuous, so that the input filter capacitor C can be greatly reducedinAnd an output filter capacitor CoThe size, the volume and the cost of the solar cell are particularly suitable for photovoltaic charging occasions; (2) first inductance L1And a second inductance L2Is equal to the mean current stress of, and L1≈L2And thus the first inductance L1And a second inductance L2The iron consumption and the copper consumption are basically the same, the heat distribution is uniform, the method is suitable for modularized batch manufacturing, and the production cost is reduced; (3) the input current has a pulse frequency twice the switching frequency and a reduced pulse rate, thereby further reducing the input filter capacitance CinThe size of the system improves the reliability and reduces the volume and the cost of the system; (4) first switch tube S1And a second switching tube S2The current stress and the voltage stress are smaller, so that the power loss is reduced, and the conversion efficiency is improved. In addition, compared with the original double-inductance switch capacitor Boost converter, the high-gain converter provided by the invention has fewer diodes, higher voltage gain and lower voltage stress, so that the structure is simpler, and the power loss and the cost are lower.
In order to achieve the purpose, the technical scheme provided by the invention is as follows:
in a first aspect, the present invention provides a high gain converter comprising an input power source UinAn input filter capacitor CinA first inductor L1A second inductor L2A first switch tube S1A second switch tube S2A first diode D1A second diode D2A first capacitor C1A second capacitor C2An output filter inductor LoAn output filter capacitor CoA direct current load R;
the input power supply UinAnd the first inductor L1One terminal of the second inductor L2One terminal of, the input filter capacitance CinThe positive electrodes of the two electrodes are connected;
the input power supply UinAnd the first switch tube S1Source electrode of, the second switchPipe S2Source electrode of, the first capacitor C1Negative pole of the second diode D2Cathode of (2), said input filter capacitor CinThe negative electrodes are connected;
the first switch tube S1And the first inductor L1Another terminal of the first diode D1The anodes of the anode groups are connected;
the second switch tube S2And the second inductor L2The other end of the first capacitor C2The positive electrodes of the two electrodes are connected;
the first diode D1And the first capacitor C1The positive pole of the filter is connected with the output filter inductor LoOne end of (a);
the second capacitor C2And the cathode of the second diode D2Anode of, the output filter capacitor CoThe negative electrode of the direct current load R is connected with one end of the direct current load R;
the output filter inductor LoAnd the other end of the output filter capacitor CoThe other end of the direct current load R is connected with the positive electrode of the capacitor.
Further, the control method of the high gain converter comprises:
first of all for the output voltage u of the high gain converteroSampling to obtain a sampling value uof；
Sampling value uofAnd the output voltage reference value uo,refComparing, processing the error signal by output voltage controller to obtain a modulated signal ur1；
Will modulate signal ur1And amplitude of UcmUnipolar triangular carrier uc1Crossing to generate a first switch tube S1PWM drive signal ug1Said PWM drive signal ug1Duty ratio of d1＝ur1/Ucm；
Will modulate signal ur1Sending to a calculation module by formula
And d2＝ur2/UcmI.e. ur2＝Ucm 2/(2Ucm-ur1) Obtaining a modulation signal u by real-time calculationr2(ii) a Will modulate signal ur2And amplitude of UcmUnipolar triangular carrier uc2Crossing to generate a second switch tube S2PWM drive signal ug2The duty ratio of the driving signal is d2. Unipolar triangular carrier uc1And uc2Are equal in amplitude and same in frequency, and are 180 ° out of phase with each other.
Further, the ideal voltage gain of the high-gain converter is as follows:
in the formula (d)1Is a first switch tube S1Duty ratio of PWM drive signal of d2Is a second switch tube S2Duty ratio of PWM drive signal of UinIs an average value of the input voltage, UoIs the average value of the output voltage.
Compared with the prior art, the invention provides the high-gain converter for photovoltaic charging and the control method thereof, wherein the high-gain converter has fewer power tubes (two switching tubes and two diodes), and the first switching tube S1And a second switching tube S2The initial phase of the driving signal is 180 degrees different from each other, and the first switch tube S1Duty ratio d of1And a second switching tube S2Duty ratio d of2And satisfying the constraint relation:
thus, the first inductance L1And a second inductance L2The input current is shared and the first inductance L is greatly reduced1A second inductor L2A first switch tube S1A second switch tube S2The current stress and the on-state loss greatly improve the conversion efficiency; the input current has a ripple frequency twice the switching frequency and the ripple rate is reduced, thereby reducing input filteringWave capacitor CinThe size of the system improves reliability and reduces the volume and cost of the system. In addition, the converter provided by the invention has the characteristics of continuous input and output currents, high voltage gain, low voltage stress, simple structure, low cost and the like, thereby being particularly suitable for photovoltaic charging occasions.
Drawings
Fig. 1 is a schematic circuit diagram of a switching capacitor Boost converter with a dual input inductor;
fig. 2 is a schematic circuit diagram of a high-gain converter that can be used for photovoltaic charging according to an embodiment of the present disclosure;
FIG. 3 is a block diagram of the logic structure of the control method of the high gain converter for photovoltaic charging shown in FIG. 2;
fig. 4(a) to (d) show the high-gain converter for photovoltaic charging shown in fig. 2 in a switching cycle (first switch transistor S)1Duty ratio d of the driving signal1Not less than 0.5 and a first switch tube S1Duty ratio d of the driving signal1<0.5 two cases) 4 working mode equivalent diagrams;
FIGS. 5(a) and (b) are waveforms illustrating the main operation of the high-gain converter for photovoltaic charging shown in FIG. 2 during a switching cycle;
fig. 6(a) to (f) are simulated waveforms of the high-gain converter shown in fig. 2, which can be used for photovoltaic charging.
Detailed Description
The technical solutions in the embodiments of the present application will be described clearly and completely with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Fig. 2 shows a schematic circuit diagram of a high-gain converter that can be used for photovoltaic charging according to an embodiment of the present application. As an exemplary and non-limiting embodiment, the converter includes an input power source UinInput filter capacitorCinA first inductor L1A second inductor L2A first switch tube S1A second switch tube S2A first diode D1A second diode D2A first capacitor C1A second capacitor C2An output filter inductor LoAn output filter capacitor CoA direct current load R; input power supply UinPositive pole and first inductance L1One terminal of (1), a second inductance L2One terminal of (1), input filter capacitor CinThe positive electrodes of the two electrodes are connected; input power supply UinNegative pole of (2) and first switch tube S1Source electrode of the first switching tube S2Source electrode, first capacitor C1Negative electrode of (1), second diode D2Cathode and input filter capacitor CinThe negative electrodes are connected; first switch tube S1Drain electrode of and first inductor L1Another terminal of (1), a first diode D1The anodes of the anode groups are connected; a second switch tube S2Drain electrode of and second inductor L2Another terminal of (1), a second capacitor C2The positive electrodes of the two electrodes are connected; first diode D1Cathode and first capacitor C1The positive pole of the filter is connected with the output filter inductor LoThe connection point is marked as a; second capacitor C2Cathode of and a second diode D2Anode and output filter capacitor CoThe negative pole of (1) is connected with one end of a direct current load R, and the connection point is marked as b;
output filter inductance LoAnother end of (1) and an output filter capacitor CoThe anode of the direct current load R is connected with the other end of the direct current load R; output filter inductance LoAnd output filter capacitor CoAre connected in series to form a filter circuit.
The control method of the high gain converter according to the present application will be described below with reference to the main circuit shown in fig. 2. Fig. 3 is a logic structure block diagram of a control method according to an embodiment of the present application. For high gain converter output voltage uoSampling to obtain a sampling value uof(ii) a Sampling value uofAnd the output voltage reference value uo,refComparing, sending the error signal to output voltage controller to obtain a modulation signal ur1(ii) a Will modulate signal ur1Banner withValue of UcmUnipolar triangular carrier uc1Crossing to generate a first switch tube S1PWM drive signal ug1The duty ratio of the driving signal is d1＝ur1/Ucm. To make the first inductance L1And a second inductance L2Are strictly equal, modulating signal ur1Sending to a calculation module by formula
And d2＝ur2/UcmI.e. ur2＝Ucm 2/(2Ucm-ur1) Obtaining a modulation signal u by real-time calculationr2(ii) a Will modulate signal ur2With a unipolar triangular carrier uc2Crossing to generate a second switch tube S2PWM drive signal ug2The duty ratio of the driving signal is d2. Unipolar triangular carrier uc1And uc2Are equal in amplitude and same in frequency, and are 180 ° out of phase with each other.
The operation of the high gain converter shown in fig. 2 is explained below.
After the system works into a steady state, the system can be divided into 4 modes in one switching period; neglecting other parasitic parameters of the switch tube except considering the parasitic capacitance of the switch tube; the energy storage element and the diode are ideal devices, and the first capacitor C1A second capacitor C2An input filter capacitor CinAn output filter capacitor CoLarge enough that voltage ripple is negligible; first inductance L1A second inductor L2The current of (2) is continuous; input power supply UinThe negative terminal is a zero potential reference point, and the direct current load R is pure resistance. Equivalent circuits of the modes are shown in fig. 4(a) to 4 (d); the main waveforms in one switching cycle are schematically shown in fig. 5(a) and (b).
The following are distinguished:
first switch tube S1Duty ratio d of the driving signal1≥0.5：
Mode 1: [ t ] of0-t1](the equivalent circuit is shown in FIG. 4 (a))
t0At the moment, the first switch tube S is switched on1And a second switching tube S2. First inductance L1A second inductor L2Bears a forward voltage drop and passes through the first switch tube S1And a second switching tube S2And charging is carried out. First diode D1A second diode D2And (6) turning off. A first capacitor C1A second capacitor C2Through a second switch tube S2In series, discharge to the load and filter the inductance L to the outputoAnd (6) charging. At this time, there are:
in the formula of UC1Is a first capacitor C1Voltage stress of UC2Is a second capacitor C2Voltage stress of (d).
To t1At that time, modality 1 ends. The duration of modality 1 is:
Δt1＝(d2-0.5)Ts (4)
in the formula, TsIs a switching cycle.
Mode 2: [ t ] of1-t2](the equivalent circuit is shown in FIG. 4 (b))
t1At the moment, the second switch tube S is turned off2Second inductance L2Bear reverse voltage drop, and for the second capacitor C2And charging is carried out. First inductance L1Bears a forward voltage drop and passes through the first switch tube S1And charging is carried out. Second diode D2Conducting the first diode D1And (6) turning off. A first capacitor C1And an output filter inductor LoAnd supplying power to the load. At this time, there are:
to t2Time, modality 2 ends, and the duration of modality 2 is:
Δt2＝(1-d2)Ts (8)
modality 3: [ t ] of2-t3](the equivalent circuit is shown in FIG. 4 (a))
t2At the moment, the second switch tube S is switched on2. First inductance L1A second inductor L2Bears a forward voltage drop and passes through the first switch tube S1And a second switching tube S2And charging is carried out. First diode D1A second diode D2And (6) turning off. A first capacitor C1A second capacitor C2Through a second switch tube S2In series, discharge to the load and output filter inductance LoAnd (6) charging. At this time, there are:
to t3At that time, modality 3 ends. The duration of modality 3 is:
Δt3＝(d1-0.5)Ts (12)
modality 4: [ t ] of3-t4](the equivalent circuit is shown in FIG. 4 (c))
t3At any moment, the first switch tube S is turned off1. Second inductance L2Bears a forward voltage drop and passes through a second switch tube S2Charging is carried out, the first inductor L1Subject to reverse voltage drop, to the load side and to the first capacitor C1And (5) supplying power. First diode D1On, the second diode D2And (6) turning off. Second capacitor C2Through a second switch tube S2Discharging to the load and outputting the filter inductance LoAnd (6) charging. At this time, there are:
to t4At that time, modality 4 ends. The duration of modality 4 is:
Δt4＝(1-d1)Ts (16)
② the first switch tube S1Duty ratio d of the driving signal1<At 0.5 time:
mode 1: [ t ] of0-t1](the equivalent circuit is shown in FIG. 4 (a))
t0At the moment, the first switch tube S is switched on1And a second switching tube S2. First inductance L1A second inductor L2Bears a forward voltage drop and passes through the first switch tube S1And a second switching tube S2And charging is carried out. First diode D1A second diode D2And (6) turning off. A first capacitor C1A second capacitor C2Through a second switch tube S2In series, discharge to the load and output filter inductance LoAnd (6) charging. At this time, there are:
to t1At that time, modality 1 ends. The duration of modality 1 is:
Δt1＝(d2-0.5)Ts (20)
mode 2: [ t ] of1-t2](the equivalent circuit is shown in FIG. 4 (b))
t1At the moment, the second switch tube S is turned off2Second inductance L2Subject to reverse voltage drop and applied to the second capacitor C2And charging is carried out. First inductance L1Bears a forward voltage drop and passes through the first switch tube S1And charging is carried out. Second diode D2Conducting the first diode D1And (6) turning off. A first capacitor C1And an output filter inductor LoAnd supplying power to the load. At this time, there are:
to t2Time, modality 2 ends, and the duration of modality 2 is:
Δt2＝(d1-d2+0.5)Ts (24)
modality 3: [ t ] of2-t3](the equivalent circuit is shown in FIG. 4 (d))
t2At any moment, the first switch tube S is turned off1First inductance L1Subject to reverse voltage drop, to the load side and to the first capacitor C1Power supply, second inductance L2Subject to reverse voltage drop and applied to the second capacitor C2And charging is carried out. First diode D1And a second diode D2And (4) opening. First inductance L1And an output filter inductor LoAnd supplying power to the load. At this time, there are:
to t3At the moment, modality 3 ends, and the duration of modality 3 is:
Δt3＝(0.5-d1)Ts (28)
modality 4: [ t ] of3-t4](the equivalent circuit is shown in FIG. 4 (c))
t3At the moment, the second switch tube S is switched on2. Second inductance L2Bears a forward voltage drop and passes through a second switch tube S2Charging is carried out, the first inductor L1Subject to a reverse pressure drop,to the load side and the first capacitor C1And (5) supplying power. First diode D1On, the second diode D2And (6) turning off. Second capacitor C2Through a second switch tube S2Discharging to the load and outputting the filter inductance LoAnd (6) charging. At this time, there are:
to t4At that time, modality 4 ends. The duration of modality 4 is:
Δt4＝0.5Ts (32)
based on the above analysis of the operation of the high gain converter of the present invention, the voltage gain thereof is analyzed below.
According to the first inductance L1A second inductor L2An output filter inductor LoThe voltage-second balance of (a) can be obtained:
Uind1Ts＝(UC1-Uin)(1-d1)Ts (33)
Uind2Ts＝(UC2-Uin)(1-d2)Ts (34)
(UC1+UC2-Uo)d2Ts＝(Uo-UC1)(1-d2)Ts(35) from equations (33) - (35), the voltage gain of the converter can be found as:
in the formula IinIs the average current of the input current, IoIs the average current of the output currents.
Further, according to the formulas (36) and (46), the following can be obtained:
a first capacitor C1Voltage stress U ofC1And a second capacitor C2Voltage stress U ofC2Comprises the following steps:
first switch tube S1Voltage stress U ofS1And a first diode D1Voltage stress U ofD1Comprises the following steps:
a second switch tube S2Voltage stress U ofS2And a second diode D2Voltage stress U ofD2Comprises the following steps:
according to the average current equivalent circuit of the converter, the following can be obtained:
ILo＝Io (44)
ILo＝(1-d1)IL1 (45)
in the formula IL1Is the average current of the first inductor, IL2Is the average current of the second inductor, ILoTo output the average current of the filter inductor.
According to formulae (43) to (45), it is possible to obtain:
ID1＝ID2＝Io (49)
in the formula IS1Is the average current of the first switch tube, IS2Is the average current of the second switch tube, ID1Is the average current of the first diode, ID2Is the average current of the second diode.
In order to verify the correctness of the theoretical analysis, saber simulation software is used for performing simulation verification on the improved gain Boost converter. Firstly, for the first switch tube S1Duty ratio d of the driving signal1The verification is carried out at least 0.5, and the design indexes are as follows: input voltage Uin48V, output voltage Uo380V, the maximum output power is 300W, and the switching frequency is fs100 kHz. In addition, a first capacitor C1And a firstTwo capacitors C2Are all 10 mu F, input filter capacitor CinAnd an output filter capacitor CoAre all 1 muF, the first inductance L10.58mH, second inductance L20.62mH, output filter inductance Lo＝2.5mH。
Waveforms of the simulation experiment are shown in FIGS. 6(a) -6 (c).
The input voltage u is given in fig. 6(a)inAnd an output voltage uoThe waveform of (2). It can be seen that the duty cycle d1＝0.75、d20.8, and the gain value of the measured voltage is G-Uo/Uin7.94, with theoretical value G2/(1-d)1) The 8 is basically matched, and higher gain is realized. The first inductor current i is given in fig. 6(b)L1And a second inductor current iL2Input current iinSwitch tube S1And S2Current i ofS1、iS2And a first switch tube S1Drive signal u ofg1A second switch tube S2Drive signal u ofg2The simulated waveform of (2). It can be seen that iL1And iL2Are all continuous, the wave forms are mutually different by 180 degrees, so that the input current iinBecomes twice the switching frequency; the pulse rate of the input current is 7.62 percent and is far lower than the first inductive current iL1And a second inductor current iL2The pulse rate of (a); first inductance L1A second inductor L2Is equal toL1＝IL23.15A; first switch tube S1Has an average current of 2.37A, and a second switching tube S2The average current of (2) was 3.16A. The drain-source voltage u of the switch tube is given in FIG. 6(c)S1And uS2Diode terminal voltage uD1And uD2Terminal voltage u of capacitorC1、uC2And uCoThe simulated waveform of (2). It can be seen that the first switching tube S1And a first diode D1Is approximately equal to 1/2 times that of the conventional dual-input inductor-switched capacitor converter shown in fig. 1, and a second switching tube S2And a second diode D2Is substantially equal to the voltage stress of (2-d) of the conventional dual input inductor-switched capacitor converter shown in fig. 11) And 2 times of the total weight.
To the first switch tube S1Duty ratio d of the driving signal1<0.5, the design indexes are as follows: input voltage Uin114V, output voltage Uo380V, the maximum output power is 300W, and the switching frequency is fs100 kHz. In addition, a first capacitor C1And a second capacitor C2Are all 40 mu F, and are input with a filter capacitor CinAnd an output filter capacitor CoAre all 1 muF, the first inductance L1Is 1.73mH, and a second inductance L2Is 2.71mH, and outputs a filter inductor Lo＝4.5mH。
Waveforms of the simulation experiment are shown in FIGS. 6(d) -6 (f).
The input voltage u is given in FIG. 6(d)inAnd an output voltage uoThe waveform of (2). It can be seen that the duty cycle d1＝0.4、d20.625, and the measured voltage gain value is G-Uo/Uin3.32, with theoretical value G2/(1-d)1) 3.33, the basic agreement. The first inductor current i is given in fig. 6(e)L1And a second inductor current iL2Input current iinA first switch tube S1Current i ofS1And a second switching tube S2Current i ofS2And a first switch tube S1Drive signal u ofg1A second switch tube S2Drive signal u ofg2The simulated waveform of (2). It can be seen that iL1And iL2Are all continuous, the wave forms are mutually different by 180 degrees, so that the input current iinBecomes twice the switching frequency; the pulse rate of the input current is 4.17 percent and is far lower than the first inductive current iL1And a second inductor current iL2The pulse rate of (a); first inductance L1A second inductor L2Is equal toL1＝IL21.32A; first switch tube S1Has an average current of 0.53A, and a second switching tube S2The average current of (2) was 1.33A. The drain-source voltage u of the switch tube is given in FIG. 6(f)S1And uS2Diode terminal voltage uD1And uD2Terminal voltage u of capacitorC1、uC2And uCoThe simulated waveform of (2). It can be seen that the first switching tube S1And a first diode D1Is approximately equal to 1/2 times that of the conventional dual-input inductor-switched capacitor converter shown in fig. 1, and a second switching tube S2And a second diode D2Is substantially equal to the voltage stress of (2-d) of the conventional dual input inductor-switched capacitor converter shown in fig. 11) And 2 times, thereby verifying the correctness of theoretical analysis.
It is noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The above description of the embodiments is only intended to facilitate the understanding of the method of the invention and its core idea, and not to limit it. It should be noted that, for those skilled in the art, without departing from the principle of the present invention, several improvements and modifications can be made to the present invention, and these improvements and modifications also fall into the protection scope of the present invention.
Claims (3)
1. A high-gain converter is characterized in that the high-gain converter is a high-gain converter capable of being used for photovoltaic charging, and comprises an input power supply UinAn input filter capacitor CinA first inductor L1A second inductor L2A first switch tube S1A second switch tube S2A first diode D1A second diode D2A first capacitor C1A second capacitor C2An output filter inductor LoAn output filter capacitor CoA direct current load R;
the input power supply UinAnd the first inductor L1One terminal of the second inductor L2One terminal of, the input filter capacitance CinThe positive electrodes of the two electrodes are connected;
the input power supply UinAnd the first switch tube S1Source electrode of, the second switching tube S2Source electrode of, the first capacitor C1Negative pole of the second diode D2Cathode of (2), said input filter capacitor CinThe negative electrodes are connected;
the first switch tube S1And the first inductor L1Another terminal of the first diode D1The anodes of the anode groups are connected;
the second switch tube S2And the second inductor L2The other end of the first capacitor C2The positive electrodes of the two electrodes are connected;
the first diode D1And the first capacitor C1The positive pole of the filter is connected with the output filter inductor LoOne end of (a);
the second capacitor C2And the cathode of the second diode D2Anode of, the output filter capacitor CoThe negative electrode of the direct current load R is connected with one end of the direct current load R;
the output filter inductor LoAnd the other end of the output filter capacitor CoThe other end of the direct current load R is connected with the positive electrode of the capacitor.
2. The method of claim 1, comprising the steps of:
first of all for the output voltage u of the high gain converteroSampling to obtain a sampling value uof；
Sampling value uofAnd the output voltage reference valueuo,refComparing, processing the error signal by output voltage controller to obtain a modulated signal ur1；
Will modulate signal ur1And amplitude of UcmUnipolar triangular carrier uc1Crossing to generate a first switch tube S1PWM drive signal ug1Said PWM drive signal ug1Duty ratio of d1，d1＝ur1/Ucm；
According to the formula ur2＝Ucm 2/(2Ucm-ur1) Obtaining a modulation signal u by real-time calculationr2；
Will modulate signal ur2And amplitude of UcmUnipolar triangular carrier uc2Crossing to generate a second switch tube S2PWM drive signal ug2Said PWM drive signal ug2Duty ratio of d2；
Unipolar triangular carrier uc1And a unipolar triangular carrier uc2Are identical in frequency and are 180 deg. out of phase with each other.
3. The control method of claim 2, wherein the ideal voltage gain G of the high-gain converter is:
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| CN102510218A (en) * | 2011-11-04 | 2012-06-20 | 安徽工业大学 | Direct current to direct current (DC-DC) power converter with high boost ratio |
| CN106936309A (en) * | 2017-03-29 | 2017-07-07 | 天津大学 | For the input-series and output-parallel gain voltage boosting dc converter wide of fuel cell |
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| CN102510218A (en) * | 2011-11-04 | 2012-06-20 | 安徽工业大学 | Direct current to direct current (DC-DC) power converter with high boost ratio |
| CN106936309A (en) * | 2017-03-29 | 2017-07-07 | 天津大学 | For the input-series and output-parallel gain voltage boosting dc converter wide of fuel cell |
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