CN114583954A - High-gain converter for photovoltaic direct current module and control method thereof - Google Patents

High-gain converter for photovoltaic direct current module and control method thereof Download PDF

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CN114583954A
CN114583954A CN202210272294.8A CN202210272294A CN114583954A CN 114583954 A CN114583954 A CN 114583954A CN 202210272294 A CN202210272294 A CN 202210272294A CN 114583954 A CN114583954 A CN 114583954A
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diode
capacitor
switch tube
inductor
voltage
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秦岭
许兴
张雷
王亚芳
杨毓
钱娇
孙诗雨
刘宇涵
周磊
段冰莹
钱天泓
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Nantong University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/50—Photovoltaic [PV] energy
    • Y02E10/56—Power conversion systems, e.g. maximum power point trackers

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  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention belongs to the technical field of converters, and discloses a high-gain converter for a photovoltaic direct current module and a control method thereof, wherein the anode of an input filter capacitor of the converter is connected with one end of a first inductor and one end of a second inductor; the other end of the first inductor is connected with the drain electrode of the first switching tube and the anode of the first capacitor; the other end of the second inductor is connected with the drain electrode of the second switching tube, the anode of the second diode and the cathode of the second capacitor; the source electrode of the second switch tube is connected with the cathode of the first capacitor and the anode of the first diode; the cathode of the second diode is connected with one end of the third inductor and the anode of the third capacitor; the other end of the third inductor is connected with the anode of the third diode and the anode of the second capacitor; the cathode of the third diode D3 is connected to the anode of the output filter capacitor. The high-gain converter has the advantages of strong boosting capacity, few power tubes, small input current ripple and the like.

Description

High-gain converter for photovoltaic direct current module and control method thereof
Technical Field
The invention belongs to the technical field of converters, and particularly relates to a high-gain converter for a photovoltaic direct-current module and a control method thereof.
Background
The inverter is a key component of a photovoltaic grid-connected power generation system and mainly comprises a centralized type, a string type, an alternating current module (namely a micro inverter), a parallel direct current module (namely a power optimizer) and the like. The first two types of inverters have higher conversion efficiency, but a large number of photovoltaic modules are required to be connected in series and in parallel for use, so that a global maximum power point is difficult to find due to the fact that a P-V characteristic curve of a photovoltaic array has a multi-peak phenomenon under the condition of local shadow shielding, and the power generation potential of each module cannot be fully exerted. The micro inverter can realize the tracking control of the maximum power point of a component level, has the advantages of flexible installation, easy expansion, high redundancy and the like, but has low overall efficiency and higher cost. Compared with the prior art, the two-stage photovoltaic grid-connected inverter with the parallel direct-current modules has the advantages of the first three inverters, and is simple in structure and relatively low in cost. However, since the voltage of the input power (single photovoltaic module) is low, the dc module must have a high voltage gain (G ═ U)o/Uin) And the direct-current bus voltage requirement of the rear-stage grid-connected inverter can be met. At present, a leakage current suppression strategy of a non-isolated grid-connected inverter is mature day by day, and the electrical safety problem is perfectly solved. Compared with an isolated converter, the non-isolated converter has the advantages of small size, low cost and low loss. Therefore, a non-isolated boost conversion is usedThe device is more advantageous as a dc module.
The Boost converter is the most widely used non-isolated Boost converter. The input current is continuous, the structure is simple, but the actual voltage gain is influenced by the parasitic parameters of the circuit and has a maximum value, generally lower than 5, and the system efficiency is seriously reduced. For this reason, various non-isolated high-gain Boost converters have been reported in recent years. Boost converters based on coupled inductors can obtain higher voltage gain by changing the winding turn ratio of the coupled inductors, but the conversion efficiency is generally lower because leakage inductance energy is difficult to effectively recover. The multi-module extended switch inductor Boost converter changes the connection mode of the inductor by controlling the turn-off and the turn-on of the switch tube, thereby obtaining higher voltage gain; however, the power device has the disadvantages of more power devices, high voltage stress of the power devices, low efficiency and the like. In addition, the input current has large pulsation, and the input side needs to be connected with a large-capacity filter capacitor in parallel, so that the system is large in size and cost and low in reliability.
Disclosure of Invention
In view of the above, the present invention is directed to a high-gain converter for a photovoltaic dc module, which has an extremely strong boosting capability, fewer power transistors, and a lower voltage stress of the power transistors; meanwhile, the two input inductors share the input current together, the inductor size and on-state loss are small, the input current is continuous, the ripple wave is small, the input filter capacitance, the size and the cost can be reduced, the reliability is improved, and the photovoltaic direct-current module is suitable for photovoltaic direct-current modules.
In order to achieve the purpose, the technical scheme provided by the invention is as follows:
a high gain converter for photovoltaic direct current module includes input filter capacitor CinA first capacitor C1A second capacitor C2A third capacitor C3Output filter capacitor CoA first inductor L1A second inductor L2A third inductor L3A first switch tube S1A second switch tube S2A first diode D1A second diode D2A third diode D3；
The input filter capacitor CinAnd the first inductor L1One terminal of the second inductor L2Is connected with one end of the connecting rod;
the first inductor L1And the other end of the first switch tube S1The drain electrode of (1), the first capacitor C1The positive electrode of (1) is connected;
the second inductor L2And the other end of the second switch tube S2The drain electrode of the second diode D2The anode of (2), the second capacitor C2The negative electrode of (1) is connected;
the second switch tube S2And the first capacitor C1Negative electrode of, the first diode D1The anode of (2) is connected;
the second diode D2And the third inductor L3One terminal of, the third capacitance C3The positive electrode of (1) is connected;
the third inductor L3And the other end of the third diode D3The anode of (2), the second capacitor C2The positive electrode of (1) is connected;
the third diode D3And the output filter capacitor CoThe positive electrode of (1) is connected;
the input filter capacitor CinAnd the first switch tube S1Source electrode of, the first diode D1The cathode of (2), the third capacitor C3Negative pole of (1), the output filter capacitor CoThe negative electrode of (1);
the input filter capacitor CinPositive pole and DC input power UinIs connected to the positive terminal of the input filter capacitor CinNegative pole and DC input power UinIs connected.
The output filter capacitor CoIs connected with the positive end of the direct current load R, and the output filter capacitor CoIs connected with the negative pole end of the direct current load R.
When outputting the voltage UoAverage voltage value and inputVoltage UinWhen the ratio of the average voltage value of the high-gain converter is greater than 3, the invention also provides a control method of the high-gain converter, which comprises the following steps:
sampling value u of output voltageo,fAnd the output voltage reference value uo,refComparing, sending the error signal to output voltage controller for processing to obtain a modulation signal ur；
Modulated signal urAnd a first unipolar triangular carrier uc1Crossing to generate a first switch tube S1Drive signal u ofgs1；
Modulated signal urAnd a second unipolar triangular carrier uc2Intercept to generate a second switch tube S2Drive signal u ofgs2；
Wherein the first unipolar triangular carrier uc1And a second unipolar triangular carrier uc2Are equal in amplitude, equal in frequency, and 180 deg. out of phase.
Further, the ideal voltage gain G of the high-gain converter is:
Figure BDA0003554080180000021
wherein D is a first switch tube S1Drive signal u ofgs1Of the duty cycle of (c).
Further, a first switch tube S1A second switch tube S2A first diode D1A second diode D2And a third diode D3The voltage stress of (a) is:
Figure BDA0003554080180000022
US1、US2are respectively a first switch tube S1A second switch tube S2The voltage stress experienced; u shapeD1、UD2And UD3Are respectively a first diode D1A second diode D2And a third diode D3BearVoltage stress of (d); u shapeinIs the average value of the input voltage, UoIs the average value of the output voltage.
Compared with the prior art, the high-gain converter for the photovoltaic direct-current module has the advantages that the number of power tubes is small, and the structure is relatively simple; and the voltage stress of the power tube is smaller. Meanwhile, the boosting capacity is extremely strong, and the voltage gain is (4D-D)2-1)/(1-D)2. In addition, the first inductance L1And a second inductance L2The input current is shared together, the input current is continuous, and the ripple rate of the input current is far less than that of the first inductor L1And a second inductance L2Thereby reducing the input filter capacitance and volume and improving reliability. Therefore, the improved gain converter is suitable for a photovoltaic direct current module.
Drawings
Fig. 1 is a schematic circuit diagram of a high-gain converter for a photovoltaic dc module according to the present application;
FIG. 2 is a control method for the high gain converter of the photovoltaic DC module shown in FIG. 1;
fig. 3 is an equivalent diagram of 4 operating modes of the high-gain converter for the photovoltaic dc module shown in fig. 1 in one switching period;
FIG. 4 is a waveform diagram illustrating the main operation of the high-gain converter for the photovoltaic DC module shown in FIG. 1 during a switching period;
FIG. 5 is a schematic diagram of an average current equivalent circuit of the high gain converter for the photovoltaic DC module shown in FIG. 1;
fig. 6 is a simulated waveform diagram of the high-gain converter for the photovoltaic dc module shown in fig. 1.
Detailed Description
The technical solutions in the embodiments of the present application will be described clearly and completely with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The invention provides a high-gain converter for a photovoltaic direct current module, and the circuit structure is shown as figure 1. The high-gain converter comprises an input filter capacitor CinA first capacitor C1A second capacitor C2A third capacitor C3An output filter capacitor CoA first inductor L1A second inductor L2A third inductor L3A first switch tube S1A second switch tube S2A first diode D1A second diode D2A third diode D3；
Input filter capacitor CinPositive pole and first inductance L1One terminal of (1), a second inductance L2Is connected with one end of the connecting rod; first inductance L1The other end of the first switch tube S1Drain electrode of, first capacitor C1The positive electrode of (1) is connected; second inductance L2And the other end of the first switch tube S2Drain electrode of the first diode D2Anode of, a second capacitor C2The negative electrode of (1) is connected; a second switch tube S2Source electrode of and the first capacitor C1Negative electrode of (1), first diode D1The anode of (2) is connected; second diode D2Cathode and third inductor L3One terminal of (C), a third capacitor C3The positive electrode of (2) is connected; third inductance L3And the other end of the first diode D and a third diode D3Anode of (2), second capacitor C2The positive electrode of (1) is connected; third diode D3Cathode and output filter capacitor CoThe positive electrode of (1) is connected; input filter capacitor CinNegative pole of (2) and first switch tube S1Source electrode of, the first diode D1Cathode and third capacitor C3Negative electrode and output filter capacitor CoIs connected to the negative electrode of (1).
Input filter capacitor CinPositive pole and DC input power UinIs connected to the positive terminal of the input filter capacitor CinNegative electrode of (2) and DC input power supply UinIs connected.
Output filter capacitor CoPositive electrode and direct currentThe positive polarity end of the load R is connected with the output filter capacitor CoIs connected with the negative polarity end of the direct current load R.
When outputting the voltage UoAverage voltage value of and input voltage UinWhen the ratio of the average voltage values is greater than 3, the invention provides a control method of the high-gain converter, a control block diagram is shown in fig. 2, and the control method comprises the following steps:
will output a voltage uoIs sampled by a value uo,fAnd the output voltage reference value uo,refComparing, and sending the error signal to the output voltage controller for processing; obtaining a modulated signal ur；
Modulated signal urWith the first unipolar triangular carrier uc1Crossing to generate a first switch tube S1Drive signal u ofgs1；
Modulated signal urAnd a second unipolar triangular carrier uc2Crossing to generate a second switch tube S2Drive signal u ofgs2；
Wherein the first unipolar triangular carrier uc1And a second unipolar triangular carrier uc2Have equal amplitude and same frequency, have 180 degrees phase difference, and D is a first switch tube S1Drive signal u ofgs1The duty cycle of (c).
Following the output voltage U of the converter shown in FIG. 1oAverage voltage value of and input voltage UinThe operation when the ratio of the average voltage values of (1) is more than 3 will be described.
To simplify the analysis, the following assumptions were made: first switch tube S1A second switch tube S2A first diode D1A second diode D2A third diode D3An input filter capacitor CinA first capacitor C1A second capacitor C2A third capacitor C3Output filter capacitor CoA first inductor L1A second inductor L2A third inductor L3Are all ideal devices; input filter capacitor CinA first capacitor C1A second capacitor C2A third capacitor C3An output filter capacitor CoLarge enough that voltage ripple is negligible; first inductance L1A second inductor L2A third inductor L3The current of (2) is continuous; DC input power UinThe negative electrode of (3) is a zero potential reference point, and the direct current load R is pure resistance. After the converter enters a steady state, the working process of the converter in one switching period can be divided into 4 modes. The equivalent circuit of each mode is shown in fig. 3. The main waveforms during one switching cycle are shown in fig. 4.
The following are distinguished:
t0before the moment, the second switch tube S2And a first diode D1Turning off; first switch tube S1A second diode D2And a third diode D3And conducting.
Mode 1[ t ]0,t1](the equivalent circuit is shown in FIG. 3 (a))
t0At the moment, the second switch tube S2A second diode D2And a third diode D3And (6) turning off. DC input power UinThrough a first switch tube S1To the first inductor L1Charging; at the same time, the DC input power UinAnd a first capacitor C1Through a first switch tube S1And a second switching tube S2To the second inductance L2And (6) charging. In addition, the first capacitor C1And a third capacitance C3Through a first switch tube S1And a second switching tube S2To a second capacitance C2And a third inductance L3And (6) charging. First inductance L1A second inductor L2And a third inductance L3Are subject to a forward voltage. During this time, there are:
Figure BDA0003554080180000031
in the formula of UinIs the average value of the input voltage; u shapeC1、UC2And UC3Are respectively a first capacitor C1A second capacitor C2And a third capacitance C3The terminal voltage of (a); l is a radical of an alcohol1、L2And L3Are respectively a first inductance L1A second inductor L2And a third inductance L3The inductance value of (a); i.e. iL1、iL2And iL3Are respectively a first inductance L1A second inductor L2And a third inductance L3The current of (2).
t1At the moment, the first switch tube S1Off, modality 1 ends and modality 2 begins.
Mode 2[ t ]1,t2](the equivalent circuit is shown in FIG. 3 (b))
First switch tube S1Off, the first diode D1And conducting. DC input power UinAnd a first inductance L1Through a first diode D1To the first capacitor C1And (6) charging. At the same time, the DC input power UinThrough a first diode D1And a second switching tube S2To the second inductance L2And (6) charging. In addition, a third capacitance C3Through a first diode D1And a second switching tube S2To the third inductance L3And a second capacitor C2And (6) charging. First inductance L1Bearing reverse voltage, second inductance L2And a third inductance L3Are subject to a forward voltage. During this time, there are:
Figure BDA0003554080180000041
in the formula of UoIs the average value of the output voltage.
t2At the moment, the first switch tube S1Open, mode 2 ends and mode 3 begins.
Mode 3[ t ]2,t3](the equivalent circuit is shown in FIG. 3 (c))
First switch tube S1An on, first diode D1And (6) turning off.
First inductance L1A second inductor L2And a third inductance L3The current expression of (c) is the same as mode 1.
t3At the moment, the second switch tube S2Shutdown, modality 3 ends, and modality 4 begins.
Mode 4[ t ]3,t4](the equivalent circuit is shown in FIG. 3 (d))
A second switch tube S2Off, second diode D2And a third diode D3And conducting. DC input power supply UinA second inductor L2A third inductor L3And a second capacitor C2Through a second diode D2And a third diode D3To the DC load R and the third capacitor C3And (6) charging. In addition, a DC input power supply UinThrough a first switch tube S1To the first inductor L1And (6) charging. First inductance L1Bearing forward voltage, a second inductor L2And a third inductance L3Are subjected to reverse voltages. During this time, there are:
Figure BDA0003554080180000042
t4at the moment, the second switch tube S2And (4) switching on, ending the mode 4 and entering the next switching period.
Based on the above operating principle of the high gain converter of the present invention, the steady state characteristics thereof are analyzed below.
According to the first inductance L1A second inductor L2And a third inductance L3The voltage-second balance of (a) can be obtained:
Figure BDA0003554080180000043
from fig. 3, it can be derived:
UC2+UC3＝Uo (5)
the voltage gain of the invented high gain converter can be obtained from equations (4) and (5) as follows:
Figure BDA0003554080180000044
first switch tube S1A second switch tube S2A first diode D1A second diode D2And a third diode D3The voltage stresses of (a) are respectively:
Figure BDA0003554080180000045
in the above formula, US1、US2Are respectively a first switch tube S1A second switch tube S2The voltage stress experienced; u shapeD1、UD2And UD3Are respectively a first diode D1A second diode D2And a third diode D3The voltage stress experienced.
After the steady state is entered, the average current of the capacitor is zero, so that the average current equivalent circuit diagram of the high gain converter shown in fig. 1 can be obtained, as shown in fig. 5, which can be obtained from fig. 5:
Figure BDA0003554080180000051
in the above formula, IL1、IL2And IL3Are respectively a first inductance L1A second inductor L2And a third inductance L3Average value of current of (a); i isD1、ID2And ID3Are respectively a first diode D1A second diode D2And a third diode D3Average value of current of (a); i isS1、IS2Are respectively a first switch tube S1A second switch tube S2Average value of current of (a); i isoIs the average value of the output current.
The converter of the present invention is designed with the following parameters.
The design criteria of the converter are: switching frequency fs100kHz, input voltage U in20V, maximum output power Po,max250W, output voltage Uo＝400V。
According to the above index, the duty ratio D satisfies the following expression (6):
Figure BDA0003554080180000052
the duty ratio D can be obtained from equation (9):
d ≈ 0.737(10) inductance L of general inductor and current ripple amount Δ I of inductorinductorSatisfies the following conditions:
Figure BDA0003554080180000053
in the formula of UinductorThe value of the forward or reverse voltage borne by the inductor, t is the forward or reverse voltage U borne by the inductor in one switching periodinductorTime of (d).
It is generally required that the maximum current ripple allowed by the inductor does not exceed 30% of its maximum average current, i.e. the first inductor L1Pulsating quantity of current Δ IL1And a first inductance L1Maximum average current I ofL1,maxSatisfies the following conditions: delta IL1≤0.3IL1,maxIn conjunction with fig. 3 and equation (11), there are:
Figure BDA0003554080180000054
similarly, the second inductor L2Pulsating quantity of current Δ IL2A second inductor L2Maximum average current I ofL2,maxSatisfies the following conditions: delta IL2≤0.3IL2,maxIn conjunction with fig. 3 and equation (11), there are:
Figure BDA0003554080180000061
similarly, the second inductor L3Pulsating quantity of current Δ IL3A second inductor L3Maximum average current I ofL3,maxSatisfies the following conditions: delta IL3≤0.3IL3,maxCombining FIG. 3 with the formula (A)11) Then, there are:
Figure BDA0003554080180000062
usually, the capacitance C of the capacitor and the voltage pulsation Δ U of the capacitorcapacitorSatisfies the following conditions:
Figure BDA0003554080180000063
in the formula IcapacitorThe average current value for charging or discharging the capacitor, and t is the time for charging or discharging the capacitor in one switching period.
Typically, the capacitor voltage pulse rate is required to be lower than 1%, and when fig. 5 and equation (15) are combined, the following results are obtained:
Figure BDA0003554080180000064
Figure BDA0003554080180000065
Figure BDA0003554080180000071
based on the modal analysis and parameter design of the high-gain converter, the high-gain converter is subjected to simulation verification as follows:
in order to verify the correctness of theoretical analysis, according to the parameter design, Saber simulation software is used for carrying out simulation verification on the boosted voltage transformer, and specific values are as follows: a first capacitor C 150 muF, second capacitance C 220 muF, third capacitance C 320 muF, first inductance L10.15mH, second inductance L20.5mH, third inductance L3Is 2.5mH, and is input into a filter capacitor C in20 muF, output filter capacitance Co＝20μF。
Fig. 6 shows simulated waveforms for the high gain converter of the present invention. It can be seen that the drive signal ugs1And ugs2The duty ratio is the same, and the initial phase difference is 180 DEG; when duty ratio D is approximately equal to 0.737 and input voltage U is obtainedinWhen 20V, the output voltage of the converter is U o400V, measured voltage gain is Uo/U in400/20-20, with theoretical value G-4D-D2-1)/(1-D)2＝(4×0.737-0.7372-1)/(1-0.737)220 substantially coincide. At the same time, it can also be seen that the input current ripple rate Δ iL/IL0.9/12.6 ≈ 7%, far less than the first inductance L1Ripple rate Δ i ofL1/IL11/8.5 ≈ 12% and a second inductance L2Ripple rate Δ i ofL2/IL21/4.1 ≈ 25%. In addition, it can be seen that the first capacitance C1A first switch tube S1And a first diode D1Voltage stress U ofC1＝US1＝UD1About 76V, second capacitance C2Voltage stress U ofC2187V, second capacitance C3Voltage stress U ofC3213V, the second switch tube S2A second diode D2And a third diode D3Voltage stress U ofS2＝UD2＝UD3About 289V, all consistent with theoretical values.
The high-gain converter provided by the invention can be applied to a photovoltaic direct current module and has the following advantages: (1) the boosting capacity is extremely strong, and the voltage gain is (4D-D)2-1)/(1-D)2Doubling; (2) the number of the power tubes is small, and the structure is relatively simple; (3) the voltage stress of the power tube is small; (4) current i of the first and second inductorsL1And iL2Are all continuous, and the pulse rate of the input current is far less than that of the first inductive current iL1And a second inductor current iL2The pulse rate of (a).
It is noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The above description of the embodiments is only intended to facilitate the understanding of the method of the invention and its core idea, and not to limit it. It should be noted that, for those skilled in the art, without departing from the principle of the present invention, several improvements and modifications can be made to the present invention, and these improvements and modifications also fall into the protection scope of the present invention.

Claims (4)

1. A high gain converter for a photovoltaic DC module comprises an input filter capacitor CinA first capacitor C1A second capacitor C2A third capacitor C3An output filter capacitor CoA first inductor L1A second inductor L2A third inductor L3A first switch tube S1A second switch tube S2A first diode D1A second diode D2A third diode D3；
The input filter capacitor CinAnd the first inductor L1One end of said second inductor L2Is connected with one end of the connecting rod;
the first inductor L1And the other end of the first switch tube S1The drain electrode of (1), the first capacitor C1The positive electrode of (2) is connected;
the second inductor L2And the other end of the first switch tube S2The drain electrode of the second diode D2The anode of (2), the second capacitor C2Is connected with the negative pole of the anode;
the second switch tube S2And the first capacitor C1Negative electrode of, the first diode D1The anode of (2) is connected;
the second diode D2And the third inductor L3One terminal of, the third capacitance C3The positive electrode of (2) is connected;
the third inductance L3And the other end of the third diode D3The anode of (2), the second capacitor C2The positive electrode of (2) is connected;
the third diode D3And the output filter capacitor CoThe positive electrode of (2) is connected;
the input filter capacitor CinAnd the first switch tube S1Source electrode of, the first diode D1The cathode of (2), the third capacitor C3Negative pole of (1), the output filter capacitor CoThe negative electrode of (1) is connected;
the input filter capacitor CinAnode and input DC power supply UinIs connected to the positive terminal of said input filter capacitor CinNegative pole and input DC power supply UinIs connected with the negative polarity end of the capacitor;
the output filter capacitor CoIs connected with the positive end of the direct current load R, and the output filter capacitor CoIs connected with the negative pole end of the direct current load R.
2. A control method for a high gain converter as claimed in claim 1, characterized in that the control method is applied to the output voltage UoAverage voltage value of and input voltage UinWhen the ratio of the average voltage values of (a) is greater than 3, the control method includes:
will output a voltage uoIs sampled by a value uo,fAnd the output voltage reference value uo,refComparing, and sending the error signal to the output voltage controller for processing; obtaining a modulated signal ur；
Modulated signal urWith the first unipolar triangular carrier uc1Intercept, produceFirst switch tube S1Drive signal u ofgs1；
Modulated signal urAnd a second unipolar triangular carrier uc2Crossing to generate a second switch tube S2Drive signal u ofgs2；
Wherein the first unipolar triangular carrier uc1And a second unipolar triangular carrier uc2Are equal in amplitude and same in frequency, and are 180 ° out of phase with each other.
3. The control method of claim 2, wherein the ideal voltage gain G of the high-gain converter is:
Figure FDA0003554080170000011
wherein D is a first switch tube S1Drive signal u ofgs1The duty cycle of (c).
4. The control method of claim 2, wherein the first switch tube S of the high-gain converter1A second switch tube S2A first diode D1A second diode D2And a third diode D3The voltage stress experienced is:
Figure FDA0003554080170000012
wherein, US1、US2Are respectively a first switch tube S1A second switch tube S2The voltage stress experienced; u shapeD1Is a first diode D1Bearing voltage stress, UD2Is a second diode D2Bearing voltage stress, UD3Is a third diode D3The voltage stress experienced; u shapeinIs the average value of the input voltage, UoIs the average value of the output voltage.
CN202210272294.8A 2022-03-18 2022-03-18 High-gain converter for photovoltaic direct current module and control method thereof Withdrawn CN114583954A (en)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115498875A (en) * 2022-09-29 2022-12-20 福州大学 Zero-ripple high-gain circuit based on magnetic integration design and control method thereof

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115498875A (en) * 2022-09-29 2022-12-20 福州大学 Zero-ripple high-gain circuit based on magnetic integration design and control method thereof

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