CN112688566B - Digital synchronous rectification control method and digital signal processor - Google Patents
Digital synchronous rectification control method and digital signal processor Download PDFInfo
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Abstract
The invention provides a digital synchronous rectification control method, which is applied to an LLC (logical link control) resonant converter, wherein a secondary side of the LLC resonant converter is connected with a rectification circuit, and the rectification circuit comprises a plurality of switching tubes; the digital synchronous rectification control method comprises the following steps: determining load parameters of the LLC resonant converter according to multiple working modes of the LLC resonant converter and the constraint conditions of each working mode, wherein the load parameters comprise voltage parameters and current parameters; determining the current working mode of the LLC resonant converter according to the load parameters, wherein the current working mode is one of a plurality of working modes; determining the on-time or off-time of each switching tube in a specific period according to the switching frequency, the load parameters and the current working mode of the LLC resonant converter; and performing synchronous rectification control on the LLC resonant converter according to the on time or the off time of each switching tube in a specific period. By adopting the invention, the current on-off time of the rectifier tube can be accurately calculated in the full load range, and the synchronous rectification control is carried out.
Description
Technical Field
The invention relates to the technical field of power conversion, in particular to a digital synchronous rectification control method and a digital signal processor.
Background
LLC resonant converters have become one of the most widely used topologies in DCDC topology due to their advantages of simple structure, high efficiency and good soft switching characteristics. The LLC primary side switching tube can realize Zero Voltage Switching (ZVS) in a full load range through reasonable design, the switching loss is greatly reduced, but in low-voltage and high-current application, a secondary side rectifier diode can generate non-negligible loss. Therefore, a synchronous rectification technology is usually adopted, that is, a MOS transistor with a small on-resistance is used to replace a diode for conduction, which greatly reduces the conduction loss of the LLC secondary side.
The existing synchronous rectification scheme can be roughly divided into a hardware scheme and a software scheme. The hardware scheme mainly adopts a synchronous rectification chip and needs to add a voltage or current detection circuit and the like, so that the system cost is increased on one hand, and on the other hand, due to the adoption of fixed hardware assistance, the DCDC bidirectional switching application is difficult to realize; the software scheme is mainly based on traditional FHA (First Harmonic Approximation, fundamental equivalent) model control or a table look-up method and the like, the FHA model has a large error at a deviation resonance point, so that the FHA model cannot guide accurate switching action of the rectifier tube, the table look-up method is to obtain approximate switching time of the rectifier tube by fitting a large amount of data measured through experiments, but the table look-up method is difficult to conclude the operating condition of a full load range because multiple modes often exist during LLC operation.
Therefore, how to accurately calculate the current on-off time of the rectifier tube in the full-load range and perform synchronous rectification control is a problem to be solved urgently at present.
Disclosure of Invention
In view of the above, it is necessary to provide a digital synchronous rectification control method and a digital signal processor, which can accurately calculate the current on/off time of a rectifier tube in a full load range and perform synchronous rectification control, for the technical problem that can be solved by the independent claims.
The invention provides a digital synchronous rectification control method, which is applied to an LLC (logical link control) resonant converter, wherein a secondary side of the LLC resonant converter is connected with a rectification circuit, and the rectification circuit comprises a plurality of switching tubes; the method comprises the following steps:
determining load parameters of the LLC resonant converter according to multiple working modes of the LLC resonant converter and the constraint conditions of each working mode, wherein the load parameters comprise voltage parameters and current parameters;
determining a current working mode of the LLC resonant converter, wherein the current working mode is one of a plurality of working modes;
determining the on-time or off-time of each switching tube in a specific period according to the switching frequency, the load parameters and the current working mode of the LLC resonant converter;
and performing synchronous rectification control on the LLC resonant converter according to the on-time or off-time of each switching tube in a specific period.
Optionally, the load parameter is a load current.
Optionally, determining a current operating mode of the LLC resonant converter according to a load parameter of the LLC resonant converter includes:
when the load current of the LLC resonant converter is within a first preset range, determining the working mode boundary of the LLC resonant converter in a specific period;
and determining the current working mode of the LLC resonant converter according to the working mode boundary.
Optionally, when the load current of the LLC resonant converter is within a first preset range, determining the boundary of the operation mode of the LLC resonant converter in a specific period includes:
when the load current of the LLC resonant converter is greater than or equal to a first preset current, determining a modal boundary equation and a boundary constraint condition among a plurality of first modes, wherein the plurality of working modes comprise the first modes;
and solving each modal boundary equation according to each boundary constraint condition to determine the working modal boundary of the LLC resonant converter in a specific period.
Optionally, the modal boundary equations and boundary constraints between the plurality of first modalities include:
a modal boundary equation and a boundary constraint condition between the PN mode and the PON mode;
modal boundary equations and boundary constraints between the PON modality and the PO modality;
a modal boundary equation and boundary constraints between the PO mode and the OPO mode;
modal boundary equations and boundary constraints between the OPO modality and the O modality;
modal boundary equations and boundary constraints between the OPO mode and the NOP mode; and the number of the first and second groups,
modal boundary equations and boundary constraints between NOP and NP modalities.
Optionally, when the load current of the LLC resonant converter is smaller than the first preset current, it is determined that the current operating mode of the LLC resonant converter is the second mode, where the second mode is one of the multiple operating modes.
Optionally, the constraint condition of each operating mode includes at least one of a continuity constraint condition, a symmetry constraint condition, a switching point secondary side current of 0, a load current constraint condition, a half-cycle normalization constraint condition, and an excitation voltage constraint condition.
Optionally, before determining the load parameter of the LLC resonant converter according to multiple operating modes of the LLC resonant converter and constraints of each operating mode, the method includes:
determining a normalized time domain differential equation of the LLC resonant converter under a P mode, an O mode and an N mode according to a kirchhoff voltage law and a kirchhoff current law;
solving a normalized time domain differential equation to obtain a current parameter and a voltage parameter of the LLC resonant converter under a P mode, an O mode and an N mode respectively;
and determining multiple working modes of the LLC resonant converter according to the current parameter, the voltage parameter and the volt-second balance principle.
In another aspect, the present invention further provides a digital signal processor, which includes a memory and a digital processing program stored in the memory, and the digital processing program is executed to implement the steps of the digital synchronous rectification control method according to any one of the above.
According to the method, the load parameters of the LLC resonant converter are determined according to multiple working modes of the LLC resonant converter and the constraint conditions of each working mode; determining the current working mode of the LLC resonant converter according to the load parameters; and determining the on-time or off-time of each switching tube in a specific period according to the switching frequency, the load parameters and the current working mode of the LLC resonant converter, so as to perform synchronous rectification control on the LLC resonant converter according to the on-time or off-time of each switching tube in the specific period. The LLC resonant converter is subjected to synchronous rectification control through a pure software scheme, an additional synchronous rectification chip or a voltage and current detection circuit is not needed, the current on-off time of the rectifier tube can be accurately calculated in a full-load range only through known switching frequency and load current (output power), and the LLC resonant converter is subjected to synchronous rectification control. Not only can reduce the hardware cost, but also is easy to realize.
Drawings
FIG. 1 is a schematic diagram of a topology of an LLC resonant converter in an embodiment;
FIG. 2 is a flow diagram illustrating a method for synchronous rectification in one embodiment;
FIG. 3a is an equivalent circuit diagram of an LLC resonant converter in the P-mode in one embodiment;
FIG. 3b is an equivalent circuit diagram of the LLC resonant converter in the O mode in one embodiment;
FIG. 3c is an equivalent circuit diagram of the LLC resonant converter in the N-mode in one embodiment;
FIG. 4a is a plot of a fit of the synchronous rectification switching times for an OPO mode in one embodiment;
FIG. 4b is a plot of a fit of the synchronous rectification switching times for the PO mode in one embodiment;
FIG. 5a is a graph of gain versus switching frequency (M-fn) at the boundary between first modes in one embodiment;
FIG. 5b is a graph of load current versus switching frequency (Iout-fn) at the boundary between the first modes in one embodiment;
FIG. 5c is a modal boundary curve between OPO and PO modes in an embodiment
Fig. 6 is a schematic diagram of the overall configuration of the digital control system in one embodiment.
Detailed Description
In order to make the aforementioned objects, features and advantages of the present invention comprehensible, embodiments accompanied with figures are described in detail below. In the following description, numerous specific details are set forth in order to provide a thorough understanding of the present invention. This invention may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein.
In one embodiment, the invention provides a synchronous rectification method applied to an LLC resonant converter. For convenience of description, each of the followingThe embodiments are described by taking the basic topology of the LLC resonant converter as an example, and it is understood that the synchronous rectification method is also applicable to LLC resonant converters with other topologies. As shown in FIG. 1, the primary side of the LLC resonant converter is in a half-bridge structure, the secondary side is connected with a rectifying circuit 101, the rectifying circuit 101 comprises a plurality of switching tubes, for example, a switching tube SS1And a switching tube SS2. The passive device of the LLC resonant converter is provided with an excitation inductor L of a transformermResonant inductor LrAnd two resonance capacitors C connected in parallelr1And Cr2. The load of the LLC resonant converter is equivalently connected in series with the resonant network, and the circuit impedance can be changed by controlling the switching frequency of the switching tube, so that the output voltage of the LLC resonant converter is changed. When LLC resonant converter is operated in frequency modulation mode, input voltage of resonant cavity is amplitude Vin50% duty cycle square wave of/2, with symmetry in the positive and negative half cycles, so that only the positive half cycle (S) of the input voltage followsp1Open time) for example.
As shown in fig. 2, the synchronous rectification method includes the steps of:
s201, determining load parameters of the LLC resonant converter according to multiple working modes of the LLC resonant converter and the constraint conditions of each working mode, wherein the load parameters comprise voltage parameters and current parameters.
In the positive half period of the input voltage, according to different current conduction states of the secondary side, the working mode of the LLC resonant converter can be divided into a P mode, an O mode and an N mode for providing three basic modes, wherein the equivalent circuit of the LLC resonant converter in the P mode is shown in fig. 3a, the equivalent circuit of the LLC resonant converter in the O mode is shown in fig. 3b, and the equivalent circuit of the LLC resonant converter in the N mode is shown in fig. 3 c.
In this embodiment, the multiple working modes of the LLC resonant converter refer to various modes that may occur when the LLC resonant converter operates, and from the perspective of the rectifying side, the multiple working modes of the LLC resonant converter are the above three basic modes and their possible permutation and combination, that is, the multiple working modes of the LLC resonant converter include 9 modes, such as p (n) mode, O mode, NP mode, OP mode, PO mode, PN mode, NOP mode, OPO mode, and PON mode.
Specifically, according to the constraint condition of each working mode, a mode equation corresponding to each working mode can be determined, and by solving each mode equation, the load parameter of the LLC resonant converter can be determined. The load parameter may be a voltage analytic solution and a current analytic solution respectively corresponding to the LLC resonant converter in the above-mentioned various different modes.
S202, determining the current working mode of the LLC resonant converter according to the switching frequency and the load parameters of the LLC resonant converter, wherein the current working mode is one of multiple working modes.
In this embodiment, in order to determine the switching time of each switching tube in the rectifying circuit in real time, the current working mode of the LLC resonant converter needs to be determined in real time. When the LLC resonant converter operates, the operating mode may or may not change according to the size of the load. Generally, if the load is large, the operation mode of the LLC resonant converter will change during the positive half cycle of the input voltage, for example, between the PN mode and the PON mode, or between the PON and the PO mode, or between the PO and the OPO mode, or between the OPO and the O mode, or between the OPO and the NOP mode, or between the NOP and the NP mode. And when the load is small, the operation mode of the LLC resonant converter will be fixed to the OPO mode in the positive half period of the input voltage. Therefore, the modal change process of the LLC resonant converter in a specific period can be determined according to the load parameters of the LLC resonant converter, and further the current working mode of the LLC resonant converter can be determined.
And S203, determining the turn-on time or turn-off time of each switching tube in a specific period according to the switching frequency, the load parameters and the current working mode of the LLC resonant converter.
The switching frequency fn of the LLC resonant converter is usually a known quantity, and the on-time and/or off-time of each switching tube on the secondary side in a specific period can be obtained by solving according to the switching frequency fn, the load current Iout, and the current operating mode. Taking the OPO mode as an example, the on-time and/or the off-time of each switching tube on the secondary side can be determined by solving the duration time of an O interval and the duration time of a P interval in the OPO mode; taking the PO state as an example, the on-time and/or off-time of each switching tube on the secondary side can be determined by solving the duration of the P interval.
For convenience of description, in each embodiment of the present application, a specific period is a positive half period of an input voltage, and it is understood that the specific period may also be a negative half period, or a whole period, or several periods, which is not limited in the present application.
And S204, performing synchronous rectification control on the LLC resonant converter according to the on-time or off-time of each switching tube in a specific period.
As an embodiment, after determining the on-time or off-time of each switching tube in a specific period, a surface fitting may be used to obtain a fitted graph of the synchronous rectification switching time as shown in fig. 4a and 4 b. Wherein FIG. 4a is a plot of a fit of the synchronous rectified switching time for an example in which the current mode is the OPO mode; fig. 4b is a fitting graph of the synchronous rectification switching time in the PO mode as the current mode in one example. According to the fitting polynomial obtained by the fitting graph, the on-time and the off-time of the synchronous rectification switch tube can be solved in real time, and further synchronous rectification control is realized.
According to the method, the load parameters of the LLC resonant converter are determined according to multiple working modes of the LLC resonant converter and the constraint conditions of each working mode, for example, a voltage and current analytic solution of the LLC resonant converter under various modes is solved; determining the current working mode of the LLC resonant converter according to the switching frequency and the load parameters of the LLC resonant converter; and determining the on-time or off-time of each switching tube in a specific period according to the switching frequency, the load parameters and the current working mode of the LLC resonant converter, so as to perform synchronous rectification control on the LLC resonant converter according to the on-time or off-time of each switching tube in the specific period. The LLC resonant converter is subjected to synchronous rectification control through a pure software scheme, an additional synchronous rectification chip or a voltage and current detection circuit is not needed, the current on-off time of the rectifier tube can be accurately calculated in a full-load range only through known switching frequency and load current (output power), and the LLC resonant converter is subjected to synchronous rectification control. Not only can reduce the hardware cost, but also is easy to realize.
In one embodiment, before determining the load parameter of the LLC resonant converter according to a plurality of operating modes of the LLC resonant converter and constraints of each operating mode, the method further comprises: determining a normalized time domain differential equation of the LLC resonant converter under a P mode, an O mode and an N mode according to a kirchhoff voltage law and a kirchhoff current law; solving a normalized time domain differential equation to obtain a current parameter and a voltage parameter of the LLC resonant converter under a P mode, an O mode and an N mode respectively; and determining multiple working modes of the LLC resonant converter according to the current parameter, the voltage parameter and the volt-second balance principle. Taking the P-mode as an example, the normalized time domain differential equation of the LLC resonant converter in the P-mode is:
solving a normalized time domain differential equation to obtain current parameters and voltage parameters of the LLC resonant converter in the P mode respectively as follows:
where θ is ωrt is electrical angle, M ═ U2/U1For cavity gain, k is Lr/Lm。
According to the current parameter, the voltage parameter and the volt-second balance principle, a plurality of working modes of the LLC resonant converter can be determined, wherein the working modes comprise 9 modes such as a P (N) mode, an O mode, an NP mode, an OP mode, a PO mode, a PN mode, an NOP mode, an OPO mode and a PON mode.
In one embodiment, optionally, the constraint condition of each of the operation modes includes at least one of a continuity constraint condition, a symmetry constraint condition, a switching point secondary side current of 0, a load current constraint condition, a half-cycle normalization constraint condition (i.e., the duration is normalized by half a switching cycle), and an excitation voltage constraint condition. Taking the OPO mode as an example, according to the above six constraints, the modal equation in the OPO mode can be determined as follows:
θO1+θP+θO2＝γ＝π/fn
umO1，n(θO1)＝M
in one embodiment, in step S201, the current operation mode of the LLC resonant converter can be determined according to the resonant frequency and the load current of the LLC resonant converter.
In one embodiment, when the load current of the LLC resonant converter is smaller than a first preset current, the current operating mode of the LLC resonant converter is determined to be a second mode, where the second mode is one of the above-mentioned operating modes. When the load current of the LLC resonant converter is within a first preset range, determining the working mode boundary of the LLC resonant converter in a specific period, and determining the current working mode of the LLC resonant converter according to the working mode boundary. The minimum value in the first preset range is larger than or equal to the current value of the first preset current.
For example, in one specific example, the power of the LLC resonant converter is 650W, and its circuit parameters are: the input voltage Uin is 400V, the output voltage Uo is 40-70V, the resonance inductance Lr is 23uH, the parallel inductance Lm of the transformer is 170uH, the resonance capacitance Cr1 is Cr2 is 112nf, and the transformer transformation ratio n is 17: 2. When the load current of the LLC resonant converter is less than 6.66A, the operation mode of the LLC resonant converter is fixed to the OPO mode. When the load current of the LLC resonant converter is greater than or equal to 6.66A, or when the load current of the LLC resonant converter is between 6.66A-10A, the operation mode of the LLC resonant converter will change from the OPO mode to the PO mode as the switching frequency increases from small to large.
Specifically, when the load current of the LLC resonant converter is greater than or equal to a first preset current, modal boundary equations and boundary constraints among a plurality of first modes are determined, wherein the plurality of working modes comprise the first modes. And solving each modal boundary equation according to each boundary constraint condition to determine the working modal boundary of the LLC resonant converter in a specific period.
The modal boundary equation and boundary constraint condition among the plurality of first modalities comprise a modal boundary equation and boundary constraint condition among a PN modality and a PON modality, a modal boundary equation and boundary constraint condition among a PON modality and a PO modality, a modal boundary equation and boundary constraint condition among a PO modality and an OPO modality, a modal boundary equation and boundary constraint condition among an OPO modality and an O modality, a modal boundary equation and boundary constraint condition among an OPO modality and an NOP modality, and a modal boundary equation and boundary constraint condition among an NOP modality and an NP modality.
Specifically, the boundary constraint conditions of the PN mode and the PON mode are: u. ofmO,n(0)＝-M；
Boundary constraint conditions of the PON mode and the PO mode are as follows: u. ofmO,n(θO)＝-M；
Boundary constraints of the PO modality and the OPO modality are: u. ofmO1,n(0)＝M；
Boundary constraints of the OPO mode and the O mode are as follows: i isout,n＝0；
Boundary constraints of the OPO modality and the NOP modality are: u. ofmO,n(θO)＝M
The boundary constraints of the NOP modality and the NP modality are: u. ofmO,n(0)＝M。
Solving a modal boundary equation between the first modes according to the boundary constraint conditions between the first modes, determining a critical switching frequency value between the first modes by combining the determined load current value, and obtaining a boundary relation curve as shown in fig. 5a, 5b and 5c, wherein fig. 5a is a gain-switching frequency (M-fn) curve at the boundary between the first modes, fig. 5b is a load current-switching frequency (Iout-fn) curve at the boundary between the first modes, and fig. 5c is a modal boundary curve between the OPO mode and the PO mode in one example. According to the boundary relation curves, the current working mode of the LLC resonant converter can be further determined.
In another aspect, the present invention further provides a digital signal processor, which is applicable to an LLC resonant converter, and includes a memory and an executable digital processing program stored in the memory, where the digital processing program is executable to implement the steps of the digital synchronous rectification control method according to any one of the foregoing embodiments to perform synchronous rectification control on the LLC resonant converter. For example, the digital signal processor (DSP controller) may be applied to a digital control system as shown in fig. 6.
It should be noted that, in the above embodiments, the terms "first" and "second" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include at least one such feature. In the description of the present invention, "a plurality" means at least two, e.g., two, three, etc., unless specifically limited otherwise.
The technical features of the above embodiments can be arbitrarily combined, and for the sake of brevity, all possible combinations of the technical features in the above embodiments are not described, but should be considered as the scope of the present specification as long as there is no contradiction between the combinations of the technical features.
The above examples only show some embodiments of the present invention, and the description thereof is more specific and detailed, but not construed as limiting the scope of the invention. It should be noted that, for a person skilled in the art, several variations and modifications can be made without departing from the inventive concept, which falls within the scope of the present invention. Therefore, the protection scope of the present patent shall be subject to the appended claims.
Claims (7)
1. A digital synchronous rectification control method is applied to an LLC resonant converter, and is characterized in that a secondary side of the LLC resonant converter is connected with a rectification circuit, and the rectification circuit comprises a plurality of switching tubes; the method comprises the following steps:
determining load parameters of the LLC resonant converter according to multiple working modes of the LLC resonant converter and the constraint conditions of each working mode, wherein the load parameters comprise voltage parameters and current parameters, and the multiple working modes comprise a P mode, an N mode, an O mode, an NP mode, an OP mode, a PO mode, a PN mode, an NOP mode, an OPO mode and a PON mode;
determining a current working mode of the LLC resonant converter according to the switching frequency of the LLC resonant converter and the load parameter, wherein the current working mode is one of the plurality of working modes;
determining the on-time or off-time of each switching tube in a specific period according to the switching frequency of the LLC resonant converter, the load parameters and the current working mode;
according to the on-time or off-time of each switching tube in a specific period, performing synchronous rectification control on the LLC resonant converter; the determining the current working mode of the LLC resonant converter according to the switching frequency of the LLC resonant converter and the load parameter includes:
when the load current of the LLC resonant converter is within a first preset range, determining the working mode boundary of the LLC resonant converter in a specific period;
and determining the current working mode of the LLC resonant converter according to the working mode boundary.
2. The digital synchronous rectification control method according to claim 1, wherein the determining the boundary of the operation mode of the LLC resonant converter in a specific period when the load current of the LLC resonant converter is in a first preset range comprises:
when the load current of the LLC resonant converter is greater than or equal to a first preset current, determining a modal boundary equation and a boundary constraint condition among a plurality of first modes, wherein the plurality of working modes comprise the plurality of first modes;
and solving each modal boundary equation according to each boundary constraint condition to determine the working modal boundary of the LLC resonant converter in a specific period.
3. The digital synchronous rectification control method of claim 2, wherein modal boundary equations and boundary constraints between the plurality of first modes comprise:
a modal boundary equation and a boundary constraint condition between the PN mode and the PON mode;
modal boundary equations and boundary constraints between the PON modality and the PO modality;
a modal boundary equation and boundary constraints between the PO mode and the OPO mode;
modal boundary equations and boundary constraints between the OPO modality and the O modality;
modal boundary equations and boundary constraints between the OPO mode and the NOP mode; and the number of the first and second groups,
modal boundary equations and boundary constraints between NOP and NP modalities.
4. The digital synchronous rectification control method according to claim 2, wherein when the load current of the LLC resonant converter is smaller than a first preset current, the LLC resonant converter is determined to be in a second mode, wherein the second mode is one of the plurality of operating modes.
5. The digital synchronous rectification control method of claim 1, wherein the constraint condition of each working mode comprises at least one of a continuity constraint condition, a symmetry constraint condition, a switching point secondary side current of 0, a load current constraint condition, a half-cycle normalization constraint condition and an excitation voltage constraint condition.
6. The digital synchronous rectification control method according to claim 1, wherein before determining the load parameter of the LLC resonant converter according to a plurality of operation modes of the LLC resonant converter and the constraint condition of each operation mode, the method comprises:
determining a normalized time domain differential equation of the LLC resonant converter under a P mode, an O mode and an N mode according to a kirchhoff voltage law and a kirchhoff current law;
solving the normalized time domain differential equation to obtain a current parameter and a voltage parameter of the LLC resonant converter under a P mode, an O mode and an N mode respectively;
and determining multiple working modes of the LLC resonant converter according to the current parameter, the voltage parameter and a volt-second balance principle.
7. A digital signal processor comprising a memory and a digital processing program stored on said memory, characterized in that said digital processing program, when executed, implements the steps of the digital synchronous rectification control method of any one of claims 1 to 6.
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