CN1113462C - Tuning control system - Google Patents

Abstract

A tuning mechanism is provided with a tuning circuit 1 constituted by cascade-connecting two phase shifting circuits to each other and a frequency control circuit 2 incorporating a phase difference detecting circuit 3 and a control voltage generating circuit 4. The circuit 3 converts the input and output signals of either of the two phase shifting circuits into rectangular-wave signals, calculates the exclusive OR of the rectangular-wave signals, and outputs the exclusive OR to the circuit 4. The circuit 4 smoothes and amplifies the output of the circuit 3 and adds a prescribed bias voltage to the amplified output to generate a control voltage for determining the tuning frequency of the tuning circuit 1. The control voltage is inputted to the two phase shifting circuits. The circuit 1, keeping the time constants of the phase shifting circuits equal to each other, adjusts the phase shift base on the control signal and equalizes the tuning frequency to the frequency of the input signal of the tuning circuit 1.

Description

Tuning control system

The present invention relates to a kind of only tuning control system by constant-frequency signal.

As you know, as existing filter and tuning circuit, the various structures of LC resonance etc. have been utilized.For example, though the intermediate frequency amplifier circuit of superheterodyne receiver comprises the function of filter, this intermediate frequency amplifier circuit, general many group intermediate frequency transformers (IFT) and the capacitor of adopting realized desirable frequency characteristic.For example, under the situation of AM receiver, set the centre frequency of 455kHz, be set in simultaneously under the situation of leaving centre frequency 9kHz, make it to have the attenuation of regulation.And, be to replace many group intermediate frequency transformers to realize desired frequency characteristic with a ceramic filter.

Yet, in the prior art of using above-mentioned superhet mode, for carrying out in the structure that tuning filter is an intermediate frequency amplifier circuit itself, owing to contain intermediate frequency transformer or ceramic filter, so integrated on the integrated circuit substrate to comprise their all circuit be difficult.

And,, simply realize that by means of the LC oscillator that utilizes the local oscillation transformer high-precision circuit is then realized by means of the PLL structure of utilizing crystal oscillation with the local oscillator circuit of this intermediate frequency amplifier circuit combination.Particularly, local oscillator circuit is being made under the situation of PLL structure, be difficult to comprise the integrated of the voltage-controlled type oscillator (VCO) that carries out sine-wave oscillation, so a part has been used mixing IC.

Like this, not only be difficult to integrated intermediate frequency amplifier circuit as filter work, and be difficult to integrated and its combination and comprise entire circuit before the local oscillator circuit that constitutes mechanical tuning device, therefore hope can have a kind of tuning control system of integrated whole mechanical tuning device.And, even suppose the overall filter that exists so far or to comprise the entire circuit of this filter integrated since take place on the circuit constant more discrete, so make each chip of making have different characteristics.Perhaps, owing to consider situations greatly such as centre frequency variation such as Yin Wendu, so, also need can reach reliably the tuning control system of desired frequency characteristics even carried out under the integrated situation.

The present invention makes for addressing this problem, and its purpose is to provide a kind of integrated new tuning control system that is suitable for.

Tuning control system of the present invention possesses: 2 phase-shift circuits of wildcard-filter style that comprise cascade, feed back to input one side of the above-mentioned phase-shift circuit of prime as feedback signal with the output of the above-mentioned phase-shift circuit that makes back level, simultaneously above-mentioned feedback signal and input signal are carried out add operation and be input to add circuit in the above-mentioned phase-shift circuit of prime, and the tuning circuit that assigned frequency signal is nearby passed through; And

When the frequency signal near handle has the afore mentioned rules frequency is input in the above-mentioned tuning circuit, according to the phase difference between the input/output signal of a phase-shift circuit that in above-mentioned tuning circuit, contains, the frequency control circuit that the tuned frequency of above-mentioned tuning circuit is overlapped with the frequency of the input signal of above-mentioned tuning circuit.

And, for example being 90 ° by the phase difference between the input/output signal of controlling, make a phase-shift circuit that in tuning circuit, comprises, tuned frequency becomes the frequency of always following input signal and changes, and both are overlapped frequency.

The simple declaration of accompanying drawing

Fig. 1 is the pie graph of mechanical tuning device of having used an embodiment of tuning circuit of the present invention;

Fig. 2 is the detailed pie graph of expression tuning circuit;

Fig. 3 represents to extract out the circuit diagram that the phase-shift circuit of the prime that is shown in Fig. 2 constitutes;

Fig. 4 is the vectogram that concerns between the voltage of input and output voltage and appearance on capacitor etc. of expression phase-shift circuit shown in Figure 3;

Fig. 5 is a circuit diagram of representing to extract out the phase-shift circuit formation of the back level that is shown in Fig. 2;

Fig. 6 is the vectogram that concerns between the voltage of input and output voltage and appearance on capacitor etc. of expression back level phase-shift circuit;

Fig. 7 is the circuit diagram that all is replaced into the circuit with transfer function K1 of 2 phase-shift circuits shown in Fig. 2 and bleeder circuit;

Fig. 8 be according to MILLER'S THEOREM conversion the circuit diagram of the circuit shown in Fig. 7;

Fig. 9 is the tuning characteristic figure of the tuning circuit shown in the presentation graphs 2;

Figure 10 is the phase diagram between the signal of input and output in 2 phase-shift circuits of expression;

Figure 11 is that the expression tuned frequency is than the phase diagram between the input and output that are input to each phase-shift circuit under the high situation of signal frequency in the prime phase-shift circuit;

Figure 12 is that the expression tuned frequency is than the phase diagram between the input and output of each phase-shift circuit under the low situation of the signal frequency in the level phase-shift circuit after being input to;

Figure 13 is the forming circuit figure of expression frequency control circuit;

Figure 14 is the sequential chart when being input to signal frequency in the tuning circuit relatively the tuned frequency of tuning circuit is high;

Figure 15 is the sequential chart when being input to signal frequency in the tuning circuit relatively the tuned frequency of tuning circuit is low;

Figure 16 is the circuit diagram of another configuration example of expression frequency control circuit;

Figure 17 is the sequential chart when being input to signal frequency in the tuning circuit that is shown in Figure 16 relatively tuned frequency is high;

Figure 18 is the sequential chart when being input to signal frequency in the tuning circuit that is shown in Figure 16 relatively tuned frequency is low;

Figure 19 is the pie graph that expression has the mechanical tuning device of FM detection concurrently;

Figure 20 is the detailed forming circuit figure of the frequency control circuit shown in expression Figure 19;

Figure 21 is a pie graph of representing to utilize the FM receiver of the mechanical tuning device that is shown in Figure 19;

Figure 22 is the pie graph of the mechanical tuning device of expression and the AM detection of having used synchronous rectification;

Figure 23 is the detailed pie graph of the circuit of synchronous rectification shown in expression Figure 22;

Figure 24 is the pie graph that expression utilizes the AM receiver of the mechanical tuning device shown in Figure 22;

Figure 25 is the forming circuit figure that expression comprises the phase-shift circuit of LR circuit;

Figure 26 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 25 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 27 is the circuit diagram of another kind of structure that expression comprises the phase-shift circuit of LR circuit;

Figure 28 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 27 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 29 is the circuit diagram of the 2nd variation of expression tuning circuit;

Figure 30 is the pie graph that expression comprises the phase-shift circuit of LR circuit;

Figure 31 is the circuit diagram of another structure that expression comprises the phase-shift circuit of LR circuit;

Figure 32 is the circuit diagram of the 4th variation of expression tuning circuit;

Figure 33 is the circuit diagram of the 5th variation of expression tuning circuit;

Figure 34 is the circuit diagram of the 6th variation of expression tuning circuit;

Figure 35 is the circuit diagram of the 7th variation of expression tuning circuit;

Figure 36 is the circuit diagram of the 8th variation of expression tuning circuit;

Figure 37 is that the circuit diagram in the formation of the prime phase-shift circuit shown in Figure 36 is extracted in expression out;

Figure 38 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 37 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 39 is that the circuit diagram in the formation of the back level phase-shift circuit shown in Figure 36 is extracted in expression out;

Figure 40 is the vectogram that is illustrated in the input and output of the phase-shift circuit shown in Figure 39 and comes across the relation between the voltage of electric capacity etc.;

Figure 41 is the pie graph that expression comprises the phase-shift circuit of LR circuit;

Figure 42 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 41 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 43 is the circuit diagram of another structure that expression comprises the phase-shift circuit of LR circuit;

Figure 44 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 43 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 45 is the circuit diagram of the 10th variation of expression tuning circuit;

Figure 46 is the circuit diagram of the 11st variation of expression tuning circuit;

Figure 47 is the circuit diagram of the 12nd variation of expression tuning circuit;

Figure 48 is that the circuit diagram in the formation of the prime phase-shift circuit shown in Figure 47 is extracted in expression out;

Figure 49 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 48 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 50 is that the circuit diagram in the formation of the back level phase-shift circuit shown in Figure 47 is extracted in expression out;

Figure 51 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 50 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 52 is the pie graph that expression comprises the phase-shift circuit of LR circuit;

Figure 53 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 52 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 54 is the circuit diagram of another structure that expression comprises the phase-shift circuit of LR circuit;

Figure 55 be illustrated in the input and output voltage of the phase-shift circuit shown in Figure 54 and the voltage that on capacitor etc., occurs between concern vectogram;

Figure 56 is the circuit diagram of the 14th variation of expression tuning circuit;

Figure 57 is the circuit diagram of the 15th variation of expression tuning circuit;

Figure 58 is the circuit diagram that is formed on the variable-resistance tuning circuit in the phase-shift circuit shown in Fig. 3 with the FET of MOS type;

Figure 59 makes to become the circuit diagram that the way that adopts the electrostatic capacitance that changes capacitor makes the tuning circuit of whole tuned frequencies variations;

Figure 60 is with the circuit diagram of the device except that FET as the variable-resistance tuning circuit in each phase-shift circuit shown in Fig. 2;

Figure 61 is a circuit diagram of having extracted the required part of phase-shift circuit work in the formation of operational amplifier out.

The most preferred embodiment that is used to carry out an invention

Below, the limit is with reference to accompanying drawing, and the limit specifies an embodiment of tuning control system of the present invention.

[integral body of A, tuned frequency constitutes and work]

Tuning control system of the present invention is characterized in that, be conceived to when same setting is included in each time constant of 2 phase-shift circuits in the tuning circuit, in each of 2 phase-shift circuits, phase difference between input/output signal is 90 °, be that amount of phase shift becomes 90 ° or 270 °, make the amount of phase shift of when importing the AC signal of an a certain frequency phase-shift circuit near 90 ° or 270 °, so that tuned frequency overlaps with the frequency of input signal by controlling.

Fig. 1 is the pie graph of mechanical tuning device of having used an embodiment of tuning circuit of the present invention.

Comprise as the tuning circuit 1 of the filter function by a certain frequency signal nearby with to the frequency control circuit 2 that centre frequency is controlled that passes through of this tuning circuit 1 with the mechanical tuning device that illustrates.

Tuning circuit 1 comprises 2 phase-shift circuits, the output of the output taking-up of the phase-shift circuit of back level as tuning circuit 1, feed back this signal by feedback resistance simultaneously, carry out add operation and be input in the prime phase-shift circuit to the input signal by input resistance input with by the feedback signal of feedback resistance feedback, in view of the above, become the tuning work that 360 ° frequency is stipulated with the amount of phase shift of 2 phase-shift circuit integral body.

And, the time constant of each phase-shift circuit is being set under the identical situation, the amount of phase shift in each phase-shift circuit becomes 90 °.If change a mode, the time constant of each phase-shift circuit is set at identical if control makes, the amount of phase shift of any phase-shift circuit is 90 ° simultaneously, and tuned frequency is overlapped with the frequency of input signal.

Also have, tuning circuit 1 by change the amount of phase shift of 2 phase-shift circuits according to the control signal from the outside input, just has the structure that can set tuned frequency in a certain scope arbitrarily.Narrate the detailed formation and the detailed operation of tuning circuit 1 below.

In 2 kinds of signals of input and output being input to the phase-shift circuit that tuning circuit 1 contains, the phase difference between these 2 signals departs from out under 90 ° the situation, and the tuned frequency of frequency control circuit 2 control tuning circuits 1 departs to eliminate this.

In order to carry out this control, the structure of frequency control circuit 2 is for comprising phase difference detecting circuit 3 and control voltage generating circuit 4.

Phase difference detecting circuit 3, duty ratio is 50% when the amount of phase shift of a phase-shift circuit that contains in the tuning circuit 1 is 90 °, when amount of phase shift departs from out 90 °, departs from corresponding to this, output duty cycle departs from 50% square-wave signal.

Control voltage generating circuit 4 takes place and duty ratio correspondent voltage from the square-wave signal of phase difference detecting circuit 3 outputs, and the voltage that the bias voltage to the voltage of this generation and regulation carries out after the add operation is exported to tuning circuit 1 as control signal.

Also have, will narrate phase difference detecting circuit 3 that constitutes said frequencies control circuit 2 and detailed formation and the work of controlling voltage generating circuit 4 below.[the detailed formation and the work of B, tuning circuit]

Below, describe the tuning circuit 1 that is shown in Fig. 1 in detail.Fig. 2 is the circuit diagram of the detailed structure of expression tuning circuit 1.The tuning circuit 1 that is shown in figure comprises: the phase shifts ormal weight of the AC signal by making input respectively under assigned frequency, amounts to phase-shift circuit 110c, the 130c of 360 ° amount of phase shift; The bleeder circuit 160 that constitutes by the resistance 162 and 164 of output one side of the phase-shift circuit 110c that is located at back level; Respectively by feedback resistance 170 and input resistance 174 (input resistance 174 is assumed to be the resistance of the n resistance value doubly of the resistance value with feedback resistance 170), with the ratio of regulation to the dividing potential drop output (feedback signal) of bleeder circuit 160 be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

Fig. 3 is a pie graph of representing to extract out the prime phase-shift circuit 110c that is shown in Fig. 2.The prime phase-shift circuit 110c that is shown in figure comprises: this is as a kind of operational amplifier 112 of differential amplifier; Make the variable resistor 116 and the electric capacity 114 that are input to non-inverting input of operational amplifier 112 behind the phase shifts ormal weight of the AC signal that is input to input 122; Be inserted into the resistance 118 between the reversed input terminal of input 122 and operational amplifier 112; The output that is connected in operational amplifier 112 constitutes the resistance 121 and 123 of bleeder circuit; And be connected in resistance 120 between the reversed input terminal of the lead-out terminal of this bleeder circuit and operational amplifier 112.

In having the phase-shift circuit 110c of this structure, the resistance value of resistance 118 and resistance 120 is set at identical value.And, variable resistor 116 can change resistance value according to the control voltage that comes from the outside, for example, and as shown in Figure 3,, adopt by control input end 194 that is shown in figure and set resistance value as resistive element with the raceway groove of FET from the outside the way that the control voltage of being supplied with is added on the grid.

If the AC signal of regulation is input on the input 122 that is shown in Fig. 3, will adds the voltage VR1 that comes across variable resistor 116 two ends at non-inverting input of operational amplifier 112.And, the voltage VC1 identical with the voltage VC1 at electric capacity 114 two ends occur at resistance 118 two ends, identical electric current I flows to 2 resistance 118 and 120, and as described above, because the resistance value of each resistance 118 and 120 equates, so voltage VC1 also occurs at the two ends of resistance 120.If the reversed input terminal of operational amplifier 112 (voltage VR1) is regarded as benchmark, the voltage VC1 at resistance 118 two ends is carried out addition of vectors just become input voltage Ei, the voltage VC1 at resistance 120 two ends is carried out the branch pressure voltage that vector subtracts each other just to be become on resistance 121 and 123 tie points (dividing potential drop output) E0 '.

Fig. 4 is the vectogram that concerns between the input and output voltage of expression prime phase-shift circuit 110c and the voltage that comes across capacitor etc.

As mentioned above, if the voltage VR1 that is added on non-inverting input of operational amplifier 112 is regarded as benchmark, then as can be known: input voltage Ei and branch pressure voltage E0 ' are only different with the direction of resultant voltage VC1 and its absolute value equates.Therefore, the size of input voltage Ei and branch pressure voltage E0 ' and the relation of phase place, can with input voltage Ei and branch pressure voltage E0 ' as hypotenuse, 2 times of isosceles triangles as the base of voltage VC1 are represented, the amplitude with input signal is identical with frequency-independent for the amplitude of branch pressure voltage E0 ', φ 1 expression of amount of phase shift to be shown in Fig. 4.This amount of phase shift φ 1 according to frequency, as benchmark, changes to 360 ° in the direction of rotation (phase delay direction) of hour hands from 180 ° with input voltage Ei.

And, the output 124 of phase-shift circuit 110c is owing to be connected with the lead-out terminal of operational amplifier 112, the resistance value of supposing resistance 121 is R21, the resistance value of resistance 123 is R23, then between output voltage E0 and above-mentioned branch pressure voltage E0 ', resistance value R21 and R23 for resistance 120 is enough hour relatively, exists the relation of E0=(1+R21/R23) E0 '.Therefore, can obtain than 1 big gain by means of the value of adjusting R21 and R23, and even as shown in Figure 4, frequency changes, the amplitude of output voltage E0 is also constant, can only make the phase shifts ormal weight.

Equally, Fig. 5 is the pie graph that the back level phase-shift circuit 130c that is shown in Fig. 2 is extracted in expression out.The back level phase-shift circuit 130c that is shown in figure comprises: this is as a kind of operational amplifier 132 of differential amplifier; Make the phase shifts ormal weight of the signal that is input to input 142 then be input to the capacitor 134 and the variable resistor 136 of non-inverting input of operational amplifier 132; The resistance 138 that between the reversed input terminal of input 142 and operational amplifier 132, inserts; The lead-out terminal that is connected in operational amplifier 132 constitutes the resistance 141 and 143 of bleeder circuit; And be connected in resistance 140 between the reversed input terminal of the lead-out terminal of this bleeder circuit and operational amplifier 132.

In having the phase-shift circuit 130c of such formation, resistance 138 and resistance 140 are set at same resistance value.And variable resistor 136 can be according to the control voltage change resistance value of coming from the outside, and the control input end 195 through being shown in Fig. 2 is added to grid to the control voltage of supplying with from the outside and sets resistance value.

AC signal as in the input 142 input regulations that are shown in Fig. 5 then on non-inverting input of operational amplifier 132, applies the voltage VC2 at capacitor 134 two ends.And, at the two ends of resistance 138, the voltage VR2 identical with the voltage VR2 at variable resistor 136 two ends appears.Same current I flows to 2 resistance 138 and 140, and, as mentioned above because the resistance value of each resistance 138 and resistance 140 is equal, so voltage VR2 also occurs at the two ends of resistance 140.If the reversed input terminal of operational amplifier 132 (voltage VC2) is regarded as benchmark, then the voltage VR2 at resistance 138 two ends is carried out addition of vectors and just become input voltage Ei, the voltage VR2 at resistance 140 two ends is carried out the branch pressure voltage that vector subtracts each other just to be become on resistance 41 and 43 tie points (dividing potential drop output) E0 '.

Fig. 6 is the vectogram that concerns between the input and output voltage of expression back level phase-shift circuit 130c and the voltage that comes across capacitor etc.

As mentioned above, if the voltage VC2 that is added on non-inverting input of operational amplifier 132 is regarded as benchmark, then as can be known: input voltage Ei and branch pressure voltage E0 ' are only different with the direction of resultant voltage VR2 and its absolute value equates.Therefore, the size of input voltage Ei and branch pressure voltage E0 ' and the relation of phase place, can with input voltage Ei and branch pressure voltage E0 ' as hypotenuse, 2 times of isosceles triangles as the base of voltage VR2 are represented, the amplitude with input signal is identical with frequency-independent for the amplitude of branch pressure voltage E0 ', φ 2 expressions of amount of phase shift to be shown in Fig. 6.This amount of phase shift φ 2 according to frequency, as benchmark, changes to 180 ° in the direction of rotation of hour hands from 0 ° with input voltage Ei.

And, the output 144 of phase-shift circuit 130c is owing to be connected with the lead-out terminal of operational amplifier 132, the resistance value of supposing resistance 141 is R41, the moon value of resistance 143 is R43, then between output voltage E0 and above-mentioned branch pressure voltage E0 ', when resistance value R41 and R43 for resistance 140 are enough hour, exist the relation of E0=(1+R41/R43) E0 '.Therefore, can obtain than 1 big gain by means of the value of adjusting R41 and R43, and even as shown in Figure 6, frequency changes, the amplitude of output voltage E0 is also constant, only the phase place of mobile ormal weight.

So, in each of 2 phase-shift circuit 110c, 130c, phase place is moved ormal weight, and as Fig. 4 and shown in Figure 6, tuning circuit 1 whole amount of phase shift just becomes 360 ° in the frequency of regulation.

And, the output of back level phase-shift circuit 130c, as shown in Figure 2, from the output that lead-out terminal 192 takes out tuning circuit 1, through feedback resistance 170 output of this phase-shift circuit 130c is fed back to the input side of the phase-shift circuit 110c of prime simultaneously by the signal of bleeder circuit 160.And, carry out addition to this feedback signal with through the signal of input resistance 174 input, the signal after the addition is input among the phase-shift circuit 110c of prime.

As mentioned above, by means of 2 phase-shift circuit 110c, 130c, total amount of phase shift in the assigned frequency is 360 °, at this moment, by being the loop gain setting of the feedback control loop that produces by 2 phase-shift circuit 110c, 130c, bleeder circuit 160 and feedback resistance 170 below 1, the tuning work that the signal of afore mentioned rules frequency content is passed through.

And, because the output of taking out the prime phase-shift circuit 130c that is input to bleeder circuit 160 from the lead-out terminal 192 of tuning circuit 1, thus can in tuning circuit 1 self, keep gain, can with tuning work while amplifying signal amplitude.

Fig. 7 is the circuit diagram that 2 phase-shift circuit 110c, 130c with above-mentioned formation and bleeder circuit 160 all is replaced as the circuit with transfer function K1, have with transfer function K1 parallel resistor R0 be feedback resistance 170, the input resistance 174 of the n times of resistance value (nR0) of being connected in series with feedback resistance 170.

Fig. 8 is the circuit diagram that circuit that is shown in Fig. 7 has been carried out conversion according to MILLER'S THEOREM, and the transfer function A of the whole system after the conversion can be expressed as:

A＝V0/Vi＝K1/{n(1-K1)+1} …(1)

The transfer function K2 of the phase-shift circuit 110c of prime is assumed to be T to the time constant of the RC circuit that is made of variable resistor 116 and electric capacity 114 ₁(resistance value of variable resistor 116 is assumed to be R, and the electrostatic capacitance of electric capacity 114 is assumed to be C and T ₁=RC), then become:

K2=-a (1-T ₁S)/(1+T ₁S) ... (2) wherein, S=j ω, a ₁Be the gain of phase-shift circuit 110c, and a ₁=(1+R21/R23)＞1.

And the transfer function K3 of the phase-shift circuit 130c of back level is assumed to be T to the time constant of the RC circuit that is made of electric capacity 134 and resistance 136 ₂(electrostatic capacitance of electric capacity 134 is assumed to be C, and the resistance value of variable resistor 136 is assumed to be R, and T ₂=RC), then become:

K3=a ₂(1-T ₂S)/(1+T ₂S) ... (3) wherein, a ₂Be the gain of phase-shift circuit 130c, and a ₂=(1+R41/R43)＞1.

By means of by bleeder circuit 160, establish if signal amplitude decays to 1/a ₁a ₂Amplitude, then the whole transfer function K1 when cascade 2 phase-shift circuit 110c, 130c and bleeder circuit 160 is:

K1=-{1+ (Ts) ²-2Ts}/{ 1+ (Ts) ²+ 2Ts} ... (4) to also have, in above-mentioned (4) formula, to calculate simply in order making, so the time constant T of each phase-shift circuit ₁, T ₂Be set at common T.Above-mentioned (1) formula of this (4) formula substitution, can obtain:

A＝-{1+(Ts) ²-2Ts}/[(2n+1){1+(Ts)2}+ ²Ts]

＝-{1/(2n+1)}[{1+(Ts) ²-2Ts}

/{1+(Ts) ²+2Ts/(2n+1)}] …(5)

According to above-mentioned (5) formula, when ω=0 (DC area), then can know to become A=-1/ (2n+1), and give the maximum attenuation amount.And, when ω=∞, then can know to become A=-1/ (2n+1), and give the maximum attenuation amount.Moreover, as can be known in the tuning point of ω=1/T, A=1 and irrelevant with the impedance ratio n of feedback resistance 170 and input resistance 174.In other words, as shown in Figure 9, no matter how the n value changes, and also can not depart from tuning point, and the attenuation of tuning point does not change yet.

And, by each resistance value of the variable resistor 116 in the change prime phase-shift circuit 110c with the variable resistor 136 that is contained in back level phase-shift circuit 130c, the time constant of each the RC circuit that is contained in phase-shift circuit 110c, 130c is changed, can in certain scope, change tuned frequency ω arbitrarily.

Although, in above-mentioned Fig. 7, have at all pass circuit of representing with transfer function K1 under the situation of input impedance, owing to forming feedback resistance 170 and, becoming also littler than the absolute value of transfer function K1 so contain the loop gain of the feedback control loop of all pass circuit by the bleeder circuit that the input impedance of this all pass circuit produces.The input impedance of so-called all pass circuit is exactly the input impedance of prime phase-shift circuit 110c, is to be parallel-connected on the input resistance 118 of operational amplifier 112 and the input impedance that forms by the RC circuit series impedance that variable resistor 116 and electric capacity 114 constitute.Therefore, in order to compensate the loop gain loss of the feedback control loop that produces because of all pass circuit input impedance, so need be the gain setting of all pass circuit self more than 1.

For example, (voltage ratio is under 1 the situation, a in above-mentioned (2) if ignore the resistance 121 that contains and 123 bleeder circuits that constitute in phase-shift circuit 110c ₁Regard as under 1 the situation), according to (2) formula, be that 1 times follower circuit must carry out work in the scope of the inverting amplifier of gain conduct-1 times from gain according to incoming frequency, be unfavorable in addition so the resistance ratio of resistance 118 and 120 is made 1.Because, if the resistance value separately of resistance 118,120 is made as R18, R20, gain when then phase-shift circuit 110c is as anti-phase amplification work is-R20/R18, but the resistance ratio of tube resistor 118 and resistance 120 is not how, gain when working often 1 as follower, thus not under 1 the situation at the resistance ratio of resistance 118 and resistance 120, in phase-shift circuit 110c work region-wide, be impossible satisfy the phase place that only changes between its input and output, and the constant ideal conditions of output amplitude.

By the bleeder circuit that is made of resistance 121 and 123 is appended on the outlet side of phase-shift circuit 110c, apply feedback through this bleeder circuit to the inverting input of operational amplifier 112, it is 1 constant and be the gain setting of phase-shift circuit 110c more than 1 that the resistance ratio of resistance 118 and resistance 120 is remained.Equally, by the bleeder circuit that is made of resistance 141 and 143 is appended on the outlet side of phase-shift circuit 130c, apply feedback through this bleeder circuit to the inverting input of operational amplifier 132, it is 1 constant and be the gain setting of phase-shift circuit 130c more than 1 that the resistance ratio of resistance 138 and resistance 140 is remained.

Also have, if obtain φ 1 (is that benchmark is 1≤360 ° of 180 °≤φ of hour hands direction of rotation (phase delay direction) with input voltage Ei) and the φ 2 (is that benchmark is 2≤180 ° of 0 °≤φ of hour hands direction of rotation with input voltage Ei) that is shown in Fig. 4 and Fig. 6 according to (2) formula or (3) formula, then can get:

φ1＝tan{2ωT ₁/(1-ω ²T ₁ ²)} …(6)

φ2＝tan{2ωT ₂/(1-ω ²T ₂ ²)} …(7)

At T ₁=T ₂Under the situation of (=T), during ω=1/T, the total amount of phase shift of 2 phase-shift circuit 110c, 130c is 360 °, carries out above-mentioned tuning work, at this moment becomes φ 1=270 °, φ 2=90 °.

Figure 10 is the phase diagram between the signal of representing among input and output to 2 phase-shift circuit 110c, the 130c, shows the situation that the signal frequency among the prime phase-shift circuit 110c equates with tuned frequency that is input to.

The output signal S2 of the phase-shift circuit 110c of prime shown in Figure 10 (A), is a benchmark with output signal S1, carries out φ 1=270 ° phase-shifts in the hour hands direction of rotation.And the output signal S2 of the phase-shift circuit 130c of back level shown in Figure 10 (B), is a benchmark with output signal S2, carries out φ 2=90 ° phase-shifts in the hour hands direction of rotation.Therefore, as cascade 2 phase-shift circuit 110c, 130c, then shown in Figure 10 (C), carry out 360 ° of phase-shifts as a whole.

Yet, the tuned frequency of setting than the also high situation of the signal frequency among the phase-shift circuit 110c that is input to prime under, the result of above-mentioned φ 1 and φ 2 merging is less than 360 °.

Figure 11 is that the expression tuned frequency is than the phase diagram between the input and output of each phase-shift circuit under the high situation of the signal frequency among the phase-shift circuit 110c that is input to prime.

So-called tuned frequency is exactly the signal frequency situation relatively lower than tuned frequency of input than the high situation of signal frequency among the phase-shift circuit 110c that is input to prime.Under these circumstances, from Fig. 4 and Fig. 6 as can be known, 1 to 270 ° of the amount of phase shift φ of the phase-shift circuit 110c of prime is little, and 2 to 90 ° of the amount of phase shift φ of the phase-shift circuit 130c of back level are little.Therefore, φ 1 and φ 2 respectively shown in Figure 11 (A), Figure 11 (B), the total amount of phase shift when cascade 2 phase-shift circuit 110c, 130c, shown in Figure 11 (C), littler than 360 °.

; under these circumstances, in order to make the signal frequency of tuned frequency, above-mentioned φ 1 and φ 2 are increased near actual input; specifically, the both end voltage VR1 of the variable resistor 116 that is shown in Fig. 2 and the both end voltage VR2 of variable resistor 136 are increased.For example, form under the situation of variable resistor 116 or 136, can reduce grid voltage and increase channel resistance at FET with the n channel-type.

On the other hand, tuned frequency than the low situation of the signal frequency among the phase-shift circuit 110c that is input to prime under, the result that above-mentioned φ 1 and φ 2 merges is also less than 360 °.

Figure 12 is that the expression tuned frequency is than the phase diagram between the input and output of each phase-shift circuit under the low situation of the signal frequency among the phase-shift circuit 110c that is input to prime.

So-called tuned frequency is exactly the signal frequency situation relatively higher than tuned frequency of input than the low situation of signal frequency among the phase-shift circuit 110c that is input to prime.Under these circumstances, from Fig. 4 and Fig. 6 as can be known, 1 to 270 ° of the amount of phase shift φ of the phase-shift circuit 110c of prime is big, and 2 to 90 ° of the amount of phase shift φ of the phase-shift circuit 130c of back level greatly.Therefore, φ 1 and φ 2 respectively shown in Figure 12 (A), Figure 12 (B) like that, the total amount of phase shift when cascade 2 phase-shift circuit 110c, 130c, shown in Figure 12 (C), bigger than 360 °.

; under these circumstances, in order to make the signal frequency of tuned frequency, the absolute value of above-mentioned φ 1 and φ 2 is dwindled near actual input; specifically, the both end voltage VR1 of the variable resistor 116 that is shown in Fig. 2 and the both end voltage VR2 of variable resistor 136 are reduced.For example, under the situation of the variable resistor 116 that forms with the FET of n channel-type or 136, the grid voltage that can raise reduces channel resistance.

As above-mentioned illustrated, because in above-mentioned tuning circuit 1, the resistance value of resistance in the phase-shift circuit 110c 118 and resistance 120 is set at identical value, simultaneously the resistance 138 in the phase-shift circuit 130c and the resistance value of resistance 140 are set at identical value, so the amplitude in the time of can preventing to change tuned frequency changes, thereby obtain having the amplitude of constant.

Particularly, by suppressing the amplitude change of tuning output, can make above-mentioned resistance ratio n increase and the Q value of tuning circuit 1 is increased.That is, if loop gain is existed frequency dependence, even then increase resistance ratio in the low frequency of gain, Q does not raise yet, and just vibrates and surpass 1 in the high frequency loop gain of gain.Therefore, under the big situation of amplitude change, take place in order to prevent such vibration, so can not be set in resistance ratio n on the excessive value, the Q value of tuning circuit 1 also diminishes.On the other hand, according to the tuning circuit shown in Fig. 21, even resistance ratio is set greatlyyer, because the amplitude change does not take place in the tuning output of tuning circuit 1, so can increase resistance ratio and increase the Q value.

And, by using as feedback signal through the signal of bleeder circuit 160 decay, to be input to bleeder circuit 160 preceding signals simultaneously takes out as the output of tuning circuit 1, can carry out from input signal only extracting out institute and decide the tuning work of frequency content, the amplification that the while can stipulate the signal of this extraction.

Also have, in above-mentioned tuning circuit shown in Figure 21, can save any bleeder circuit among the bleeder circuit on the output of the operational amplifier 112 that is connected in each phase-shift circuit that contains tuning circuit 1 or 132, or voltage ratio is set at 1.For example, save the bleeder circuit in the phase-shift circuit 110c and direct the connection also with an end of resistance 120 of the lead-out terminal of operational amplifier 112 be fine.

Like this, be gain setting 1 if of 2 phase-shift circuits of cascade is saved bleeder circuit, then by being than 1 big value, carry out and be shown in the same tuning work of tuning circuit 1 of Fig. 2 to the gain setting of the opposing party's phase-shift circuit 110c.

And, do not needing to amplify under the situation of work, can save the back level bleeder circuit 160 of phase-shift circuit 130c, the output of phase-shift circuit 130c is directly fed back to prime one side.Perhaps, also can be to make the resistance value of the resistance 162 in the bleeder circuit 160 be set at 1 for extremely little value and voltage ratio.[the detailed formation and the work of C, frequency control circuit]

Below, describe the frequency control circuit 2 that is shown in Fig. 1 in detail.Figure 13 is the circuit diagram of the formation of expression frequency control circuit 2, the figure shows phase difference detecting circuit 3 that is included in the frequency control circuit 2 and the detailed structure of controlling voltage generating circuit 4.

The phase difference detecting circuit 3 that is shown in Figure 13 comprises: 30,2 voltage comparators 31,32 such as the buffer of source follower etc. and EX-OR (distance) door 33.

2 voltage comparators 31 and 32 inverting input common ground, through buffer 30, the signal of exporting from control output end 196 of tuning circuit 1 (input signal of the phase-shift circuit 130c of back level) is input to the non-inverting input of a voltage comparator 31, and the signal of exporting from control output end 197 of tuning circuit 1 (output signal of the phase-shift circuit 130c of back level) is input to the non-inverting input of another voltage comparator 32.

According to the signal voltage level that is input to non-inverting input is than 0V height or low, each voltage comparator 31 and 32 outputs have positive and negative the two one of the square-wave signal of voltage level.That is, voltage comparator 31,32 output respectively with from the signal same frequency of control output end 196,197 outputs of tuning circuit 1 and the square-wave signal of phase place.

The square-wave signal of exporting respectively from each voltage comparator 31 and 32 as input, make each square-wave signal have the voltage level of positive polarity corresponding to logic H, the voltage level of negative polarity is obtained the distance of these 2 inputs corresponding to logic L by EX-OR door 33.

Therefore, for example, be under 90 ° the situation at phase difference from 2 signals of 2 control output end 196,197 output of tuning circuit 1, the phase difference of the square-wave signal of exporting respectively from voltage comparator 31 and 32 is 90 °, the frequency that then has 2 times of these square-wave signals from 33 outputs of EX-OR door, and duty ratio is 50% square-wave signal.

The control voltage generating circuit 4 that is shown in Figure 13 has: the low pass filter that is made of resistance 40 and electric capacity 41, the variable resistor 42 that the regulation bias voltage takes place, and the amplifier that is made of operational amplifier 44, resistance 45 and resistance 46.

Low pass filter according to the time constant by resistance 40 and electric capacity 41 decisions, is removed radio-frequency component from the square-wave signal of EX-OR door 33 outputs.Therefore, from the duty ratio of the square-wave signal of EX-OR door 33 output than 50% also big situation under (situation that the relative scale of high level is big), the output voltage of low pass filter slowly rises, on the contrary, from the duty ratio of the square-wave signal of EX-OR door 33 output than 50% little situation under, the output voltage of low pass filter slowly descends.Also having, is to be inserted into before the amplifier though be shown in the low pass filter of Figure 13, also can adopt the be connected in parallel way and the amplifier of capacitor etc. of feedback resistance with amplifier integrally formed.

Between the lead-out terminal of operational amplifier 44 and reversed input terminal, be connected with resistance 45, and make reversed input terminal ground connection through resistance 46.By means of such connected mode, operational amplifier 44 conducts have the function corresponding to the amplifier of the multiplication factor of the resistance ratio of resistance 45,46.The voltage that has amplified in operational amplifier 44 as described below, after the bias voltage with regulation carries out add operation generation control voltage, is input in the tuning circuit 1 and goes.

On the reversed input terminal of operational amplifier 44, connect the movable terminal that 2 fixed terminals has been connected in the variable resistor 42 on positive supply Vdd and the negative supply Vss through resistance 43.Thereby the biasing circuit that constitutes by means of comprising variable resistor 42 is set on the bias voltage of regulation the output end voltage of operational amplifier 44.Also have, in fact forming under the situation of this variable resistor 42 on the Semiconductor substrate, can utilize the active device of FET etc. to form variable resistor.

When the tuned frequency of tuning circuit 1 overlaps with the frequency of input signal (, when not having error), owing to set the voltage that should add on the grid separately of the variable resistor 136 that contains on the variable resistor 116 that in a phase-shift circuit 110c of tuning circuit 1, contains and another phase-shift circuit 130c, so be provided with this biasing circuit.

Also have, using FET to constitute under the situation of variable resistor 116 and 136, even be added on each FET, if the resistance value difference then appears in the differences such as source potential of each FET sometimes with same gate voltage.Therefore, under the situation of practical combinations circuit, it is desirable to make it mutual interlock, the distributor 5 that 2 kinds of variable grid voltages take place is connected between control voltage generating circuit 4 and the tuning circuit 1 according to the output voltage of control voltage generating circuit 4.Perhaps, when adding same grid voltage, can selecting FET, to make that resistance value becomes equal, carries out such selecting and just can save the distributor 5 that is shown in Figure 13.

The frequency control circuit 2 of present embodiment has so detailed formation, below the branch situation its detailed operation is described.[C-1, the situation that tuned frequency is higher than frequency input signal]

Figure 14 is that the tuned frequency of tuning circuit 1 is compared the sequential chart of high situation with the signal frequency in being input to tuning circuit 1, and shows each the input and output sequential chart that constitutes in the frequency control circuit 2.With scheming (A)～(F) corresponding to the label A～F shown in the circuit diagram of Figure 13.

Tuned frequency than the high situation of the frequency input signal of tuning circuit 1 under, as shown in figure 11, because the amount of phase shift φ 2 of the phase-shift circuit 130c of back level is less than 90 °, so, have the control output that is shown in Figure 14 (A) respectively and 1. export 2. such phase relation with the control that is shown in Figure 14 (B) from 2 signals that 2 control output end 196,197 of tuning circuit 1 are exported.

The voltage comparator 31 of a side in the phase difference detecting circuit 3, when above-mentioned control output voltage level 1. is higher than 0V, the signal of output H level.Thereby, shown in Figure 14 (C), have with control from voltage comparator 31 output and to export the 1. signal of same frequency and phase place, promptly, control output voltage level 1. becomes the H level when positive polarity, and control output voltage level 1. is the square-wave signal of L level when negative polarity on the contrary.

Equally, another voltage comparator 32 in the phase difference detecting circuit 3, when above-mentioned control output voltage level 2. is higher than 0V, the signal of output H level.Thereby, shown in Figure 14 (D), have with control from voltage comparator 32 output and to export the 2. signal of same frequency and phase place, promptly, control output voltage level 2. is the H level when positive polarity, and control output voltage level 2. is the square-wave signal of L level when negative polarity on the contrary.

When each output logics of 2 voltage comparators 31,32 square-wave signal of the H level of EX-OR door 33 outputs becoming simultaneously not, then become the square-wave signal of L level when each output logic is identical.When tuned frequency is higher than the frequency input signal of tuning circuit 1, because 2 to 90 ° of the amount of phase shift φ of the phase-shift circuit 130c of back level are little, so shown in Figure 14 (E), output duty cycle is less than 50% square-wave signal.

From the square-wave signal of these EX-OR door 33 outputs, the low pass filter through being made of resistance 40 in the control voltage generating circuit 4 and capacitor 41 is input in the non-inverting input of operational amplifier 44.This low pass filter is in order to remove radio-frequency component and to use from the square-wave signal of input, the duty ratio of the square-wave signal of this input less than 50% situation under, shown in Figure 14 (F), the output voltage of low pass filter becomes and is lower than 0V.

By means of by the amplifier that comprises that operational amplifier 44 constitutes, amplify the output voltage of this low pass filter with the multiplication factor of regulation, and then the bias voltage with the regulation of variable resistor 42 settings is carried out add operation.And, be added on the distributor 5 by the voltage that addition is calculated, and produce each control voltage on control input end 194,195 be added to tuning circuit 1.Therefore, from the duty ratio of the square-wave signal of EX-OR door 33 output less than 50% o'clock, these control voltages will be to little variation.

Like this,, made the tuned frequency step-down of tuning circuit 1 to the control voltage reduction of tuning circuit 1 feedback.Repeat this control till the deviation of the output signal frequency of tuning circuit 1 and tuned frequency is eliminated, just overlap with output signal frequency through tuned frequency after the stipulated time.[C-2, the situation that tuned frequency is lower than frequency input signal]

Figure 15 is that the tuned frequency of tuning circuit 1 is compared the sequential chart of low situation with the signal frequency in being input to tuning circuit 1, and shows each the input and output sequential chart that constitutes in the frequency control circuit 2.Identical with Figure 14, Figure 15 (A)～(F) is corresponding to the label A～F shown in the circuit diagram of Figure 13.

Tuned frequency than the low situation of the frequency input signal of tuning circuit 1 under, as shown in figure 12, because the amount of phase shift φ 2 of the phase-shift circuit 130c of back level becomes greater than 90 °, so, just become the 2. such phase relation of control output that Figure 15 (B) was exported and be shown in to the control that is shown in Figure 15 (A) 1. if observe from 2 signals of 2 control output end, 196,197 outputs of tuning circuit 1.

As mentioned above, the voltage comparator 31 in the phase difference detecting circuit 3, when control output voltage level 1. was higher than 0V, output became the square-wave signal (Figure 15 (C)) of H level; Voltage comparator 32, when control output voltage level 2. was higher than 0V, output became the square-wave signal (Figure 15 (D)) of H level.

And, when each output logic of these 2 voltage comparators 31,32 not simultaneously, the square-wave signal of EX-OR door 33 outputs becoming H level is then exported the square-wave signal that becomes the L level when identical.Thereby, when tuned frequency is lower than the frequency input signal of tuning circuit 1, because the amount of phase shift φ 2 of the phase-shift circuit 130c of back level becomes greater than 90 °, so shown in Figure 15 (E), the duty ratio of the square-wave signal that EX-OR door 33 is exported becomes greater than 50%.

Therefore, the output voltage of the low pass filter in the control voltage generating circuit 4 becomes shown in Figure 15 (F) and is higher than 0V, also changes to high direction to the control voltage that tuning circuit 1 applies from control voltage generating circuit 4 through distributor 5 thereupon.

Like this,, the tuned frequency of tuning circuit 1 is changed to high direction to the control voltage rising of tuning circuit 1 feedback.Repeat this control till the deviation of the output signal frequency of tuning circuit 1 and tuned frequency is eliminated, just overlap with output signal frequency through tuned frequency after the stipulated time.

Like this, mechanical tuning device according to present embodiment, become 90 ° in order to control the phase difference that makes between the input/output signal of a phase-shift circuit 130c of tuning circuit 1, thus always follow frequency input signal during tuned frequency and change, and both frequencies must overlap.Therefore, be applied to, for example under the situation of superheterodyne receiver, the carrier frequency of tuned frequency and input transmitted wave etc. overlapped at mechanical tuning device present embodiment.

And, tuning circuit 1 and frequency control circuit 2 that the mechanical tuning device inside of present embodiment is comprised, constitute by voltage comparator and gate circuit or operational amplifier, capacitor, resistance etc., because any device all can be formed on the Semiconductor substrate, so can or comprise mechanical tuning device and peripheral circuit integral body is integrated on the Semiconductor substrate whole mechanical tuning device.

Particularly, integrated under the situation of whole mechanical tuning device, though consider in each chip of making take place on the circuit constant big discrete and frequency characteristic is not overlapped, even but under such situation, mechanical tuning device according to present embodiment, because the tuned frequency of tuning circuit 1 is changed in the mode of following input signal with assigned frequency, do not influence actual tuning characteristic so the circuit devcie characteristic is discrete, always can obtain stable tuning characteristic.

And, integrated under the situation of whole mechanical tuning device, though the variations in temperature when considering with use makes various device constants variations such as resistance, but because control with the tuning control system of present embodiment, always overlap with the frequency of input signal, even so under the situation that various device constants have changed, add the appropriateness feedback, misfitting also between the frequency of input signal and the tuned frequency has been eliminated.[another example of D, frequency control circuit]

Below, another example of the frequency control circuit 2 that is shown in Fig. 1 is described.Though the phase difference detecting circuit 3 that has shown in detail in Figure 13 in the frequency control circuit 2 of formation uses EX-OR doors 33 to realize, also can constitute with device in addition.

Figure 16 is the detailed circuit diagram of another configuration example of expression frequency control circuit, and this figure has the structure that the phase difference detecting circuit 3 that is shown in Figure 13 is replaced as phase difference detecting circuit 3A.

The phase difference detecting circuit 3A that is shown in Figure 16 comprises: 30,2 voltage comparators 31 of buffer and 32 and the translation buffer 34 of controlling various work according to the output of voltage comparator 31.The EX-OR doors 33 that this phase difference detecting circuit 3A has in the phase difference detecting circuit that is shown in Figure 13 3 are replaced as translation buffer 34, simultaneously 2 structures that the input terminals transposing connects of voltage comparator 32.Also having, also can be that this translation buffer 34 is replaced as analog switch.

Figure 17 be be input to the tuning circuit 1 that is shown in Figure 16 in signal frequency compare, sequential chart under the higher situation of tuned frequency, this figure show the input and output sequential in the phase difference detecting circuit 3A that constitutes frequency control circuit and each formation of controlling voltage generating circuit 4 respectively.Figure 17 (A)～(F) is corresponding to the label A～F that has illustrated among Figure 16.

Also have, the sequential that is shown in Figure 17 (A)～(C) is identical with the various sequential that are shown in Figure 14 (A)～(C), and below explanation mainly is conceived to the work of translation buffer 34.

As mentioned above, the output signal of a voltage comparator 31 is input to the control terminal of translation buffer 34, according to the voltage level of this control terminal, translation buffer 34 by or cut off the output of voltage comparator 32.For example, when the output signal of voltage comparator 31 is the H level, allows and intactly pass through, otherwise when voltage comparator 31 is output as the L level, then become high impedance status from the signal of another voltage comparator 32 outputs.

But, tuned frequency than the high situation of the frequency input signal of tuning circuit 1 under, translation buffer 34 can be used as buffer and carries out work, promptly, when one voltage comparator 31 is output as the H level, the output of another voltage comparator 32, long during the L level than during the H level.

Therefore, shown in Figure 17 (E), when the output of a voltage comparator 31 is in the L level, become and be 0V, when the output of voltage comparator 31 is in the H level, then be output as the signal of L level or H level from the output of translation buffer 34.

Like this, under the tuned frequency situation higher than frequency input signal, because the output of translation buffer 34 is long during the L level than during the H level, so output voltage of the low pass filter that constitutes by resistance 40 in the control voltage generating circuit 4 and capacitor 41, shown in Figure 17 (F), become and be lower than 0V, the control voltage that thereupon feeds back in the tuning circuit 1 also changes to the direction that reduces.

Also have, the output of translation buffer 34 is because the half period among 1 cycle necessarily becomes 0V, so compare with the situation of using EX-OR door 33 as shown in figure 13, detection sensitivity is low, and the response speed of control is slack-off.

Figure 18 be be input to the tuning circuit 1 that is shown in Figure 16 in signal frequency compare, each input and output sequential in constituting that sequential chart under the low situation of tuned frequency, this figure show the phase difference detecting circuit 3A that constitutes frequency control circuit and control voltage generating circuit 4 respectively.Figure 18 (A)～(F) is corresponding to the label A～F that has illustrated among Figure 16.

Tuned frequency than the low situation of the frequency input signal of tuning circuit 1 under, the output level of the translation buffer 34 when voltage comparator 31 is output as the H level is different with above-mentioned situation.That is, when voltage comparator 31 is output as the H level, the output of translation buffer 34, long during the H level than during the L level.Also have, when voltage comparator 31 was output as the L level, the output of translation buffer 34 is constant to be 0V.

Like this, under the tuned frequency situation lower than frequency input signal, because the output of translation buffer 34 is long during the H level than during the L level, so output voltage of the low pass filter that constitutes by resistance 40 in the control voltage generating circuit 4 and capacitor 41, shown in Figure 18 (F), become and be higher than 0V, the control voltage that thereupon feeds back in the tuning circuit 1 also changes toward high direction.

Like this, tuned frequency than the high situation of the frequency input signal of tuning circuit 1 under, the control voltage step-down of feedback, tuned frequency is changed to low direction, on the contrary under tuned frequency is low situation, because the control voltage of feedback uprises, tuned frequency is also changed toward high direction, also overlap with it so control the frequency that always makes tuned frequency follow input signal.[E, the example when being applied to the FM receiver]

Below, the situation that the mechanical tuning device of above-mentioned present embodiment is applied to the FM receiver is described.Under the situation that the frequency input signal of tuning circuit 1 changes, the frequency control circuit 2 that is shown in Fig. 1 is followed this frequency change and is made the control change in voltage that feeds back in the tuning circuit 1.Therefore, should control voltage on the principle, in the frequency change of the FM ripple being regarded as the input signal of tuning circuit 1, promptly under the situation as input signal, comprising the modulation signal same frequency composition with this FM ripple, present embodiment has just been got this frequency content come out as the FM rectified signal.

Figure 19 is a pie graph of representing to have concurrently the mechanical tuning device of FM detection.Be shown in the formation of this figure, the frequency control circuit 2 interior control voltage generating circuits 4 that are shown in Fig. 1 are replaced as control voltage generating circuit 4A, and with parallel from this control voltage generating circuit 4A taking-up FM rectified signal to the control voltage of tuning circuit 1 feedback.

Figure 20 is the circuit diagram of the detailed structure of expression frequency control circuit 2 shown in Figure 19.The detailed formation of the phase difference detecting circuit 3 of formation frequency control circuit 2 is identical with the formation that is shown in Figure 13, and the formation of control voltage generating circuit 4A has some different with the control voltage generating circuit 4 that is shown in Figure 13.

Control voltage generating circuit 4A, comprise the low pass filter that constitutes by resistance 40 and capacitor 41, operational amplifier 44, and this point of amplifier of constituting by resistance 45 and 46, reach by means of operation variable resistor 42 and can change the bias voltage this point that is added to the control voltage on the tuning circuit 1 from control voltage generating circuit 4A arbitrarily, identical with the control voltage generating circuit 4 that is shown in Figure 13.

Control voltage generating circuit 4A has and the identical structure of control voltage generating circuit that is shown in Figure 13, has the 2nd low pass filter that is made of resistance 47 and electric capacity 48 and the 2nd amplifier that is made of operational amplifier 49 and resistance 50,51 in addition.

In order from the square-wave signal of phase difference detecting circuit 3 outputs, to remove high-frequency signal, so be provided with the 1st low pass filter that constitutes by resistance 40 and capacitor 41.According to the duty ratio of above-mentioned square-wave signal, from the signal of the 1st low pass filter output DC voltage level smooth change.

In contrast, in order from the square-wave signal of phase difference detecting circuit 3 outputs, to remove the radio-frequency component more than about 20kHz, so be provided with the 2nd low pass filter that constitutes by resistance 47 and electric capacity 48.From the 2nd low pass filter, the FM modulation signal of FM sound etc. is exported as the FM rectified signal.This FM rectified signal uses the amplifier that is made of operational amplifier 49 grades to amplify, and is fetched into the outside of control voltage generating circuit 4A.

Figure 21 is the pie graph that expression utilizes the FM receiver of the mechanical tuning device be shown in Figure 19.

The FM receiver that is shown in Figure 21 comprises: the tuning circuit 1 and frequency control circuit 2, high-frequency amplifier circuit 10, low-frequency amplifier circuit 12, loud speaker 14 and the antenna 16 that are shown in Figure 19 and Figure 20.

10 pairs of FM ripples that received by antenna 16 of high-frequency amplifier circuit carry out the high frequency amplification and are input to tuning circuit 1.As mentioned above, according to control voltage from frequency control circuit 2, the control that tuning circuit 1 makes tuned frequency overlap with the FM wave frequency of input.

12 pairs of low-frequency amplifier circuits carry out low frequency from frequency control circuit 2 interior control voltage generating circuit 4A output FM rectified signals and amplify, and from loud speaker 14 output sounds.In addition, also can be transformed to sound with earphone, and without loud speaker 14.

And the FM receiver that is shown in Figure 21 is because need not be by the lc circuit of variable capacitor and magnetic rod antenna one-tenth, so the design of importation has become easily with the FM ripple of the tuning circuit 1 direct extraction frequency of wanting in the importation from antenna 16.Therefore, can form antenna 16, can efficient receive the FM ripple well with the conductive material of corynebacterium or wire.Specifically, or form antenna 16, or the lead portion of only using earphone just can receive desired FM ripple with excellent sensitivity as antenna 16, can save indispensable in the past magnetic rod antenna by means of the telescopic antenna that is used in auto radio etc.

And, because fully without magnetic rod antenna, thus can be on Semiconductor substrate the integrated forming circuit that almost all comprises the FM receiver of tuning circuit 1 and frequency control circuit 2 and high-frequency amplifier circuit 10 etc., also can on 1 chip, form forming circuit.

Like this, by being adjusted at the time constant of the low pass filter that comprises among the control voltage generating circuit 4A, easily the carrying out from be input to tuning circuit 1 only take out the FM modulation signal in the signal of FM modulation, mechanical tuning device shown in Figure 19 is being applied under the situation of FM receiver, just needn't be as original, back level at mechanical tuning device is provided with the FM detecting circuit in addition, can simplify circuit structure.

In existing FM receiver, in order after eliminating the amplitude influence of change, to carry out the FM detection, and between mechanical tuning device and FM detecting circuit, be provided with amplitude limiter, but be not subjected to the amplitude influence of change because of being transformed into square-wave signal with 2 voltage comparators in the phase difference detecting circuit 3 in the mechanical tuning device that is shown in Figure 20, so necessary in the past amplitude limiter circuit has not just needed yet.

In addition, though Figure 19 and Figure 20 have illustrated the situation of taking out the FM rectified signal from frequency control circuit 2 interior control voltage generating circuit 4A, certainly, as in existing receiver, also the FM detecting circuit that uses amplitude limiter circuit and various detection modes can be connected to the last FM of acquisition of the back level rectified signal of tuning circuit 1.[F, the example when being applied to the AM receiver]

Below, the situation that the mechanical tuning device of above-mentioned present embodiment is applied to the AM receiver is described.The tuning circuit 1 of present embodiment by means of whole 2 phase-shift circuit 110c, 130c, adds up to and carries out 360 ° phase shift when tuning.Therefore, can be by the output signal of tuning circuit 1 be carried out synchronous rectification as reference signal to input signal, only from the various frequency contents that are contained in input signal, extract the frequency content identical out, and this synchronous rectification output is used as the AM rectified signal with tuned frequency.

Figure 22 is a structure chart of having represented and used the mechanical tuning device of the AM detection that is realized by synchronous rectification.The mechanical tuning device that is shown in this figure is added on the tuning circuit 1 and frequency control circuit 2 that is shown in Fig. 1, comprises circuit of synchronous rectification 6 and is connected in the low pass filter (LPF) 7 of level thereafter.

Usually, synchronously input signal being carried out conversion operations with a certain reference signal, is exactly that what is called is equivalent to reference signal is mixed with input signal.Now, be considered as input signal the 1st and the 2nd approaching signal of frequency each other, the frequency of establishing the 1st signal is f1, and the frequency of the 2nd signal is f2 (=f1+ Δ f).And establishing reference signal frequency is fr.

If input signal is carried out synchronous rectification with such reference signal, then owing to each signal that is equivalent to available trigonometric function is represented multiplies each other each other, so, as its result, produce between frequency input signal f1 and f2 and the reference signal frequency fr and and the composition that differs from.Thereby, multiplying each other by making the 1st signal and reference signal in the input signal, each frequency content of f1+fr, f1-fr appears, multiplies each other by making the 2nd signal and reference signal in the input signal, each frequency content of f1+ Δ f+fr, f1+ Δ f-fr appears.

Now, if establish fr=f1,, 2f1, each frequency content of 0 occur, multiply each other, each frequency content of 2f1+ Δ f, Δ f occurs by making the 2nd signal and reference signal in the input signal then by the 1st signal and reference signal in the input signal are multiplied each other.Therefore, as synchronous output 2f+ Δ f, 2f1, Δ f, each frequency content of 0 appear.Wherein, so-called frequency " 0 " composition is exactly a flip-flop, in fact in this flip-flop, contain modulation signal, so adopt this flip-flop to be separated with alternating component (2f1+ Δ f, 2f1, Δ f) in addition and only to take out the way of flip-flop, can utilize the detection and the separated in synchronization of synchronous rectification simultaneously.

Under the situation of having considered domestic AM emission,,, just can only take out the desired transmitted wave composition that has same frequency with reference signal so employing can be removed the way greater than the low pass filter 7 of this 9kHz frequency content because above-mentioned Δ f is 9kHz.

Figure 23 is the detailed structure view of expression circuit of synchronous rectification 6 shown in Figure 22.The circuit of synchronous rectification 6 that is shown in this figure has voltage comparator 60 and analog switch (AS) 61.

This voltage comparator 60, its reversed input terminal ground connection, the output signal of tuning circuit 1 is input to its non-inverting input.Therefore, voltage comparator 60, output has the square-wave signal of regulation positive voltage when the output signal of tuning circuit 1 is in than the high voltage level of 0V, then exports the square-wave signal with regulation negative voltage on the contrary when being in than the low voltage level of 0V.

Analog switch 61 is according to the voltage level from voltage comparator 60 outputs, change over switch state.That is, when the square-wave signal from voltage comparator 60 outputs is the positive voltage of regulation, allow the input signal of tuning circuit 1 pass through, when square-wave signal is the negative voltage of regulation, cut off the input signal of tuning circuit 1.The output of analog switch 61 is imported into low pass filter 7, only extracts the frequency content that equates with tuned frequency out by means of this low pass filter 7, thereby obtains the AM rectified signal.

In the present embodiment, used tuning circuit 1, as illustrate with the detailed formation that is shown in Fig. 2, even in theory under the situation of tuned frequency variation, signal amplitude can not decayed yet, and always can obtain the output signal of uniform amplitude.But, in fact, simulate and it seems from assembling tuning circuit 1, understand some because of the variation output amplitude of tuned frequency and change, and also can produce distortion sometimes because of different output signals such as the kind of the FET that constitutes variable resistor 116,136 or variable amplitude., as shown in figure 22, carry out synchronous rectification, but can eliminate by tuning circuit 1 making amplitude change or the influence of the AM rectified signal that distortion etc. causes takes place, can take out the AM rectified signal of good SN ratio by input signal to tuning circuit 1.

And, in that synchronous rectification output is being used under the situation of AM detection, owing to the no signal zone that is lower than forward voltage that does not exist resembling when for example carrying out the AM detection, so can have linear good AM received signal with diode.Particularly, under the situation of the integrated whole mechanical tuning device that comprises the AM detecting circuit on the Semiconductor substrate, not using the low germanium diode of forward voltage owing to use the high silicon diode of forward voltage, is desirable so do not use the detection mode of diode.Therefore, be shown in the mechanical tuning device of Figure 22, effective especially under integrated situation.

In addition, in being shown in the mechanical tuning device of Figure 22, though the input signal to tuning circuit 1 has carried out synchronous rectification, but obviously, as existing receiver, the AM detecting circuit that utilizes synchronous rectification is connected on the back level of tuning circuit 1, perhaps the AM detecting circuit that utilizes other detection mode is connected to and obtains the AM rectified signal on the back level of tuning circuit 1 and also be fine.

Figure 24 is the structure chart that expression has utilized the AM receiver that is shown in Figure 22 mechanical tuning device.

Be shown in the AM receiver of Figure 24, except that the tuning circuit 1 that is shown in Figure 22, frequency control circuit 2, circuit of synchronous rectification 6 and low pass filter 7, also comprise high-frequency amplifier circuit 10, low pass filter 7, low-frequency amplifier circuit 12, loud speaker 14 and antenna 16.

After carrying out the high frequency amplification, the AM ripple that receives with 10 pairs of antennas 16 of high-frequency amplifier circuit is input in the tuning circuit 1.By means of the tuned frequency of frequency control circuit 2 control tuning circuits 1, at this moment use from the signal of tuning circuit 1 output and carry out synchronous rectification, and from low pass filter 7 output AM rectified signals.This AM rectified signal is exported from loud speaker 14 after amplifying by low-frequency amplifier circuit 12 again.[the 1st variation of tuning circuit]

Comprise that the RC circuit has constituted each phase-shift circuit 110c, 130c though contain the tuning circuit 1 of the mechanical tuning device that is shown in Fig. 2, also can adopt the RC circuit is replaced as the phase-shift circuit of the LR circuit that is made of resistance and inductance and constitutes tuning circuit.

Figure 25 is the circuit diagram of another kind of structure that expression contains the phase-shift circuit of LR circuit, has shown the structure of the phase-shift circuit 110c that can be replaced into tuning circuit 1 prime that is shown in Fig. 2.The phase-shift circuit 110L that is shown in this figure has the RC circuit that is made of electric capacity 114 and variable resistor 116 in the phase-shift circuit 110c of Fig. 3 being shown in, and is replaced as the structure of the LR circuit that is made of variable resistor 116 and inductance 117.

Therefore, be shown in the relation of input and output voltage etc. of the phase-shift circuit 110L of Figure 25, shown in the vectogram of Figure 26, can think, respectively the voltage VC1 that is shown in Fig. 4 is replaced into the voltage VR1 at variable resistor 116 two ends, and the voltage VR1 that is shown in Fig. 4 is replaced into the voltage VL1 at inductance 117 two ends.

And, be T if establish the LR circuit time constant that constitutes by inductor 117 and variable resistor 116 ₁(resistance value that the inductance of establishing inductor 117 is L, establish variable resistor 116 is R, then T ₁=L/R), then the amount of phase shift φ 3 of phase-shift circuit 110L is identical with the φ 1 shown in above-mentioned (6) formula.

Figure 27 is the circuit diagram of another kind of structure that expression contains the phase-shift circuit of LR circuit, has shown the structure of the phase-shift circuit 130c that can be replaced into the tuning circuit 1 back level that is shown in Fig. 2.The phase-shift circuit 130L that is shown in this figure has the RC circuit that is made of variable resistor 136 and electric capacity 134 in the phase-shift circuit 130c of Fig. 5 being shown in, and is replaced as the structure of the LR circuit that is made of inductance 137 and variable resistor 136.

Therefore, be shown in the relation of input and output voltage etc. of the phase-shift circuit 130L of Figure 27, shown in the vectogram of Figure 28, can think, respectively the voltage VC2 that is shown in Fig. 6 is replaced into the voltage VR2 at variable resistor 136 two ends, and the voltage VR2 that is shown in Fig. 6 is replaced into the voltage VL2 at inductance 137 two ends.

And, be T if establish the LR circuit time constant that constitutes by variable resistor 136 and inductor 137 ₂(inductance that the resistance value of establishing variable resistor 136 is R, establish inductor 137 is L, then T ₂=L/R), then the amount of phase shift φ 4 of phase-shift circuit 130L is identical with the φ 2 shown in above-mentioned (7) formula.

Like this, be shown in the phase-shift circuit 110L and the phase-shift circuit 130L that is shown in Figure 27 of Figure 25, respectively with the phase-shift circuit 110c that is shown in Fig. 3 or Fig. 5,130c equivalence, in the tuning circuit 1 that is shown in Fig. 2, can be replaced as the phase-shift circuit 110L that is shown in Figure 25 to the phase-shift circuit 110c of prime respectively, the phase-shift circuit 130c of back level is replaced as the phase-shift circuit 130L that is shown in Figure 27.The tuned frequency of the tuning circuit that comprises phase-shift circuit 110L, 130L and constitute, since for example with each phase-shift circuit 110L, 130L in the R/L reciprocal of LR circuit time constant proportional, dwindle by means of the integrated inductance L that makes therein easily, contain 2 phase-shift circuit 110L, 130L and constitute the integrated way of whole tuning circuit so adopt to make, make the tuned frequency high frequencyization easily.

In addition, be shown in phase-shift circuit 110c, the 130c of Fig. 2 at handle, be replaced as respectively under the situation of phase-shift circuit 110L that is shown in Figure 25 and the phase-shift circuit 130L that is shown in Figure 27, because changing in the opposite direction of each amount of phase shift when gate voltage of the FET of formation variable resistor 116 and 136 changes, so must also be replaced as the EX-OR door 33 in the phase difference detecting circuit 3 that is shown in Figure 13 EX-NOR (XNOR) door, and equal exchange is shown in any 2 inputs of voltage comparator 31,32 of Figure 13, and the change direction of control voltage is turned around.

And, the phase-shift circuit 110c, the 130c that are shown in the tuning circuit 1 of Fig. 2, be replaced as respectively under the situation of phase-shift circuit 110L, 130L, be connected among the operational amplifier 112 or the bleeder circuit on 132 the output in each phase-shift circuit, can save arbitrary bleeder circuit.Perhaps, can save both sides' bleeder circuit, and adopt adjust the way of resistance ratio, resistance 138 and 140 the resistance ratio of resistance 118 and 120, the loss that produces on the feedback circuit of tuning circuit 1 is compensated.

Do not needing to amplify under the situation of work, can save the back level bleeder circuit 160 of back level phase-shift circuit again, and the output of back level phase-shift circuit is directly fed back to prime one side.Perhaps, also can make extremely little value to the resistance value of the resistance 162 in the bleeder circuit 160 voltage ratio is set at 1.[the 2nd variation of tuning circuit]

Figure 29 is the circuit diagram of the 2nd variation of expression tuning circuit.Be shown in the tuning circuit 1A of this figure, comprise: adopt the phase place that makes the AC signal of importing respectively to carry out the way of ormal weight displacement, carry out 2 phase-shift circuit 210c, 230c of 360 ° of amount of phase shift in the frequency total of regulation; Respectively through feedback resistance 170 and input resistance 174 (supposing that input resistance 174 has n times of resistance value of feedback resistance 170 resistance values), with the ratio of regulation to the output (feedback signal) of the phase-shift circuit 230c of back level be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

In the tuning circuit 1 that is shown in Fig. 2, be set at each resistance value of resistance 118 in the phase-shift circuit 110c of prime and resistance 120 identical, amplitude variations when dying the frequency change that can suppress input exchange signal, by the bleeder circuit that is formed by resistance 121 and 123 being connected to output one side of operational amplifier 112, and be the gain setting of phase-shift circuit 110c value greater than 1.Therefore, the prime phase-shift circuit 210c that in being shown in the tuning circuit 1A of Figure 29, contains, do not establish bleeder circuit in phase-shift circuit, adopt the resistance value way also bigger than the resistance value of resistance 118 ' of setting resistance 120 ', the gain setting that makes phase-shift circuit 210c is the value greater than 1.

As for back level phase-shift circuit 230c too, adopt the resistance value way also bigger than the resistance value of resistance 138 ' of setting resistance 140 ', the gain setting that makes phase-shift circuit 230c is the value greater than 1.And, be connected with feedback resistance 170, lead-out terminal 192 and resistance 178 at the lead-out terminal of phase-shift circuit 230c.

Also have,, bleeder circuit is connected on the back level of back level phase-shift circuit 230c, through this dividing potential drop output of feedback resistance 170 feedbacks though the output of the phase-shift circuit 230c of back level is directly fed back among the tuning circuit 1A that is shown in Figure 29.

But, as mentioned above,, then can produce gain variations with the signal frequency of input if set gain that each resistance value makes phase-shift circuit for greater than 1 value.For example, phase-shift circuit 210c with regard to prime, when frequency input signal is low, because phase-shift circuit 210c becomes voltage follower circuit, gain at this moment is 1 times, on the contrary when frequency is high, because phase-shift circuit 230c becomes inverting amplifier, at this moment gain is-m times (m is the ratio of resistance 120 ' and resistance 118 '), so when frequency input signal changed, the gain of phase-shift circuit 210c also changed and produce the amplitude change of output signal.

The change of such amplitude can be adopted resistance 119 is connected on the reversed input terminal of operational amplifier 112, when making input signal low and the way of the gain coincidence of Gao Shi suppress.Specifically, if establishing the resistance value of resistance 118 ' and be the resistance value of r, resistance 120 ' is mr, then adopt the way that the resistance value of resistance 119 is set at mr/ (m-1), the frequency that just can make input signal is 0 and each coincidence that gains of the phase-shift circuit 210c when infinitely great.Equally, concerning phase-shift circuit 230c, also can adopt the resistance 119 with regulation resistance value is connected to way on the reversed input terminal of operational amplifier 132, suppress the amplitude change of output signal.In addition, an end of resistance 119 and resistance 139 also can be connected on the fixed potential except that ground level.[the 3rd variation of tuning circuit]

In being shown in the tuning circuit 1A of Figure 29, the example that contains the RC circuit at phase-shift circuit 210c, 230c being described, but having replaced also can constituting same phase-shift circuit under the situation of RC circuit with the LR circuit.

Figure 30 is the forming circuit figure that expression contains the phase-shift circuit of LR circuit, and shows the structure of the prime phase-shift circuit 210c that can be replaced into the tuning circuit 1A that is shown in Figure 29.The phase-shift circuit 210L that is shown in this figure has the RC circuit that constitutes by electric capacity 114 in the prime phase-shift circuit 210c that is shown in Figure 29 and variable resistor 116, is replaced as the LR circuit that is made of variable resistor 116 and inductance 117.

On the other hand, Figure 31 is the another kind of forming circuit figure that expression contains the phase-shift circuit of LR circuit, and shows the structure of the back level phase-shift circuit 230c that can be replaced into the tuning circuit 1A that is shown in Figure 29.The phase-shift circuit 230L that is shown in this figure has the RC circuit that constitutes by variable resistor 136 in the back level phase-shift circuit 230c that is shown in Figure 29 and electric capacity 134, is replaced as the LR circuit that is made of inductance 137 and variable resistor 136.

The phase-shift circuit 210L that is shown in Figure 30 is equivalent with the prime phase-shift circuit 210c that is shown in Figure 29, can be replaced as the phase-shift circuit 210L that is shown in Figure 30 to the prime phase-shift circuit 210c of the tuning circuit 1A that is shown in Figure 29.Similarly, the phase-shift circuit 230L that is shown in Figure 31 is equivalent with the back level phase-shift circuit 230c that is shown in Figure 29, can be replaced as the phase-shift circuit 230L that is shown in Figure 31 to the back level phase-shift circuit 230c of the tuning circuit 1A that is shown in Figure 29.

2 phase-shift circuit 210c, 230c, be replaced as respectively under the situation of phase-shift circuit 210L, 230L, by making whole tuning circuit integrated, just make the tuned frequency high frequencyization easily.

In addition, be shown in phase-shift circuit 210c, the 230c of Figure 29 at handle, be replaced as respectively under the situation of phase-shift circuit 210L that is shown in Figure 30 and the phase-shift circuit 230L that is shown in Figure 31, because the change direction of each amount of phase shift when gate voltage of the FET that forms variable resistor 116 and 136 is changed becomes rightabout, so must also be replaced as the EX-OR door 33 in the phase difference detecting circuit 3 that is shown in Figure 13 EX-NOR (XNOR) door, and equal exchange is shown in any 2 inputs of voltage comparator 31,32 of Figure 13, and the change direction of control voltage is turned around.

But, be shown in the tuning circuit 1A of Figure 29, adopt the way that connects resistance 119 or 139 on 2 phase-shift circuit 210c, the 230c respectively, to prevent the tuned frequency amplitude change in when change, but because the variable range of frequency when narrow the amplitude change also diminish, constitute tuning circuit so can remove above-mentioned resistance 119 and 139.Perhaps, one that also can only remove in resistance 119 or 139 constitutes tuning circuit.[the 4th variation of tuning circuit]

In above-mentioned tuning circuit 1,1A, result from the input impedance of prime phase-shift circuit 110c etc. owing to comprise the loss of the feedback oscillator of all pass circuit of 2 phase-shift circuit 110c etc. and the feedback circuit that feedback resistance 170 constitutes, so, in order to suppress to result from the loss occurrence of this input impedance, can insert the follow circuit that constitutes by transistor in the prime again of the phase-shift circuit 110c of prime etc., feedback signal be outputed in the phase-shift circuit (for example 110c and 110L etc.) of prime through this follow circuit.

Figure 32 is the inner circuit diagram that contains tuning circuit one example of follow circuit of expression.The tuning circuit 1B that is shown in this figure is to have inserted the follow circuit 150 that is formed by transistor in prime one side of prime phase-shift circuit 110c with the difference that is shown in the tuning circuit 1 of Fig. 2.Also have, be shown in the follow circuit 150 of Figure 32,, also can constitute with emitter follower circuit though available so-called source follower constitutes.In Figure 32, also can be set at 1 to the voltage ratio of bleeder circuit 160, perhaps, it is own to save this bleeder circuit 160, is only carried out tuning work and is not carried out amplification work by whole tuning circuit.

Like this, if the follow circuit 150 that is formed by transistor in the prime one side cascade of the phase-shift circuit 110c of prime etc. with the comparison such as tuning circuit 1 grade of Fig. 2, can increase the resistance value of feedback resistance 170 and input resistance 174.Particularly, under situation about whole tuning circuit being integrated on the Semiconductor substrate,, the occupied area of device is increased, so wish that resistance value greatly to a certain degree if do the resistance value of feedback resistance 170 grades for a short time.Therefore, under situation such as integrated, this follow circuit 50 that connects shown in figure 32 is effective especially.[the 5th variation of tuning circuit]

In the tuning circuit 1 that is shown in Fig. 2, be decided to be 360 ° though suppose the amount of phase shift that 2 phase-shift circuit 110c, 130c lump together, but also can in the phase-shift circuit 110c and 130c of cascade, connect the negative circuit of not carrying out phase-shifts and constitute tuning circuit.

Figure 33 is the circuit diagram that expression is connected to non-reversed-phase circuit 350 the tuning circuit 1C formation on the prime of 2 phase-shift circuits.As shown in the drawing, tuning circuit 1C comprises: have by saved among the phase-shift circuit 110c that is shown in Fig. 3 resistance 121 and 123 and the phase-shift circuit 310c of the structure that forms, have by saved among the phase-shift circuit 130c that is shown in Fig. 5 resistance 141 and 143 and the phase-shift circuit 330c of the structure that forms, be connected in the non-reversed-phase circuit 350 of the prime of phase-shift circuit 310c, the bleeder circuit 160 that constitutes by resistance 162 and 164 and the add circuit that constitutes by feedback resistance 170 and input resistance 174.

Be shown in phase-shift circuit 310c, the 330c of Figure 33, except that the output in operational amplifier 112 or 132 does not connect bleeder circuit, have and the same structure of each phase-shift circuit 110c, 130c that is shown in Fig. 3, transfer function or amount of phase shift are also identical with phase-shift circuit 110c, 130c.But, in (2) formula, become a ₁=1, in (3) formula, a ₂=1.

Non-reversed-phase circuit 350 is input to non-inverting input by AC signal and makes the operational amplifier 352 of reverse inter-input-ing ending grounding through resistance 354; And the inverting input and the resistance between the lead-out terminal 356 that are connected to this operational amplifier 352 constitute.Operational amplifier 352 has the regulation multiplication factor that resistance ratio determined by 2 resistance 354,356.

Resistance value is identical separately with 120 owing to resistance 118, so phase-shift circuit 310c gain is 1.Equally, also resistance value is identical separately with 140 owing to resistance 138 for phase-shift circuit 330c, so its gain is 1.Thereby in above-mentioned tuning circuit 1C, the gain of setting above-mentioned non-reversed-phase circuit 350 is the value greater than 1, to replace obtaining gain with each phase-shift circuit.

Have the non-reversed-phase circuit 350 of this formation, phase of input signals is exported unchangeably,, compensate the decay of the signal amplitude that causes because of bleeder circuit 160 or the loss that in feedback circuit, produces easily by adjusting gain.And non-reversed-phase circuit 350 is same with the follow circuit that is formed by above-mentioned transistor, also has the function as the buffer of prime one side that is connected to prime phase-shift circuit 310c.

In addition, the non-reversed-phase circuit 350 that is shown in Figure 33 can also be connected on the tuning circuit 1 that is shown in Fig. 2 or Figure 29, the prime of 1A etc.[the 6th variation of tuning circuit]

Though the amount of phase shift that above-mentioned each tuning circuit 1,1A, 1B and 1C produce with 2 phase-shift circuits adds up to the tuning work that 360 ° frequency is stipulated, but by 2 phase-shift circuits that carry out identical work basically formation tuning circuit that combines, it is also passable to form the tuning work that frequency that the amount of phase shift that produces with 2 phase-shift circuits adds up to 180 ° stipulates.

Figure 34 is the circuit diagram of the 6th variation of expression tuning circuit, promptly connects phase-shift circuit 310c to replace the back level phase-shift circuit 330c of Figure 33, connects negative circuit 380 to replace non-reversed-phase circuit 350.

Negative circuit 380 makes the operational amplifier 382 of the sub-ground connection of non-inverting input by when resistance 384 is input to reversed input terminal to the AC signal of input; And the inverting input and the resistance between the output 386 that are connected in this operational amplifier 382 constitute.If AC signal is input on the reversed input terminal of operational amplifier 382 through resistance 384, then from the lead-out terminal of operational amplifier 382, the inversion signal that output phase has reversed, and this inversion signal is input among the phase-shift circuit 310c of prime.And the regulation multiplication factor of these negative circuit 380 useful 2 resistance 384 and the decision of 386 resistance ratio is because the resistance value of resistance 386 is bigger than the resistance value of resistance 384, so acquisition is greater than 1 gain.

Although as mentioned above, phase-shift circuit 310c is benchmark along with the frequencies omega of input signal changes to ∞ from 0 with input voltage Ei, at clockwise, phase place is displaced to 360 ° from 180 °.Under the situation of the RC circuit time constant in 2 phase-shift circuit 310c identical (establish it and be T), under the frequency of ω=1/T, 2 phase-shift circuit 310c amount of phase shift separately becomes 270 °.Therefore, 270 ° * the 2=540 of whole phase-shifts ° (=180 °) that carry out with 2 phase-shift circuit 310c, and owing to use the negative circuit 380 of the prime that is connected in 2 phase-shift circuit 310c to make phase place anti-phase, so phase place is as one week of all circulations, amount of phase shift is that 360 ° signal is from the phase-shift circuit 310c ' output of back level.

And, in the tuning circuit 1D shown in Figure 34, is the gain setting of above-mentioned negative circuit 380 value greater than 1, to replace obtaining gain with each phase-shift circuit, compensates the decay of the signal amplitude that causes because of bleeder circuit 160 and the loss that produces easily in feedback circuit.[the 7th variation of tuning circuit]

The tuning circuit 1D that has been shown in Figure 34 shows the example of cascade phase-shift circuit 310c, and also can carry out tuning work when the phase-shift circuit 330c that is shown in Figure 33 cascaded up.

Figure 35 is the circuit diagram of the 7th variation of expression tuning circuit.The tuning circuit 1E that is shown in this figure replaces the phase-shift circuit 310c of Figure 34 with cascade phase-shift circuit 330c and forms.

But as mentioned above, phase-shift circuit 330c is benchmark along with the frequencies omega of input signal changes to ∞ from 0 with input voltage Ei, and at clockwise, phase place is displaced to 180 ° from 0 °.Under the situation of the RC circuit time constant in 2 phase-shift circuit 330c identical (establish it and be T), under the frequency of ω=1/T, 2 phase-shift circuit 330c amount of phase shift separately becomes 90 °.Therefore, all make 180 ° of phase-shifts with 2 phase-shift circuit 330c, and owing to make phase place anti-phase with the negative circuit 380 of prime that is connected in 2 phase-shift circuit 330c, so phase place as one week of all circulations, amount of phase shift is that 360 ° signal is from the phase-shift circuit 310c output of back level.

And, same with the tuning circuit 1D that is shown in Figure 34, in above-mentioned tuning circuit 1E, is the gain setting of above-mentioned negative circuit 380 value greater than 1, to replace obtaining gain with each phase-shift circuit, compensation reaches the loss that produces because of the signal amplitude decay that bleeder circuit 160 causes in feedback circuit easily.

And any comprises that all the RC circuit constitutes 2 phase-shift circuits at tuning circuit 1C, the 1D shown in Figure 33～Figure 35 and 1E, yet also can be by comprising that the LR circuit constitutes.For example, in being shown in the tuning circuit 1C of Figure 33, can be replaced as the phase-shift circuit that from phase-shift circuit 110L, saves bleeder circuit to the phase-shift circuit 310c of prime, simultaneously the phase-shift circuit 330c of back level is replaced as the phase-shift circuit that saves bleeder circuit from phase-shift circuit 130L.

Also have, in the tuning circuit 1C, the 1D that are shown in Figure 33～Figure 35 and 1E, do not carry out under the situation of signal amplitude amplification planning only to carry out tuning work, it is good to save bleeder circuit 160.And, bleeder circuit is connected at least one the output of 2 operational amplifiers in the phase-shift circuit good.For example, in the tuning circuit 1C of Figure 33, if respectively bleeder circuit is connected to the output of the operational amplifier 132 in the phase-shift circuit 330c of the output of the operational amplifier 112 in the phase-shift circuit 310c of prime and back level, it is identical then to become the structure that forms on the more prime of phase-shift circuit 110c of the prime interior with non-reversed-phase circuit 350 being connected to the tuning circuit 1 that is shown in Fig. 2.

But, at tuning circuit 1C, 1D shown in Figure 33～Figure 35 and 1E etc. by 2 phase-shift circuits and non-reversed-phase circuit, or 2 phase-shift circuits and negative circuit constitute, and by 3 circuit integral body connecting under assigned frequency, the tuning work that the way that adds up to amount of phase shift to become 360 ° is stipulated.Therefore,, then can to a certain degree the degree of freedom be arranged, can determine the order of connection as required regardless of 3 circuit that are linked in sequence with which type of iff being conceived to amount of phase shift.[the 8th variation of tuning circuit]

The 1st of above-mentioned tuning circuit～the 7th variation, any all contains operational amplifier in phase-shift circuit inside, yet also can constitute phase-shift circuit with transistor without operational amplifier.

The tuning circuit 1F that is shown in Figure 36 comprises: employing makes the way of the phase-shifts ormal weight of input exchange signal add up to 2 phase-shift circuit 410c, 430c of 360 ° of phase shifts respectively under the frequency of regulation; Make phase-shift circuit 430c output signal phase invariant and with the multiplication factor of regulation with the non-reversed-phase circuit 450 of its amplification and output; The bleeder circuit 160 that constitutes by the resistance 162 and 164 of the back level of being located at non-reversed-phase circuit 450; And in certain proportion respectively through feedback resistance 170 and input resistance 174 (supposition input resistance 174 has the n resistance value doubly of feedback resistance 170) with the dividing potential drop output (feedback signal) of bleeder circuit 160 be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

And the electric capacity 172 that feedback resistance 170 is connected in series and be inserted into input resistance 174 and input terminal 190 between electric capacity 176 1 be used from the prevention direct current, under operating frequency its impedance extremely little, promptly have huge electrostatic capacitance amount.

Figure 37 is the forming circuit figure that the phase-shift circuit 410c that has been shown in Figure 36 is extracted in expression out.The prime phase-shift circuit 410c that is shown in this figure comprises: grid is connected to the FET412 of input 122; Be connected in series to the source electrode of this FET412 and electric capacity 414 and the variable resistor 416 between the drain electrode; Be connected to drain electrode and the resistance between the positive supply 418 of FET412; Be connected to source electrode and the resistance between the ground 420 of FET412.Also have, FET412 and following FET432 can be with wherein at least one is replaced as bipolar transistor.

At this, setting is connected in 2 resistance 418 of the source electrode of above-mentioned FET412 and drain electrode and 420 resistance value for about equally, for being added to the alternating component of the input voltage on the input 122, the signal of phase coincidence is from the source electrode output of FET412, and anti-phase (180 ° of the phase place phase shifts) signal of phase place is exported from the drain electrode of FET412.

Also have, the interior resistance 426 of phase-shift circuit 410c that is shown in Figure 36 is used for FET412 is applied appropriate bias voltage.And variable resistor 416 for example as shown in figure 37, utilizes the raceway groove that forms between the source-drain electrode of junction type FET as resistive element, adopts and makes the variable way of grid voltage, can arbitrarily change resistance value in certain scope.

In having the phase-shift circuit 410c of this structure, if the AC signal of regulation is input to input 122, promptly, when adding the alternating voltage (input voltage) of regulation for the grid of FET412, alternating voltage with this input voltage homophase then just appears on the source electrode of FET412, on the contrary, alternating voltage anti-phase with this input voltage and that equate with voltage amplitude on coming across source electrode is then appearring in the drain electrode of FET412.And setting the amplitude that comes across the alternating voltage in this source electrode and the drain electrode all is Ei.

Between the source electrode of this FET412 and drain electrode, be connected with the series circuit (RC circuit) that constitutes by variable resistor 416 and electric capacity 414.Therefore, will be through the signal of synthetic source electrode that comes across FET412 respectively of variable resistor 416 or electric capacity 414 and the voltage in the drain electrode from output 124 outputs.

Figure 38 be the expression prime phase-shift circuit 410c input and output voltage and come across the vectogram that concerns between the voltage of electric capacity etc.

Owing at the source electrode of FET412 and drain electrode be respectively and input voltage homophase and anti-phase, and voltage amplitude is rendered as the alternating voltage of Ei, thus source electrode and drain between potential difference (alternating component) be 2Ei.And the voltage VR1 at the voltage VC1 at electric capacity two ends and variable resistor 416 two ends has 90 ° of phase deviations mutually, to its voltage that synthesizes, just equals the source electrode of FET412 and the voltage 2Ei between the drain electrode on the vector.

Therefore, as shown in figure 38, forming with voltage Ei 2 times as hypotenuse, is the right-angled triangle on perpendicular two limits with the both end voltage VR1 of the both end voltage VC1 of electric capacity 414 and variable resistor 416.Therefore, under the situation that the amplitude of input signal only changes with certain frequency, change the voltage VR1 at the two ends of the both end voltage VC1 of electric capacity 414 and variable resistor 416 along the circumference of the semicircle that is shown in Figure 38.

But, suppose the tie point of electric capacity 414 and variable resistor 416 and the potential difference between the earth level are taken out as output voltage E0, then this output voltage E0 can come out with vector representation, this vector is exactly to be starting point with its central point in being shown in the semicircle of Figure 38, and on the circumference that voltage VC1 and voltage VR1 are intersected a bit as vector of terminal point, its size equals the radius Ei of semicircle.And, even the frequency change of input signal, because this vectorial terminal point is just mobile on circumference, so can obtain the constant stable output of output amplitude along with frequency change.

And, as shown in Figure 38, because voltage VR1 and voltage VC1 intersect at a right angle on circumference, so theoretically, along with frequencies omega changes to ∞ from 0, be added to input voltage on the grid of FET412 and the phase difference between the voltage VR1, will with the voltage Ei of input voltage homophase as benchmark, the direction of rotating at hour hands changes to 360 ° from 270 °.And the whole amount of phase shift φ 5 of phase-shift circuit 410c is along with frequency changes to 360 ° from 180 °.And, adopt the variable way of resistance value that makes variable resistor 416, amount of phase shift φ 5 is changed.

Being shown in the transfer function of the phase-shift circuit 410c of Figure 37, is T if establish the time constant of the RC circuit that is made of electric capacity 414 and variable resistor 416 ₁(the electrostatic capacitance amount of establishing electric capacity 414 is that the resistance value of C, variable resistor 416 is R, then T ₁=RC), then can use in the same old way the K2 that is shown in (2) formula (but, a ₁＜1), the amount of phase shift φ 5 that is shown in Figure 38 is also with to be shown in the φ 1 shown in above-mentioned (6) formula identical.

Equally, Figure 39 is the forming circuit figure that the phase-shift circuit 430c that is shown in Figure 36 is extracted in expression out.The back level phase-shift circuit 430c that is shown in this figure comprises: grid is connected to the FET432 of input 142; Be connected in series to the source electrode of this FET432 and electric capacity 434 and the variable resistor 436 between the drain electrode; Be connected to drain electrode and the resistance between the positive supply 438 of FET432; Be connected to source electrode and the resistance between the ground 440 of FET432.

Same with the phase-shift circuit 410c that is shown in Figure 37, setting is connected in the resistance value of 2 resistance 438 of the source electrode of the FET432 shown in Figure 39 and drain electrode and 440 to about equally, for being added to the alternating component of the input voltage on the input 142, the signal of phase coincidence is from the source electrode output of FET432, and the anti-phase signal of phase place is exported from the drain electrode of FET432.

Also have, the interior resistance 446 of phase-shift circuit 430c that is shown in Figure 36 is used for FET432 is applied suitable bias voltage.And, be located at the electric capacity 148 of input one side of phase-shift circuit 430c, be used to forbid that taking out flip-flop from the output of phase-shift circuit 410c promptly intercepts direct current, only makes alternating component be input to phase-shift circuit 430.

In having the phase-shift circuit 430c of this structure, if the AC signal of regulation is input to input 142, promptly, add the alternating voltage (input voltage) of regulation to the grid of FET432, the alternating voltage with this input voltage homophase then on the source electrode of FET432, just occurs, then occurring alternating voltage anti-phase with this input voltage and that equate with voltage amplitude on coming across source electrode in the drain electrode of FET432 on the contrary.And the amplitude of the alternating voltage on supposing to come across this source electrode and drain all is Ei.

Between the source electrode of this FET432 and drain electrode, be connected with the series circuit (RC circuit) that constitutes by electric capacity 434 and variable resistor 436.Therefore, will be through the signal of synthetic source electrode that comes across FET432 respectively of electric capacity 434 or variable resistor 436 and the voltage in the drain electrode from output 144 outputs.

Figure 40 be expression back level phase-shift circuit 430c input and output voltage and come across the vectogram that concerns between the voltage of electric capacity etc.

Owing in the source electrode of FET432 and drain electrode, be respectively and input voltage homophase and anti-phase, and voltage amplitude is the alternating voltage of Ei, thus source electrode and drain between potential difference be 2Ei.And the voltage VC2 that comes across the voltage VR2 at variable resistor 436 two ends and the electric capacity two ends occur has 90 ° of phase deviations mutually, on the vector it is carried out voltage after the add operation, just equal the source electrode of FET432 and drain between potential difference 2Ei.

Therefore, as shown in figure 40, form right-angled triangle, this right-angled triangle as hypotenuse, is perpendicular both sides formation with the both end voltage VC2 of the both end voltage VR2 of variable resistor 436 and electric capacity 434 with 2 times of voltage Ei.Therefore, under the situation that the amplitude of input signal only changes with certain frequency, change the voltage VR2 at two ends of variable resistor 436 and the both end voltage VC2 of electric capacity 434 along the circumference of the semicircle that is shown in Figure 40.

If the tie point of variable resistor 436 and electric capacity 434 and the potential difference between the earth level are taken out as output voltage E0, then this output voltage E0 can come out with vector representation, this vector is exactly to be starting point with its central point in being shown in the semicircle of Figure 40, and on the circumference that voltage VC1 and voltage VR1 are intersected a bit as vector of terminal point, its size equals the radius Ei of semicircle.And, even the frequency change of input signal, because this vectorial terminal point is just mobile on circumference, so can obtain the constant stable output of output amplitude along with frequency change.

And, as shown in Figure 40,, so theoretically,, be added to input voltage on the grid of FET432 and the phase difference between the voltage VR2 on circumference along with frequencies omega changes to ∞ from 0 because voltage VR2 and voltage VC2 intersect at a right angle, just change to 90 ° from 0 °.And the whole amount of phase shift φ 6 of phase-shift circuit 430c is along with frequency changes to 180 ° from 0 °.

Be shown in the transfer function of the phase-shift circuit 430c of Figure 37, if the time constant of the RC circuit that hypothesis is made of variable resistor 436 and electric capacity 434 is T ₂(the electrostatic capacitance amount of establishing electric capacity 434 is that the resistance value of C, variable resistor 436 is R, then T ₂=RC), then can use in the same old way the K3 that is shown in (3) formula (but, a ₂＜1), the amount of phase shift φ 6 that is shown in Figure 40 is also with to be shown in the φ 2 shown in above-mentioned (7) formula identical.

Like this, phase-shifts ormal weight separately in 2 phase-shift circuit 410c, 430c, shown in Figure 38 and 40, under the frequency of regulation, all by 2 phase-shift circuit 410c, 430c, it is 360 ° signal that output adds up to amount of phase shift.

And, the non-reversed-phase circuit 450 that is shown in Figure 36 comprises: have the resistance 454 between the drain electrode of being connected to and the positive supply and be connected with the drain electrode of FET452 in FET452, the base stage of the resistance 456 between source electrode and the ground, simultaneously the transistor 458 that is connected with the source electrode of FET452 through resistance 460 of collector electrode, be used for the suitable bias voltage of handle and be added to resistance 462 on the FET452.Also have, be located at electric capacity 164 on the prime of the non-reversed-phase circuit shown in Figure 36 450 and forbid that taking out flip-flop from the output of the phase-shift circuit 430c of back level promptly is used to intercept direct current, only is input to alternating component in the non-reversed-phase circuit 450.

FET452 is when the grid input exchange signal, from drain electrode output inversion signal.And, when transistor 458 is imported this inversion signal in base stage, and then from the signal of collector electrode output reversing phase place, be the in-phase signal of benchmark promptly, and make this in-phase signal from non-reversed-phase circuit 450 outputs with signal phase with the grid that is input to FET452.

The output of this non-reversed-phase circuit 450, output as tuning circuit 1F is taken out from lead-out terminal 192, makes the output of this non-reversed-phase circuit 450 simultaneously, by the signal of bleeder circuit 160, through feedback resistance 170, feed back to input one side of the phase-shift circuit 410c of prime.And, carry out add operation to this feedback signal with through the signal of input resistance 174 input, and the signal voltage after this add operation is added on the input (being shown in the input 122 of Figure 37) of the phase-shift circuit 410c of prime.

And, the gain of above-mentioned non-reversed-phase circuit 450 is set to, each resistance value by above-mentioned resistance 454,456 and 460 decides, by adjusting the resistance value of these resistance, the loss that produces in decay that compensation causes because of 2 phase-shift circuit 410c, 430c being shown in Figure 36 or bleeder circuit 160 and the feedback circuit, and the circuit gain that makes whole tuning circuit is less than 1.

For the lead-out terminal 192 from tuning circuit 1 takes out the output signal that is input to bleeder circuit 160 non-reversed-phase circuit 450 before, thus can in tuning circuit 1F self, keep gain, and can be at tuning work while amplifying signal amplitude.[the 9th variation of tuning circuit]

Be shown in the tuning circuit of Figure 36, contain the RC circuit, yet also can use the phase-shift circuit that the RC circuit is replaced as the LR circuit that is made of resistance and inductance to constitute tuning circuit in the inside of each phase-shift circuit 410c, 430c.

Figure 41 is the forming circuit figure that expression contains the phase-shift circuit of LR circuit, and shows the structure of the prime phase-shift circuit 410c that can be replaced into the tuning circuit 1F that is shown in Figure 36.The phase-shift circuit 410L that is shown in this figure has the RC circuit that is made of electric capacity 414 and variable resistor 416 that will be shown in the prime phase-shift circuit 410c of Figure 36 and is replaced as the structure that is made of the LR circuit variable resistor 416 and inductance 417, and each resistance value of resistance 418 and resistance 420 is made as identical value.Also have, between the drain electrode of inductance 417 and FET412, insert electric capacity 419 and be used for the stopping direct current electric current.

The relation of the input and output voltage of above-mentioned phase-shift circuit 410L etc., shown in the vectogram of Figure 42, can think, respectively the voltage VC1 that is shown in Figure 38 is replaced as the voltage VR1 at variable resistor 416 two ends, the voltage VR1 that is shown in Figure 38 is replaced as the voltage VL1 at inductance 417 two ends.

And, be T if establish the LR circuit time constant that constitutes by inductor 417 and variable resistor 416 ₁(resistance value that the inductance of establishing inductor 417 is L, establish variable resistor 416 is R, then T ₁=L/R), the transfer function that then is shown in the phase-shift circuit 410L of Figure 41 can be used K2 (but a that is shown in (2) formula in the same old way ₁＜1) it is also identical with the φ 1 shown in above-mentioned (6) formula, to be shown in the amount of phase shift φ 7 of Figure 42.

Therefore, be shown in the phase-shift circuit 410L and the phase-shift circuit 410c that is shown in Figure 37 equivalence basically of Figure 41, the phase-shift circuit 410c that is shown in Figure 37 can be replaced as the phase-shift circuit 410L that is shown in Figure 41.

Figure 43 is the another kind of forming circuit figure of phase-shift circuit that expression contains the LR circuit, shows the structure that can be replaced into the phase-shift circuit 430c of level behind the tuning circuit 1F that is shown in Figure 36.The phase-shift circuit 430L that is shown in this figure has the RC circuit that is made of electric capacity 434 and variable resistor 436 that will be shown in the phase-shift circuit 430c of Figure 39, be replaced as the structure of the LR circuit that constitutes by variable resistor 436 and inductance 437, and each resistance value of resistance 438 and resistance 440 is made as identical value.In addition, the electric capacity 439 that inserts between the drain electrode of variable resistor 436 and FET432 is used for the stopping direct current electric current.

The relation of the input and output voltage of above-mentioned phase-shift circuit 430L etc., shown in the vectogram of Figure 44, can think, respectively the voltage VR2 that is shown in Figure 40 is replaced into the voltage VL2 at inductance 437 two ends, and the voltage VC2 that is shown in Figure 40 is replaced into the voltage VR2 at variable resistor 436 two ends.

And, be T if establish the LR circuit time constant that constitutes by variable resistor 436 and inductor 437 ₂(inductance that the resistance value of establishing variable resistor 436 is R, establish inductor 437 is L, then T ₂=L/R), the transfer function that then is shown in the phase-shift circuit 430L of Figure 43 can be used K3 (but a that is shown in (3) formula in the same old way ₂＜1) it is also identical with the φ 2 shown in above-mentioned (7) formula, to be shown in the amount of phase shift φ 8 of Figure 44.

Therefore, be shown in the phase-shift circuit 430L and the phase-shift circuit 430c that is shown in Figure 39 equivalence basically of Figure 43, the phase-shift circuit 430c that is shown in Figure 39 can be replaced as the phase-shift circuit 430L that is shown in Figure 43.

Like this, can be replaced as phase-shift circuit 410L and the 430L that is shown in Figure 41 and Figure 43 to 2 phase-shift circuit 410C that are shown in Figure 36 and 430C both sides.Adopt the integrated way of whole tuning circuit, make the tuned frequency high frequencyization easily.

In addition, be shown in phase-shift circuit 410c, the 430c of Figure 36 at handle, be replaced as respectively under the situation of phase-shift circuit 410L that is shown in Figure 41 and the phase-shift circuit 430L that is shown in Figure 43, because changing in the opposite direction of each amount of phase shift when gate voltage of the FET that forms variable resistor 416 and 436 is changed, so must also be replaced as the EX-OR door 33 in the phase difference detecting circuit 3 that is shown in Figure 13 EX-NOR (XNOR) door, and need equal exchange to be shown in any 2 inputs of voltage comparator 31,32 of Figure 13, the change direction of control voltage is turned around.

And, respectively the phase-shift circuit 410c, the 430c that are shown in Figure 36 being replaced as under the situation of phase-shift circuit 410L, 430L, also can save bleeder circuit 160, and the output of back level phase-shift circuit is directly fed back to prime one side; Perhaps remove the resistance 162 in the bleeder circuit 160 and only keep resistance 164.Under the situation of having saved bleeder circuit 160, or under the situation of removing resistance 162, can only carry out tuning work.[the 10th variation of tuning circuit]

Figure 45 is the circuit diagram of another variation of expression tuning circuit.The tuning circuit 1G that is shown in this figure comprises: adopt the phase place of the AC signal that makes input respectively to carry out the way that ormal weight is shifted, under the frequency of regulation, add up to 2 phase-shift circuit 410c of 180 ° of phase shifts, again the phase-shift circuit 410c phase of output signal of counter-rotating back level negative circuit 480, with the ratio of regulation to respectively through feedback resistance 170 and input resistance 174, from the signal (feedback signal) of negative circuit 480 outputs be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

Each phase-shift circuit 410c, it constitutes in detail and the phase relation of input and output is described as follows with Figure 37 and Figure 38.For example establishing the RC circuit time constant that is made of electric capacity 414 and variable resistor 416 is T ₁, at ω=1/T ₁The amount of phase shift φ 5 of frequency be 270 ° of hour hands rotation directions (phase delay direction).

Therefore, the amount of phase shift of the phase delay direction that 2 phase-shift circuit 410c are all adds up to 5=270 °+270 °=540 ° of φ 5+ φ (=180 °) under the frequency of regulation.

And negative circuit 480 comprises: have the resistance 484 between drain electrode of being connected respectively to and the positive supply and the FET482 of the resistance 486 between source electrode and the ground, the grid of FET482 applied the resistance 488 of regulation bias voltage.During the grid input exchange signal of FET482, just export the inversion signal of inverted phase from the drain electrode of FET482.And this negative circuit 480 has the regulation gain by the resistance ratio decision of 2 resistance 484 and 486.

Like this, under the frequency of regulation, make 180 ° of phase-shifts by means of 2 phase-shift circuit 410c, and then make phase place anti-phase by the negative circuit 480 that connects in the back level, these 3 all amount of phase shift of circuit add up to 360 °.Therefore, through feedback resistance 170 output of negative circuit 480 is fed back on input one side of phase-shift circuit 410c of prime, and this feedback signal and signal through input resistance 174 input carried out add operation, simultaneously by adjusting the gain of negative circuit 480, carry out the tuning work same with the tuning circuit 1 that is shown in Fig. 2.

Also have, though in the tuning circuit 1G that feedback resistance 170 directly makes the output of negative circuit 480 feed back to be shown in Figure 45, but same with the tuning circuit 1F that is shown in Figure 36, also can be connected to bleeder circuit 160 the upward feedback dividing potential drop output of back level of this negative circuit 480.[the 11st variation of tuning circuit]

Figure 46 is the circuit diagram of another variation of expression tuning circuit, and is opposite with Figure 45, and its formation comprises the phase-shift circuit 430C of the back level that is shown in Figure 36.

The tuning circuit 1H that is shown in Figure 46 comprises: adopt the phase place of the AC signal that makes input respectively to carry out the way that ormal weight is shifted, under the frequency of regulation, add up to 2 phase-shift circuit 430C of 180 ° of phase shifts, again the phase-shift circuit 430c phase of output signal of counter-rotating back level negative circuit 480, with the ratio of regulation to respectively through feedback resistance 170 and input resistance 174, from the signal (feedback signal) of negative circuit 480 outputs be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

Each phase-shift circuit 410c, it constitutes in detail and the phase relation of input and output is described as follows with Figure 37 and Figure 38.The time constant of for example establishing the RC circuit that is made of electric capacity 434 and variable resistor 436 is T ₂, at ω=1/T ₂The amount of phase shift φ 6 of frequency be 90 ° of hour hands rotation directions (phase delay direction).

Therefore, the frequency in regulation by means of 2 phase-shift circuit 430c, makes 180 ° of phase-shifts, and then makes phase place anti-phase by means of the negative circuit 480 that is connected in the back level, and these 3 all amount of phase shift of circuit add up to 360 °.For this reason, make the output of negative circuit 480 feed back to input one side of the phase-shift circuit 430C of prime through feedback resistance 170, and handle is in the signal that input resistance 174 is imported adds this feedback signal, simultaneously by adjusting the gain of negative circuit 480, can carry out the tuning work same with the tuning circuit 1 that is shown in Fig. 2.

Also have, same with the tuning circuit 1F that is shown in Figure 36, also can in being shown in the tuning circuit 1H of Figure 46, bleeder circuit 160 be connected on the back level of this negative circuit 480, amplify simultaneously with tuning.

But, above-mentioned various tuning circuit 1F, 1G and 1H etc., constitute by 2 phase-shift circuits and non-reversed-phase circuit or 2 phase-shift circuits and negative circuit, and make and make in the frequency of regulation all by means of 3 circuit that couple together that to add up to amount of phase shift be 360 °, the tuning work of stipulating.Therefore, if only be conceived to amount of phase shift, which type of 3 circuit that are linked in sequence that then don't work all have to a certain degree the degree of freedom, can determine the connecting circuit order as required.

And in the above-mentioned tuning circuit 1G and 1H that is shown in Figure 45 and Figure 46, though show the example that contains the RC circuit in phase-shift circuit inside, the formation tuning circuit also can cascade up the phase-shift circuit that the LR circuit is contained in inside.For example, also can connect the phase-shift circuit 410L that is shown in Figure 41 and need not be shown in 2 phase-shift circuit 410c of the tuning circuit 1G of Figure 45.Perhaps, also can connect the phase-shift circuit 430L that is shown in Figure 43 and need not be shown in 2 phase-shift circuit 430c of the tuning circuit 1H of Figure 46.

But, the phase-shift circuit that contains the RC circuit is being replaced as under the situation of the phase-shift circuit that contains the LR circuit, because changing in the opposite direction of each amount of phase shift when grid voltage of the FET that forms variable resistor 416 and 436 is changed, so must also be replaced as the EX-OR door 33 in the phase difference detecting circuit 3 that is shown in Figure 13 EX-NOR (XNOR) door, and equal exchange is shown in any 2 inputs of voltage comparator 31,32 of Figure 13, and the change direction of control voltage is turned around.

In addition, in above-mentioned tuning circuit 1F, 1G and 1H,, also can replace FET to constitute phase-shift circuit with bipolar transistor though constituted phase-shift circuit with FET412 or FET432.[the 12nd variation of tuning circuit]

Figure 47 is the circuit diagram of the 12nd variation of expression tuning circuit.The tuning circuit 1J that is shown in this figure comprises: the non-reversed-phase circuit 550 that the phase of ac signal of input is exported unchangeably, adopt the way that makes phase of input signals displacement ormal weight respectively, the phase-shift circuit 510C and the 530C that add up to 360 ° phase shift in assigned frequency, the bleeder circuit 160 that constitutes by the resistance 162 and 164 of the back level of being located at back level phase-shift circuit 530C, respectively through feedback resistance 170 and input resistance 174 (supposing that input resistance 174 has the n resistance value doubly of feedback resistance 170), with the ratio of regulation to the dividing potential drop output (feedback signal) of bleeder circuit 160 be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

In addition, non-reversed-phase circuit 550 is the non-reversed-phase circuits as the buffer circuits function, is to be used to prevent take place when phase-shift circuit 510C that directly connects prime and above-mentioned add circuit the loss of signal etc. and non-reversed-phase circuit 550 is set.Non-reversed-phase circuit 550 can be made of for example emitter follower circuit or source follower etc.Also have, so that the loss when directly connecting etc. are suppressed under the minimal situation, also can save this non-reversed-phase circuit 550 and constitute tuning circuits at the device constant of each device of having selected feedback resistance 170 grades.

Shown in Figure 48 is the pie graph of extracting the phase-shift circuit 510C of the prime that is shown in Figure 47 out.The phase-shift circuit 510C that is shown in the prime of this figure comprises: with the multiplication factor of regulation amplify the differential voltage of 2 inputs and with the differential amplifier 512 of its output, make the electric capacity 514 and the variable resistor 516 of non-inverting input that is input to differential amplifier 512 behind the signal phase displacement ormal weight that is input to input 122 and do not change the signal phase that is input to input 122, is this voltage level dividing potential drop about 1/2, is input to the resistance 518 and 520 of the reversed input terminal of differential amplifier 512.

Above-mentioned variable resistor 516, for example as shown in figure 48, the raceway groove that forms between the source electrode of the FET that utilizes at junction type and the drain electrode is as resistance, and by making the grid voltage variation, can arbitrarily change the resistance value of resistance within the specific limits.

If to the AC signal of the input 122 input regulation that is shown in Figure 48, will be added on voltage Ei on the input 122 by resistance 518 and resistance 520, dividing potential drop is that about 1/2 voltage is added on the reversed input terminal of differential amplifier 512.

On the other hand, if input signal is input to input 122, the signal that then comes across on the contact of electric capacity 514 and variable resistor 516 is imported on non-inverting input of differential amplifier 512.Because input signal is input to an end of the RC circuit that is made of electric capacity 514 and variable resistor 516, the signal voltage behind the phase of input signals displacement ormal weight is applied on non-inverting input of differential amplifier 512 by this RC circuit.Like this, differential amplifier 512 is just exported and has been amplified the signal of the voltage difference that is added on 2 input terminals with the regulation multiplication factor.

Figure 49 be shown in Figure 48 phase-shift circuit 510C input and output voltage and come across the vectogram that concerns between the voltage on electric capacity etc.

As shown in figure 49, the voltage VC1 at the voltage VR1 at variable resistor 516 two ends and electric capacity 514 two ends, phase place is offset 90 ° mutually, and its voltage that carries out after the vectorial addition computing is become input voltage Ei.Therefore, under the situation only change frequency, the edge is shown in the circumference of the semicircle of Figure 49 in that input signal amplitude is constant, and the both end voltage VR1 of variable resistor 516 and the both end voltage VC1 of electric capacity 514 are changed.

And, carry out the voltage that the vector subtraction computing promptly deducts the voltage (the both end voltage Ei/2 of resistance 520) that is added on reversed input terminal the voltage from non-inverting input that is added to differential amplifier 512 (the both end voltage VR1 of variable resistor 516) and become differential voltage E0 '.This differential voltage E0 ' can be used in the semicircle that is shown in Figure 49, is starting point with its central point, and on the circumference that intersects with voltage VR1 and voltage VC1 a bit is that the vectogram of terminal point represents that its size equals the radius Ei/2 of semicircle.

The output voltage E0 of differential amplifier 512 becomes the voltage of multiplication factor after this differential voltage E0 ' is amplified with regulation.And in above-mentioned phase-shift circuit 510C, output voltage E0 does not depend on the frequency of input signal and is constant that it carries out work as all pass circuit.

And, as shown in Figure 49, because voltage VR1 and voltage VC1 intersect at a right angle on circumference, so the phase difference between input voltage Ei and the voltage VR1, change to ∞ with frequencies omega from 0, go up in hour hands rotation direction (phase delay direction) as benchmark with input voltage Ei and change to 360 ° from 270 °.And all amount of phase shift φ 9 of phase-shift circuit 510C change to 360 ° corresponding to frequency from 180 °.

Equally, be the pie graph of extracting the phase-shift circuit 530C of the back level be shown in Figure 47 out shown in Figure 50.The phase-shift circuit 530C that is shown in the back level of this figure comprises: with the multiplication factor of regulation amplify the differential voltage of 2 inputs and output differential amplifier 532, make the variable resistor 536 and the electric capacity 534 of non-inverting input that is input to differential amplifier 532 behind the signal phase displacement ormal weight that is input to input 142 and do not change the signal phase that is input to input 142, is this voltage level dividing potential drop about 1/2, is input to the resistance 538 and 540 of the reversed input terminal of differential amplifier 532.

If to the AC signal of the input 142 input regulation that is shown in Figure 50, just will be added on voltage Ei on the input 142 by resistance 538 and resistance 540, dividing potential drop is that about 1/2 voltage is added on the reversed input terminal of differential amplifier 532.

On the other hand, if input signal is input to input 142, the signal that then comes across on the contact of variable resistor 536 and electric capacity 534 is imported on non-inverting input of differential amplifier 532.Because input signal is input to an end of the RC circuit that is made of variable resistor 536 and electric capacity 534, the signal voltage behind the phase of input signals displacement ormal weight is applied on non-inverting input of differential amplifier 532 by this RC circuit.Like this, differential amplifier 532 is just exported and has been amplified the signal of the voltage difference that is added on 2 input terminals with the regulation multiplication factor.

Figure 51 is the input and output voltage of expression phase-shift circuit 530C and comes across the vectogram that concerns between the voltage on the electric capacity etc.

Shown in Figure 51, the voltage VR2 at the voltage VC2 at electric capacity 534 two ends and variable resistor 536 two ends, phase place is offset 90 ° mutually, and its voltage that carries out after the vectorial addition computing is become input voltage Ei.Therefore, under the situation only change frequency, the edge is shown in the circumference of the semicircle of Figure 51 in that input signal amplitude is constant, and the both end voltage VC2 of electric capacity 534 and the both end voltage VR2 of variable resistor 536 are changed.

And, carry out the voltage that the vector subtraction computing promptly deducts the voltage (the both end voltage Ei/2 of resistance 540) that is added on reversed input terminal the voltage from non-inverting input that is added to differential amplifier 532 (the both end voltage VC2 of electric capacity 534) and become differential voltage E0 '.This differential voltage E0 ' can be used in the semicircle that is shown in Figure 51, is starting point with its central point, and on the circumference that intersects with voltage VC2 and voltage VR2 a bit is that the vectogram of terminal point represents that its size equals the radius Ei/2 of semicircle.

The output voltage E0 of differential amplifier 532 becomes the voltage of multiplication factor after this differential voltage E0 ' is amplified with regulation.Therefore, in above-mentioned phase-shift circuit 530C, output voltage E0 does not depend on the frequency of input signal and is constant, carries out work as all pass circuit.

And, by Figure 51 as can be known,,, change to 90 ° on circumference from 0 ° so the phase difference between input voltage Ei and the voltage VC2 changes to ∞ with frequencies omega from 0 because voltage VC2 and voltage VR2 intersect at a right angle.And all amount of phase shift φ 10 of phase-shift circuit 530C change to 180 ° corresponding to frequency from 0 °.

Like this, in 2 phase- shift circuit 510C, 530C, make the phase-shifts ormal weight respectively, shown in Figure 49 and Figure 51, pass through all of 2 phase- shift circuit 510C, 530C in the frequency of regulation, output total amount of phase shift is 360 ° a signal.

And, the output of the phase-shift circuit 530C of back level, be removed from the output of lead-out terminal 192 as tuning circuit 1J, the signal that passes through bleeder circuit 160 feeds back to the output of this phase-shift circuit 530C input one side of non-reversed-phase circuit 550 through feedback resistance 170 simultaneously.Then, the signal of this feedback and the signal that is transfused to through input resistance 174 are carried out add operation, the signal after this add operation is input to the phase-shift circuit 510C of prime through non-reversed-phase circuit 550.

And, by means of the gain separately of adjusting 2 phase- shift circuit 510C, 530C, compensation reaches the loss that produces because of the decay that 2 phase- shift circuit 510C, 530C being shown in Figure 47 and bleeder circuit 160 produce in feedback circuit, and the circuit gain that tuning circuit is all is set at below 1.In addition, also can in non-reversed-phase circuit 550, keep the gain more than 1, and adjust this value, and not adjust the gain of phase- shift circuit 510C, 530C.

And, because take out the output that is input to the phase-shift circuit 530C before the bleeder circuit 160 from the lead-out terminal 192 of tuning circuit 1J, so tuning circuit 1J self can keep gain, can with tuning work while amplifying signal amplitude.

Also have, in being shown in the tuning circuit of Figure 47,, can also saving bleeder circuit 160, and the output of phase-shift circuit 530C is directly fed back to the higher level not needing to amplify under the situation of work.Perhaps the resistance value of the resistance 162 in the bleeder circuit 160 being made extremely little value and sets voltage ratio is 1.[the 13rd variation of tuning circuit]

Comprise that the RC circuit has constituted each phase- shift circuit 510C, 530C though be shown in the tuning circuit 1J of Figure 47, also can constitute tuning circuit with the phase-shift circuit that the RC circuit is replaced as the LR circuit that constitutes by resistance and inductance.

Figure 52 is the another kind of structural circuit figure that expression contains the phase-shift circuit of LR circuit, and shows the structure of the prime phase-shift circuit 510C that can be replaced into the tuning circuit 1J that is shown in Figure 47.The phase-shift circuit 510L that is shown in this figure has a RC circuit that is made of electric capacity 514 and variable resistor 516 that the phase-shift circuit 510C that is shown in Figure 48 is interior and is replaced as the LR circuit that is made of variable resistor 516 and inductance 517.In addition, the electric capacity 519 that is connected in series with inductance 517 is used for the stopping direct current electric current, and its impedance is decided extremely for a short time under operating frequency, promptly has huge electrostatic capacitance amount.

Figure 53 is the input and output voltage of expression phase-shift circuit 510L and comes across the vectogram that concerns between the voltage on the inductance etc.The time constant of the LR circuit that is made of variable resistor 516 and inductance 517 when hypothesis is T ₁(resistance value of establishing variable resistor 516 is R, and the inductance of inductance 517 is L, then T ₁=L/R) time, be shown in the amount of phase shift φ 11 of the phase-shift circuit 510L of this figure, identical with the φ 1 of above-mentioned (6) formula.

Figure 54 is the another kind of structural circuit figure that expression contains the phase-shift circuit of LR circuit, and shows the structure of the phase-shift circuit 530C of the back level that can be replaced into the tuning circuit 1J that is shown in Figure 47.The phase-shift circuit 530L that is shown in this figure has a RC circuit that is made of variable resistor 536 and electric capacity 534 that the phase-shift circuit 530C that is shown in Figure 50 is interior and is replaced as the LR circuit that is made of inductance 537 and variable resistor 536.In addition, the electric capacity 539 that is connected in series with inductance 537 is used for the stopping direct current electric current, and its impedance is established extremely for a short time under operating frequency, promptly has huge electrostatic capacitance amount.

Figure 55 is the input and output voltage of expression phase-shift circuit 530L and comes across the vectogram that concerns between the voltage on the inductance etc.The time constant of supposing the LR circuit that is made of inductance 537 and variable resistor 536 is T ₂(inductance of establishing inductance 537 is L, and the resistance value of variable resistor 536 is R, then T ₂=L/R) time, be shown in the amount of phase shift φ 12 of the phase-shift circuit 510L of this figure, identical with the φ 2 of above-mentioned (7) formula.

In addition, be shown in phase-shift circuit 510c, the 530c of Figure 47 at handle, be replaced as respectively under the situation of phase-shift circuit 510L that is shown in Figure 52 and the phase-shift circuit 530L that is shown in Figure 54, because changing in the opposite direction of each amount of phase shift when grid voltage of the FET that forms variable resistor 536 is changed, so must also be replaced as the EX-OR door 33 in the phase difference detecting circuit 3 that is shown in Figure 13 EX-NOR (XNOR) door, and need equal exchange to be shown in any 2 inputs of voltage comparator 31,32 of Figure 13, the change direction of control voltage is turned around.

Like this, be shown in the phase-shift circuit 510L and the phase-shift circuit 530L that is shown in Figure 54 of Figure 52, respectively with the phase-shift circuit 510C that is shown in Figure 48 or Figure 50,530C equivalence, in being shown in the tuning circuit 1J of Figure 47, can be replaced as the phase-shift circuit 510L that is shown in Figure 52 to the phase-shift circuit 510C of prime respectively, the phase-shift circuit 530C of back level is replaced as the phase-shift circuit 530L that is shown in Figure 54.In that both are replaced as under the situation of phase-shift circuit 510L, 530L 2 phase- shift circuit 510C, 530C, adopt to make all integrated ways of tuning circuit, make the tuned frequency high frequencyization easily.[the 14th variation of tuning circuit]

Though be shown in 2 phase-shift circuits that the tuning circuit 1J of Figure 47 comprises that mutual phase shift direction is different, also 2 phase-shift circuits that structure is identical basically can have been combined and constitute tuning circuit.

Figure 56 is the another kind of forming circuit figure of expression tuning circuit.The tuning circuit 1K that is shown in this figure comprises: the negative circuit 580 of the anti-phase output of phase place that makes the AC signal of input, employing makes the way of the phase-shifts ormal weight of the AC signal of input respectively, 2 phase-shift circuit 510C that add up to 180 ° of phase shifts in the frequency of regulation, the bleeder circuit 160 that constitutes by the resistance 162 and 164 of the back level of the phase-shift circuit 510C that is located at back level, respectively through feedback resistance 170 and input resistance 174, with the ratio of regulation to the dividing potential drop output (feedback signal) of bleeder circuit 160 be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

The detailed formation of 2 phase-shift circuit 510C and the phase relation of input/output signal are illustrated with Figure 48 and Figure 49, and in the frequency of regulation, all total amount of phase shift of 2 phase-shift circuit 510C are 180 °.

And the negative circuit 580 that is connected in the prime of 2 phase-shift circuit 510C is the anti-phase circuit of phase place that make input exchange signal, for example, and by making earthed-emitter circuit and source ground circuit or realizing by operational amplifier and resistor group circuit altogether.

Like this, the frequency in regulation makes 180 ° of phase-shifts by means of 2 phase-shift circuit 510C, and then makes phase place anti-phase by means of the negative circuit 580 that is connected in its prime, and all total amount of phase shift of these 3 circuit are 360 °.

And, the output of the phase-shift circuit 510C of back level, from the output that lead-out terminal 192 takes out as tuning circuit 1K, the signal that passes through bleeder circuit 160 is through feedback resistance 170 simultaneously, and the output of the phase-shift circuit 510C of level feeds back to input one side of negative circuit 580 after making.And, carry out add operation to this feedback signal with through the input signal of input resistance 174, and the signal that this add operation obtains is input in the negative circuit 580.

Like this, make the output of bleeder circuit 160 feed back to input one side of negative circuit 580 through feedback resistance 170, through the signal plus of input resistance 174 input in this feedback signal, adopt the gain of adjusting 2 phase-shift circuit 510C simultaneously, the way of the loss that compensates bleeder circuit 160 and produce in the coupling part of feedback resistance 170 and input resistance 174 etc. can be carried out and same tuning work and the amplification work of tuning circuit 1J that is shown in Figure 47.In addition, also can replace adjusting the gain of phase-shift circuit 510C to adjust the gain of negative circuit 580.

In addition, in being shown in the tuning circuit 1K of Figure 56,, also can save bleeder circuit 160, the output of phase-shift circuit 510C is directly fed back to prime one side not needing to amplify under the situation of work.Perhaps, also can make extremely little value to the resistance value of the resistance 162 in the bleeder circuit 160, setting voltage ratio is 1.[the 15th variation of tuning circuit]

Figure 57 is the circuit diagram of another variation of expression tuning circuit, and is opposite with Figure 56, and its formation comprises the phase-shift circuit 530C of the back level that is shown in Figure 47.

The tuning circuit 1L that is shown in Figure 57 comprises: adopt the phase place of the AC signal that makes input respectively to carry out the way that ormal weight is shifted, frequency in regulation, add up to 2 phase-shift circuit 530C of 180 ° of phase shifts, again the phase-shift circuit 530c phase of output signal of counter-rotating back level negative circuit 580, with the ratio of regulation respectively through feedback resistance 170 and input resistance 174, to from the signal (feedback signal) of negative circuit 580 outputs be input to the add circuit that the signal (input signal) of input terminal 190 carries out add operation.

The detailed formation of each phase-shift circuit 530c and the phase relation of input and output describe with Figure 50 and Figure 51.The time constant of for example establishing the RC circuit that is made of electric capacity 534 and variable resistor 536 is T ₂, at ω=1/T ₂The amount of phase shift φ 10 of frequency be 90 ° of hour hands rotation directions (phase delay direction).Therefore, in the frequency of regulation, all total amount of phase shift of 2 phase-shift circuit 530C are 180 °.

Like this, even use under the situation of 2 above-mentioned phase-shift circuit 530C, in the frequency of regulation, by means of 2 phase-shift circuit 530c, make 180 ° of phase-shifts, and then by the negative circuit 580 that is connected in its prime, make phase place anti-phase, all total amount of phase shift of these 3 circuit are 360 °.

Therefore, above-mentioned tuning circuit 1L, make the output of bleeder circuit 160 feed back to input one side of negative circuit 580 through feedback resistance 170, and the signal through input resistance 174 input is carried out add operation be added on this feedback signal, adjust the gain of 2 phase-shift circuit 530C simultaneously, the loss that compensation produces on the coupling part of bleeder circuit 160 and feedback resistance 170 and input resistance 174 etc., and the circuit gain of setting feedback circuit is below 1, in view of the above, can carry out and same tuning work and the amplification work of tuning circuit 1K that is shown in Figure 56.

Also have, be shown in tuning circuit 1K, the 1L of Figure 56 and Figure 57, though cascade the inner phase-shift circuit that contains the RC circuit, also can make and make the formation that contains the LR circuit in both phase-shift circuit inside.

Specifically, in being shown in the tuning circuit 1K of Figure 56, also can be replaced as the phase-shift circuit 510L that is shown in Figure 52 to 2 phase-shift circuit 510C.And, in being shown in the tuning circuit 1L of Figure 57, also can be replaced as the phase-shift circuit 530L that is shown in Figure 54 to 2 phase-shift circuit 530C.

But, the phase-shift circuit that contains the RC circuit is being replaced as under the situation of the phase-shift circuit that contains the LR circuit, because changing in the opposite direction of each amount of phase shift when gate voltage of the FET that forms variable resistor 116 and 136 is changed, so must also be replaced as the EX-OR door 33 in the phase difference detecting circuit 3 that is shown in Figure 13 EX-NOR (XNOR) door, and equal exchange is shown in any 2 inputs of voltage comparator 31,32 of Figure 13, and the change direction of control voltage is turned around.

But above-mentioned various tuning circuit 1J, 1K and 1L etc., constitute by non-reversed-phase circuit and 2 phase-shift circuits or negative circuit and 2 phase-shift circuits, and make in the frequency of regulation all by means of 3 circuit that couple together that to add up to amount of phase shift be 360 °, the tuning work of stipulating.Therefore,,, or, the degree of freedom is to a certain degree arranged all, can determine the connecting circuit order as required with which type of above-mentioned 3 circuit that are linked in sequence then no matter in 2 phase-shift circuits that prime is used which if only be conceived to amount of phase shift.

In each above-mentioned tuning circuit,, also can only be replaced as the phase-shift circuit that contains the LR circuit to any phase-shift circuit among 2 phase-shift circuits of cascade in that the phase-shift circuit that contains the RC circuit is replaced as under the situation of the phase-shift circuit that contains the LR circuit.But, in the case, since the controlling party of the resistance value of the variable resistor 116 in the phase-shift circuit of prime to the phase-shift circuit of back level in the controlling party of resistance value of variable resistor 136 to opposite, so need modification to make some circuit of the anti-phase grade of distributor 5 output levels that is shown in Figure 13.Like this, the phase-shift circuit that contains the RC circuit and the phase-shift circuit that contains the LR circuit formation tuning circuit that cascades up, making under all integrated situations of tuning circuit, prevent to produce the change of tuned frequency because of variations in temperature, promptly can have so-called temperature compensation function.

In above-mentioned each tuning circuit, detected the phase difference between the input/output signal of back level phase-shift circuit, yet also can detect the phase difference between the input/output signal of prime phase-shift circuit.Just, in the case, because and the situation ratio of the phase difference between the input/output signal of detection back level phase-shift circuit, the change direction changeabout direction of amount of phase shift is so must wait the modification of making on some circuit to the EX-OR door 33 in the phase difference detecting circuit 3 that is shown in Figure 13 also is replaced as EX-NOR (XNOR) door.[J, other variation]

At the various mechanical tuning devices shown in Fig. 1 or Figure 20 etc., the FET of usefulness junction type forms the variable resistor 116 of 2 phase-shift circuits that constitute tuning circuit, yet, also can form variable resistor with other device.

Tuning circuit 1M shown in Figure 58 has been replaced as the variable resistor 115,135 that the FET with the MOS type forms to the variable resistor in the phase-shift circuit 110c, the 130c that are shown in Fig. 3 116,136 respectively.Like this, also can be the raceway groove that between the source-drain electrode of the FET of MOS type, forms as resistive element.At this moment, the control voltage that is added on the grid by change just can change the channel resistance of this FET, so can arbitrarily change the tuned frequency of tuning circuit 1 in certain limit.

And, above-mentioned employings such as phase-shift circuit 110c make the resistance change of variable resistor 116 grades that are connected in series with electric capacity 114 grades and way that amount of phase shift is changed, make whole tuned frequency change, but also can be by making the electrostatic capacitance change of electric capacity 114 grades, and make whole tuned frequency change.

Figure 59 is that expression adopts the way of the electrostatic capacitance change make electric capacity 114 grades to make the pie graph of the tuning circuit that whole tuned frequency changes.The tuning circuit 1N that is shown in this figure serves as that the basis constitutes with phase-shift circuit 110c, the 130c that is shown in Fig. 2 mainly, but also can serve as that the basis constitutes with the various phase-shift circuits that are shown in Figure 29 and Figure 46 etc.

In Figure 59, with the electric capacity the 128, the 148th that variable capacitance diode 127,147 is connected in series, be used for the stopping direct current electric current when adding reverse bias to variable capacitance diode, under operating frequency its impedance minimum, promptly have big electrostatic capacitance.

In addition, in being shown in the tuning circuit of Figure 59, though with variable capacitance diode as variable-capacitance element, also can be with according to the control voltage that is added on the grid, the FET that its grid capacitance can change in certain limit is as variable-capacitance element.

Figure 60 is the circuit diagram of the example of expression when utilizing device except that FET as the interior variable resistor of the phase-shift circuit 110c, the 130c that are shown in Fig. 2.

Be shown in the phase-shift circuit 110C of Figure 60 and " have the structure that the variable resistor 116 that will form with the FET in the phase-shift circuit 110c that is shown in Fig. 2 is replaced as the CdS photoelectrical coupler 177 that is made of CdS photoelectric sensor and light-emitting diode.The CdS photoelectric sensor that comprises 177 li of CdS photoelectrical couplers, the more little characteristic of the many more resistance values of luminous quantity with light-emitting diode, thus can such CdS photoelectrical coupler 177 as the Control current of coming according to the outside the modifiable variable resistor of resistance value.

Equally, be shown in the phase-shift circuit 130C of Figure 60 and " have the structure that the variable resistor 136 that will form with the FET in the phase-shift circuit 130c that is shown in Fig. 2 is replaced as the CdS photoelectrical coupler 179 that is made of CdS photoelectric sensor and light-emitting diode.

The control voltage generating circuit 4B that is shown in Figure 60 has partly makes control voltage generating circuit 4 deformed configurations that are shown in Figure 13, and it is different with control voltage generating circuit 4 to remove the biasing circuit this point that comprises variable resistor 42 and resistance 43 formations.

And, be shown in the voltage-to-current translation circuit 200 of Figure 60, comprise through resistance 202 this variable resistor 206 that is input to the operational amplifier 204 of reversed input terminal and is used to produce variable bias voltage as the control voltage of control voltage generating circuit 4B output.

Operational amplifier 204,2 light-emitting diodes in the above-mentioned photoelectrical coupler 177,179 that between its lead-out terminal and reversed input terminal, is connected in series, and the sub-ground connection of its non-inverting input.Therefore, after the output voltage of control voltage generating circuit 4B is determined, just the resistance ratio by resistance 202 and variable resistor 206 determines predetermined electric current to flow to each light-emitting diode in the photoelectrical coupler 177,179, and the CdS photoelectric sensor paired with this light-emitting diode has certain resistance value of respective leds luminous quantity.

Therefore, adopt the way of the output voltage that reduces control voltage generating circuit 4B, to reduce to flow to the current value in the light-emitting diode luminous quantity is tailed off, the resistance value that the CdS photoelectric sensor is had uprises, and the tuned frequency that is shown in the tuning circuit of Figure 60 reduces.On the contrary, adopt the way of the output voltage of the control voltage generating circuit 4B that raises, the current value that flows in the light-emitting diode with increase increases luminous quantity, and the resistance value that the CdS photoelectric sensor is had reduces, and the tuned frequency that is shown in the tuning circuit 1 of Figure 60 uprises.This relation is the same with the relation of control voltage with the variable resistor that forms with above-mentioned FET, can the mechanical tuning device of tuning circuit 1 be overlapped with the frequency of input signal with identical control order.

Like this, even photoelectrical coupler 177,179 is used as variable resistor, also can constitute the structure of the mechanical tuning device of realizing the foregoing description.With photoelectrical coupler 177,179 as variable-resistance situation under because be not to obtain constant resistance value, so have the advantage of few tuning output that can easily obtain distorting by this variable-resistance both end voltage etc.But, owing to can not all be integrated in the whole tuning circuit 1 that contains photoelectrical coupler 177,179 on the Semiconductor substrate, so photoelectrical coupler 177,179 connects discrete component with regard to handy connecting line etc.

And, in above-mentioned tuning circuit, though can adopt by the way that constitutes tuning circuit 1 with phase-shift circuit 110c, the 130c of operational amplifier, realize the tuning circuit of high stability, but when resembling the such occupation mode of phase-shift circuit 110c, the 130c of present embodiment, bias voltage or voltage gain since require so not high, so can replace operational amplifier in each phase-shift circuit with the differential amplifier that the regulation multiplication factor is arranged.

Figure 61 is a circuit diagram of having extracted the necessary part of phase-shift circuit work in the structure of operational amplifier out, and whole conduct has the differential amplifier of regulation multiplication factor and works.The differential amplifier that is shown in this figure by the differential input section 100 that constitutes with FET, to this differential input section supply with the constant-current circuit 102 of constant current, the output amplifier 106 of supplying with the biasing circuit 104 of regulation bias voltage and being connected to differential input section to constant-current circuit constitutes.As shown in the drawing, save the multistage amplifying circuit that is used to obtain be included in the voltage gain of actual operational amplifier, simplified the structure of differential amplifier, can obtain broadband.Like this,, can improve the upper limit of operating frequency, so can improve the upper limit of various tuning circuits 1 tuned frequency that constitutes with this differential amplifier by circuit is simplified.

Below be illustrated in the invention put down in writing in each claim and the corresponding relation of accompanying drawing, and the corresponding relation of the parts of putting down in writing in inscape of in each claim, being put down in writing and the specification.

(1) phase difference detecting circuit of claim 6, corresponding with the phase difference detecting circuit 3 of Figure 13, each inscape corresponding as follows.

The 1st voltage comparator → voltage comparator 31;

The 2nd voltage comparator → voltage comparator 32;

The output signal of the 2nd square-wave signal device → voltage comparator 31 (Figure 14 (C));

The output signal of the 3rd square-wave signal device → voltage comparator 31 (Figure 14 (D));

Square wave synthesizer → EX-OR door 33.

(2) the 1st, 2,3 resistance and Figure 33 in claim 10, the resistance in 34,35 corresponding as follows.

The 2nd resistance → resistance 118,138;

The 3rd resistance → resistance 120,140;

The 1st resistance → variable resistor 116,136.

(3) tuning circuit of claim 18, corresponding to Fig. 2,25,27.The 1st, 2,3 resistance in claim 18 and the resistance of Ge Tu corresponding as follows.

The 2nd resistance → resistance 118,138;

The 3rd resistance → resistance 120,140;

The 1st resistance → variable resistor 116, resistance 136.

(4) tuning circuit of claim 26, corresponding to Figure 29,30,31.The 1st～4 resistance in claim 26 and the resistance of Ge Tu corresponding as follows.

The 2nd resistance → resistance 118 ', 138 ';

The 3rd resistance → resistance 120 ', 140 ';

The 4th resistance → resistance 119,139;

The 1st resistance → variable resistor 116, resistance 136.

(5) tuning circuit of claim 34, corresponding to Figure 36,41,43.The resistance of the 1st resistance in claim 34 etc. and each figure etc. corresponding as follows.

The 1st resistance → variable resistor 416, resistance 436;

Converting means → FET412, resistance 418,420; Or FET432, resistance 438,440.

(6) tuning circuit of claim 40, corresponding to Figure 45,46.The corresponding relation of the resistance of the 1st resistance in claim 40 etc. and each figure etc. is as follows.

The 1st resistance → variable resistor 416, resistance 436;

Converting means → FET412, resistance 418,420; Or FET432, resistance 438,440.

(7) tuning circuit of claim 46, corresponding to Figure 47,52,54.The corresponding relation of the resistance of the 1st resistance in claim 46 etc. and each figure etc. is as follows.

The 2nd resistance → resistance 518,538;

The 3rd resistance → resistance 520,540;

The 1st resistance → variable resistor 516, resistance 536.

(8) tuning circuit of claim 52 is corresponding to each figure of aforesaid right requirement 10,18,26,34,40,46.Input impedance element in the claim 52 and the corresponding relation of feedback impedance element and Ge Tu are as follows.

Input impedance element → resistance 174;

Feedback impedance element → resistance 170.

The present invention is not limited to above various form of implementation, can implement various distortion in aim scope of the present invention.

For example, the tuning circuit 1 of detailed structure has been shown at Fig. 2, be as the feedback impedance element feedback resistance 170, and with input resistance 174 as the input impedance element, since be not input to separately the phase relation of the signal of element to carry out add operation good but do not change, so also can replace resistance to form feedback impedance element and input impedance element, or combined resistance or electric capacity etc. be adjusted the real part of impedance and the ratio of imaginary part simultaneously with electric capacity.

And, at least a resistance among feedback resistance 170 and the input resistance 174 is constituted with variable resistor, and make the tuning bandwidth of tuning circuit 1 etc. variable.

And in the phase-shift circuit 110c that is shown in Fig. 2 etc., though constituted variable resistor 116 with 1 FET, also can be connected in parallel p channel fet and n channel fet constitute 1 variable resistor.Like this, adopt 2 FET of combination to constitute variable-resistance way, because of improving the nonlinear area of FET, so can reduce the distortion of tuning output.

As described above, tuning control system of the present invention, because the tuned frequency to tuning circuit carries out FEEDBACK CONTROL, makes the frequency input signal of phase-shift circuit and the deviation of tuned frequency eliminate, so tuned frequency is overlapped with the frequency of input signal.Therefore, make under the integrated situation of whole mechanical tuning device,, also eliminated the discrete of tuning characteristic even do not overlap in each frequency characteristic of the chip of making.And, even the device constant change of each device of reason tuned frequencies such as Yin Wendu, because tuned frequency is constant, so also be suitable for integrated.

Claims (53)

1, a kind of tuning control system has:

2 phase-shift circuits of wildcard-filter style that comprise cascade, feed back to input one side of the above-mentioned phase-shift circuit of prime as feedback signal with the output of the above-mentioned phase-shift circuit that makes back level, simultaneously above-mentioned feedback signal and input signal are carried out add operation and be input to add circuit in the above-mentioned phase-shift circuit of prime, and tuning circuit that the signal near the assigned frequency is passed through; And

It is characterized in that also having, when the frequency signal near handle has the afore mentioned rules frequency is input to and goes in the above-mentioned tuning circuit, according to the phase difference between the input/output signal of a phase-shift circuit that in above-mentioned tuning circuit, contains, the frequency control circuit that the tuned frequency of above-mentioned tuning circuit is overlapped with the frequency of the input signal of above-mentioned tuning circuit.

2, tuning control system according to claim 1 is characterized in that: each of 2 phase-shift circuits that contain in the above-mentioned tuning circuit, contain the series circuit that time constant can change;

The said frequencies control circuit, under the frequency input signal of the above-mentioned tuning circuit situation different with the tuned frequency of above-mentioned tuning circuit, make the time constant of both sides' above-mentioned series circuit keep the mutually equilateral mutually amount of phase shift of each phase-shift circuit that makes to change by the limit, the tuned frequency of above-mentioned tuning circuit is overlapped with the frequency input signal of above-mentioned tuning circuit.

3, tuning control system according to claim 2 is characterized in that: each of above-mentioned series circuit comprises reactance component and the 1st resistance that electric capacity or inductance form;

Control signal by means of from the output of said frequencies control circuit can change the time constant of both sides' above-mentioned series circuit;

The said frequencies control circuit is exported above-mentioned control signal, makes the tuned frequency of above-mentioned tuning circuit overlap with the frequency input signal of tuning circuit.

4, tuning control system according to claim 3, it is characterized in that: the said frequencies control circuit, when the phase difference of the input/output signal of any the above-mentioned phase-shift circuit that contains in above-mentioned tuning circuit has departed from 90 °, change by the time constant that makes the above-mentioned series circuit that contains in each of above-mentioned 2 phase-shift circuits, the phase difference of the input/output signal of an above-mentioned phase-shift circuit is controlled at 90 °.

5, tuning control system according to claim 4 is characterized in that: the said frequencies control circuit has:

According to the phase difference of the input/output signal of any phase-shift circuit that is contained in above-mentioned tuning circuit, the phase difference detecting circuit of the 1st square-wave signal that output duty cycle changes; And

By making above-mentioned the 1st square-wave signal level and smooth,, produce the control voltage generating circuit of the control voltage of voltage level change according to the duty ratio of above-mentioned the 1st square-wave signal; Described control voltage is exported as described control signal.

6, tuning control system according to claim 5 is characterized in that: above-mentioned phase difference detecting circuit has:

The 1st voltage comparator of the 2nd square-wave signal that output is synchronous with being contained in the input signal of any phase-shift circuit in the above-mentioned tuning circuit,

The 2nd voltage comparator of the 3rd square-wave signal that the output signal of an output and an above-mentioned phase-shift circuit is synchronous; And

Synthetic the above-mentioned the 2nd and the 3rd square-wave signal is also exported the square wave synthesizer of above-mentioned the 1st square-wave signal.

7, tuning control system according to claim 6 is characterized in that: above-mentioned square wave synthesizer comprises the gate of carrying out XOR with the above-mentioned the 2nd and the 3rd square-wave signal, and the output of this gate as the 1st square-wave signal.

8, tuning control system according to claim 6, it is characterized in that: above-mentioned square wave synthesizer comprises the voltage level according to control terminal, make the signal that is input to input terminal by or the three condition buffer that cuts off, any of the above-mentioned the 2nd and the 3rd square-wave signal is input to above-mentioned control terminal, another is input to above-mentioned input terminal, the output of above-mentioned three condition buffer as above-mentioned the 1st square-wave signal.

9, tuning control system according to claim 5 is characterized in that: above-mentioned control voltage generating circuit has to be made from the level and smooth smoothing circuit of above-mentioned the 1st square-wave signal of above-mentioned phase difference detecting circuit output and amplifies the output voltage of above-mentioned smoothing circuit and export the amplifier of above-mentioned control voltage.

10, tuning control system according to claim 3, it is characterized in that: at least one of above-mentioned 2 phase-shift circuits that is contained in above-mentioned tuning circuit comprises an end of the 2nd resistance is connected to the differential amplifier of inverting input through above-mentioned the 2nd resistance input exchange signal, and be connected the 3rd resistance between the reversed input terminal of the output of above-mentioned differential amplifier and above-mentioned differential amplifier, above-mentioned series circuit is connected to the other end of above-mentioned the 2nd resistance, and above-mentioned the 1st resistance that constitutes above-mentioned series circuit and the coupling part of above-mentioned reactance component are connected on non-inverting input of above-mentioned differential amplifier.

11, tuning control system according to claim 10 is characterized in that: above-mentioned tuning circuit has the phase place of the AC signal that does not change input and the non-reversed-phase circuit exported; And above-mentioned non-reversed-phase circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

It is near 360 ° the frequency signal that the integral body that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade adds up to amount of phase shift.

12, tuning control system according to claim 10 is characterized in that: above-mentioned tuning circuit has the anti-phase and negative circuit of output of the phase place of the AC signal that makes input; And above-mentioned negative circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

It is near 180 ° the frequency signal that the integral body that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade adds up to amount of phase shift.

13, tuning control system according to claim 10 is characterized in that: the prime at 2 phase-shift circuits of above-mentioned cascade is inserted the follow circuit that is formed by transistor.

14, tuning control system according to claim 10 is characterized in that: the part of the feedback circuit that forms at 2 phase-shift circuit by above-mentioned cascade is inserted bleeder circuit;

Above-mentioned tuning circuit is exported the AC signal that is input in the above-mentioned bleeder circuit as harmonic ringing.

15, tuning control system according to claim 10, it is characterized in that: form above-mentioned the 1st resistance in the above-mentioned series circuit by variable resistor, and the voltage level according to above-mentioned control signal changes above-mentioned variable-resistance resistance value, makes the tuned frequency of above-mentioned tuning circuit variable.

16, tuning control system according to claim 10 is characterized in that: above-mentioned differential amplifier is an operational amplifier.

17, tuning control system according to claim 10 is characterized in that: the whole composed component that forms on Semiconductor substrate.

18, tuning control system according to claim 3, it is characterized in that: at least one that is contained in above-mentioned 2 phase-shift circuits in the above-mentioned tuning circuit comprises: an end of the 2nd resistance is connected to reversed input terminal and through the differential amplifier of above-mentioned the 2nd resistance input exchange signal, be connected in the 1st bleeder circuit of the lead-out terminal of above-mentioned differential amplifier, and be connected to the 3rd resistance between the reversed input terminal of the output of above-mentioned the 1st bleeder circuit and above-mentioned differential amplifier, above-mentioned series circuit is connected to the other end of above-mentioned the 2nd resistance, and above-mentioned the 1st resistance that constitutes above-mentioned series circuit and the coupling part of above-mentioned reactance device are connected on non-inverting input of above-mentioned differential amplifier.

19, tuning control system according to claim 18 is characterized in that: above-mentioned tuning circuit has the phase place of the AC signal that does not change input and the non-reversed-phase circuit exported; And above-mentioned non-reversed-phase circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

It is near 360 ° the frequency signal that the integral body that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade adds up to amount of phase shift.

20, tuning control system according to claim 18 is characterized in that: above-mentioned tuning circuit has the anti-phase and negative circuit of output of the phase place of the AC signal that makes input; And above-mentioned negative circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

It is near 180 ° the frequency signal that the integral body that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade adds up to amount of phase shift.

21, tuning control system according to claim 18 is characterized in that: the prime at 2 phase-shift circuits of above-mentioned cascade is inserted the follow circuit that is formed by transistor.

22, tuning control system according to claim 18 is characterized in that: the part at the feedback circuit that forms with 2 of above-mentioned cascade phase-shift circuit is inserted the 2nd bleeder circuit;

Above-mentioned tuning circuit is exported the AC signal that is input in above-mentioned the 2nd bleeder circuit as harmonic ringing.

23, tuning control system according to claim 18, it is characterized in that: form above-mentioned the 1st resistance in the above-mentioned series circuit by variable resistor, and the voltage level according to above-mentioned control signal changes above-mentioned variable-resistance resistance value, makes the tuned frequency of above-mentioned tuning circuit variable.

24, tuning control system according to claim 18 is characterized in that: above-mentioned differential amplifier is an operational amplifier.

25, tuning control system according to claim 18 is characterized in that: the whole composed component that forms on Semiconductor substrate.

26, tuning control system according to claim 3, it is characterized in that: at least one that is contained in above-mentioned 2 phase-shift circuits in the above-mentioned tuning circuit comprises: an end of the 2nd resistance is connected to reversed input terminal and through the differential amplifier of above-mentioned the 2nd resistance input exchange signal, be connected in the reversed input terminal of above-mentioned differential amplifier and the 3rd resistance between the lead-out terminal, and one end be connected to the reversed input terminal of above-mentioned differential amplifier and the 4th resistance of other end ground connection, above-mentioned series circuit is connected to the other end of above-mentioned the 2nd resistance, and above-mentioned the 1st resistance that constitutes above-mentioned series circuit and the coupling part of above-mentioned reactance device are connected on non-inverting input of above-mentioned differential amplifier.

27, tuning control system according to claim 26 is characterized in that: above-mentioned tuning circuit has the phase place of the AC signal that does not change input and the non-reversed-phase circuit exported; And above-mentioned non-reversed-phase circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

It is near 360 ° the frequency signal that the integral body that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade adds up to amount of phase shift.

28, tuning control system according to claim 26 is characterized in that: above-mentioned tuning circuit has the anti-phase and negative circuit of output of the phase place of the AC signal that makes input; And above-mentioned negative circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

It is near 180 ° the frequency signal that the integral body that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade adds up to amount of phase shift.

29, tuning control system according to claim 26 is characterized in that: the prime at 2 phase-shift circuits of above-mentioned cascade is inserted the follow circuit that is formed by transistor.

30, tuning control system according to claim 26 is characterized in that: the part at the feedback circuit that forms with 2 of above-mentioned cascade phase-shift circuit is inserted bleeder circuit;

Above-mentioned tuning circuit is exported the AC signal that is input in the above-mentioned bleeder circuit as harmonic ringing.

31, tuning control system according to claim 26, it is characterized in that: form above-mentioned the 1st resistance in the above-mentioned series circuit by variable resistor, and the voltage level according to above-mentioned control signal changes above-mentioned variable-resistance resistance value, so that the tuned frequency of above-mentioned tuning circuit is variable.

32, tuning control system according to claim 26 is characterized in that: above-mentioned differential amplifier is an operational amplifier.

33, tuning control system according to claim 26 is characterized in that: the whole composed component that forms on Semiconductor substrate.

34, tuning control system according to claim 3 is characterized in that: above-mentioned tuning circuit has the phase place of the AC signal that does not change input and the non-reversed-phase circuit exported; And above-mentioned non-reversed-phase circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

At least one of above-mentioned 2 phase-shift circuits comprises: the AC signal of having imported is transformed into homophase and anti-phase AC signal and the converting means of exporting, to use this converting means conversion the synthesizer that synthesizes through the other end of above-mentioned series circuit through an end of above-mentioned series circuit and another AC signal of an AC signal.

35, tuning control system according to claim 34 is characterized in that: all total amount of phase shift that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade are near the signal 360 ° the frequency.

36, tuning control system according to claim 34 is characterized in that: insert bleeder circuit in the part of the feedback circuit that 2 phase-shift circuits and above-mentioned noninverting input circuit with above-mentioned cascade form;

Above-mentioned tuning circuit makes the AC signal that is input in the above-mentioned bleeder circuit export as harmonic ringing.

37, tuning control system according to claim 34, it is characterized in that: the above-mentioned converting means in above-mentioned 2 phase-shift circuits comprises transistor, above-mentioned transistorized source electrode and drain electrode, or connect resistance value the 2nd resistance about equally on the emitter and collector respectively, to above-mentioned transistorized grid or base stage input exchange signal, and between above-mentioned transistorized source electrode and drain electrode or connect and compose the above-mentioned series circuit of above-mentioned synthesizer between emitter and the collector electrode.

38, tuning control system according to claim 34, it is characterized in that: form above-mentioned the 1st resistance in the above-mentioned series circuit by variable resistor, and the voltage level according to above-mentioned control signal changes above-mentioned variable-resistance resistance value, so that the tuned frequency of above-mentioned tuning circuit is variable.

39, tuning control system according to claim 34 is characterized in that: the whole composed component that forms on Semiconductor substrate.

40, tuning control system according to claim 3 is characterized in that: above-mentioned tuning circuit has the phase place of AC signal of counter-rotating input and the negative circuit exported; And above-mentioned negative circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

At least one of above-mentioned 2 phase-shift circuits comprises: the AC signal of having imported is transformed into homophase and anti-phase AC signal and the converting means of exporting, to use this converting means conversion an AC signal through an end of above-mentioned series circuit, the synthesizer that synthesizes through the other end of above-mentioned series circuit with another AC signal.

41, according to the described tuning control system of claim 40, it is characterized in that: it is near 180 ° the frequency signal that above-mentioned tuning circuit only adds up to amount of phase shift by the integral body by 2 phase-shift circuits of above-mentioned cascade.

42, according to the described tuning control system of claim 40, it is characterized in that: in the part of the feedback circuit that 2 phase-shift circuits and above-mentioned anti-phase input circuit with above-mentioned cascade form, insert bleeder circuit;

Above-mentioned tuning circuit makes the AC signal that is input in the above-mentioned bleeder circuit export as harmonic ringing.

43, according to the described tuning control system of claim 40, it is characterized in that: the above-mentioned converting means in above-mentioned 2 phase-shift circuits comprises transistor, above-mentioned transistorized source electrode and drain electrode, or connect resistance value the 2nd resistance about equally on the emitter and collector respectively, to above-mentioned transistorized grid or base stage input exchange signal, and between above-mentioned transistorized source electrode and drain electrode or connect and compose the above-mentioned series circuit of above-mentioned synthesizer between emitter and the collector electrode.

44, according to the described tuning control system of claim 40, it is characterized in that: form above-mentioned the 1st resistance in the above-mentioned series circuit by variable resistor, and the voltage level according to above-mentioned control signal changes above-mentioned variable-resistance resistance value, so that the tuned frequency of above-mentioned tuning circuit is variable.

45, according to the described tuning control system of claim 40, it is characterized in that: the whole composed component that forms on Semiconductor substrate.

46, tuning control system according to claim 3, it is characterized in that: at least one of above-mentioned 2 phase-shift circuits that comprise in above-mentioned tuning circuit comprises: with the 1st bleeder circuit of resistance value the 2nd and the 3rd resistance formation about equally, and the differential amplifier that differs from and make it to export between the current potential of the tie point of the above-mentioned reactance device of the output current potential that amplifies above-mentioned the 1st bleeder circuit with the multiplication factor of regulation and the above-mentioned series circuit of formation and above-mentioned the 1st resistance, and respectively AC signal is input to an end of above-mentioned the 1st bleeder circuit and above-mentioned series circuit.

47, according to the described tuning control system of claim 46, it is characterized in that: above-mentioned tuning circuit has the phase place of the AC signal that does not change input and the non-reversed-phase circuit exported; And above-mentioned non-reversed-phase circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

It is near 360 ° the frequency signal that the integral body that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade adds up to amount of phase shift.

48, according to the described tuning control system of claim 46, it is characterized in that: above-mentioned tuning circuit has the anti-phase and negative circuit of output of the phase place of the AC signal that makes input; And above-mentioned negative circuit is inserted in the part of the feedback circuit that 2 phase-shift circuits with above-mentioned cascade form;

All total amount of phase shift that above-mentioned tuning circuit only produces by 2 phase-shift circuits by above-mentioned cascade are near the signal 180 ° the frequency.

49, according to the described tuning control system of claim 46, it is characterized in that: in the part of the feedback circuit that 2 phase-shift circuit with above-mentioned cascade forms, insert the 2nd bleeder circuit;

Above-mentioned tuning circuit is exported the AC signal that is input in above-mentioned the 2nd bleeder circuit as harmonic ringing.

50, according to the described tuning control system of claim 46, it is characterized in that: form above-mentioned the 1st resistance in the above-mentioned series circuit by variable resistor, and the voltage level according to above-mentioned control signal changes above-mentioned variable-resistance resistance value, so that the tuned frequency of above-mentioned tuning circuit is variable.

51, according to the described tuning control system of claim 46, it is characterized in that: the whole composed component that forms on Semiconductor substrate.

52, tuning control system according to claim 3, it is characterized in that: above-mentioned tuning circuit comprises that input signal is input to impedance device on the end and feedback signal and is input to feedback impedance device on the end, above-mentioned add circuit with above-mentioned add circuit to carrying out add operation through the above-mentioned input signal of above-mentioned input impedance device input with through the above-mentioned feedback signal of above-mentioned feedback impedance device input.

53, according to the described tuning control system of claim 52, it is characterized in that:, the bandwidth of above-mentioned tuning circuit is changed by means of the device constant ratio that changes between above-mentioned input impedance device and the above-mentioned feedback impedance device.

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