CN110176860B - Boost converter with output current compensation branch - Google Patents
Boost converter with output current compensation branch Download PDFInfo
- Publication number
- CN110176860B CN110176860B CN201910527609.7A CN201910527609A CN110176860B CN 110176860 B CN110176860 B CN 110176860B CN 201910527609 A CN201910527609 A CN 201910527609A CN 110176860 B CN110176860 B CN 110176860B
- Authority
- CN
- China
- Prior art keywords
- inductor
- output current
- channel mos
- port
- current compensation
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
- 239000003990 capacitor Substances 0.000 claims abstract description 49
- 238000004146 energy storage Methods 0.000 claims abstract description 8
- 230000008878 coupling Effects 0.000 claims description 12
- 238000010168 coupling process Methods 0.000 claims description 12
- 238000005859 coupling reaction Methods 0.000 claims description 12
- 238000011217 control strategy Methods 0.000 claims description 3
- 230000001105 regulatory effect Effects 0.000 claims description 3
- 238000010586 diagram Methods 0.000 description 13
- 238000011084 recovery Methods 0.000 description 8
- 238000004088 simulation Methods 0.000 description 8
- 230000009286 beneficial effect Effects 0.000 description 6
- 238000010521 absorption reaction Methods 0.000 description 4
- 230000003071 parasitic effect Effects 0.000 description 4
- 230000007423 decrease Effects 0.000 description 3
- XAGFODPZIPBFFR-UHFFFAOYSA-N aluminium Chemical compound [Al] XAGFODPZIPBFFR-UHFFFAOYSA-N 0.000 description 2
- 229910052782 aluminium Inorganic materials 0.000 description 2
- 230000000694 effects Effects 0.000 description 2
- 230000005389 magnetism Effects 0.000 description 2
- 230000007547 defect Effects 0.000 description 1
- 230000002349 favourable effect Effects 0.000 description 1
- 230000001502 supplementing effect Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
- H02M1/143—Arrangements for reducing ripples from dc input or output using compensating arrangements
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/1557—Single ended primary inductor converters [SEPIC]
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The boost converter comprises an inductor L1, an N-channel MOS tube M1, a diode D1, a capacitor Co, an output current compensation branch and a controller, wherein when the N-channel MOS tube M1 is cut off, a part of current is separated from the inductor L1 through a port a of the output current compensation branch for energy storage; when the N channel MOS tube M1 is conducted, energy is released through the port b of the N channel MOS tube M1, and current is provided for the capacitor Co and the load RL; the controller adopts a soft switch controller, the switching state of the N-channel MOS tube M1 is controlled through the port g of the controller, and the working state of energy storage or release of the output current compensation branch is controlled through the port c of the controller. The invention has the characteristics of low output voltage ripple and high efficiency.
Description
Technical Field
The invention relates to a boost converter, in particular to a boost converter with an output current compensation branch, which not only has small output voltage ripple, but also can work in a soft switching state, and is suitable for low output voltage ripple and high-efficiency application occasions.
Background
The output current (i.e., the current flowing through the freewheeling diode to the output) of a conventional Boost converter is intermittent, which results in a large ripple in its output voltage. To obtain smaller output voltage ripple, it is common practice to increase the capacity of the output electrolytic capacitor or to increase the filter. However, the common aluminum electrolytic capacitor has poor tolerance to pulsating current, and the performance of the common aluminum electrolytic capacitor is seriously affected by temperature; common filters (e.g., LC filters) reduce the dynamic response speed and overall efficiency of the circuit.
Therefore, the output voltage ripple is improved by supplementing the output current without increasing the output electrolytic capacitance by introducing an output current compensation branch for the conventional Boost converter. Furthermore, a soft switch controller can be adopted, and the working mode of changing a hard switch into a soft switch is changed, so that the circuit efficiency is improved.
Disclosure of Invention
In order to overcome the defect of larger output voltage ripple of the traditional Boost converter, the invention provides a Boost converter with an output current compensation branch circuit, and aims to improve the output voltage ripple and simultaneously improve the efficiency.
The technical scheme adopted for solving the technical problems is as follows:
The boost converter comprises an inductor L1, an N-channel MOS tube M1, a diode D1, a capacitor Co, an output current compensation branch and a controller, wherein the current compensation branch is provided with a port a, a port b and a port c, the controller is provided with a port g and a port c, the positive end of a direct current power supply Vi is connected with one end of the inductor L1, the other end of the inductor L1 is simultaneously connected with the drain electrode of the N-channel MOS tube M1, the port a of the output current compensation branch and the anode of the diode D1, the cathode of the diode D1 is simultaneously connected with the port b of the output current compensation branch, one end of the capacitor Co and one end of a load RL, the other end of the load RL is simultaneously connected with the other end of the capacitor Co, the source electrode of the N-channel MOS tube M1 and the negative end of the direct current power supply Vi, the port c of the output current compensation branch is connected with the port c of the controller, and the port g of the controller is connected with the grid electrode of the N-channel MOS tube M1;
In the output current compensation branch, when the N-channel MOS tube M1 is cut off, a part of current is separated from the inductor L1 through a port a of the N-channel MOS tube M1 for energy storage; when the N channel MOS tube M1 is conducted, energy is released through the port b of the N channel MOS tube M1, and current is provided for the capacitor Co and the load RL;
In the controller, the switching state of the N-channel MOS tube M1 is controlled through the port g, and the working state of energy storage or release of the output current compensation branch is controlled through the port c.
Further, the first preferred scheme of the output current compensation branch circuit, the output current compensation branch circuit includes an inductor La1, an N-channel MOS tube Ma1 and a diode Da1, one end of the inductor La1 is connected with a port a of the output current compensation branch circuit, the other end of the inductor La1 is connected with a drain electrode of the N-channel MOS tube Ma1 and an anode electrode of the diode Da1 at the same time, a cathode electrode of the diode Da1 is connected with a port b of the output current compensation branch circuit, a source electrode of the N-channel MOS tube Ma1 is connected with a source electrode of the N-channel MOS tube M1, and a gate electrode of the N-channel MOS tube Ma1 is connected with a port c of the output current compensation branch circuit.
Or, the second preferred scheme of the output current compensation branch circuit, the output current compensation branch circuit includes an inductor Lb1, an inductor Lb2, an N-channel MOS tube Mb1 and a diode Db1, one end of the inductor Lb1 is connected with a port a of the output current compensation branch circuit, the other end of the inductor Lb1 is connected with a drain electrode of the N-channel MOS tube Mb1, a source electrode of the N-channel MOS tube Mb1 is simultaneously connected with a source electrode of the N-channel MOS tube M1 and one end of the inductor Lb2, the other end of the inductor Lb2 is connected with an anode of the diode Db1, a cathode of the diode Db1 is connected with a port b of the output current compensation branch circuit, a gate electrode of the N-channel MOS tube Mb1 is connected with a port c of the output current compensation branch circuit, the inductor Lb1 and the inductor Lb2 have a coupling relationship, and one end of the inductor Lb1 and one end of the inductor Lb2 are the same name. Considering that leakage inductance exists between the inductor Lb1 and the inductor Lb2, a voltage spike absorbing branch can be added, the voltage spike absorbing branch comprises a resistor Rb1, a capacitor Cb1 and a diode Db2, one end of the resistor Rb1 is simultaneously connected with one end of the inductor Lb1 and one end of the capacitor Cb1, the other end of the resistor Rb1 is simultaneously connected with the other end of the capacitor Cb1 and the cathode of the diode Db2, and the anode of the diode Db2 is connected with the other end of the inductor Lb 1. The second preferred version of the output current compensation branch has a wider output current compensation range than the first preferred version of the output current compensation branch due to the coupling inductances Lb1 and Lb 2.
Still alternatively, the third preferred solution of the output current compensation branch circuit, the output current compensation branch circuit includes an inductor Lc1, an inductor Lc2, an N-channel MOS tube Mc1 and a diode Dc1, one end of the inductor Lc1 is connected to the port a of the output current compensation branch circuit, the other end of the inductor Lc1 is connected to the drain of the N-channel MOS tube Mc1 and one end of the inductor Lc2 at the same time, the other end of the inductor Lc2 is connected to the anode of the diode Dc1, the cathode of the diode Dc1 is connected to the port b of the output current compensation branch circuit, the source of the N-channel MOS tube Mc1 is connected to the source of the N-channel MOS tube M1, the gate of the N-channel MOS tube Mc1 is connected to the port c of the output current compensation branch circuit, the coupling relationship exists between the inductor Lc1 and the inductor Lc2, and one end of the inductor Lc1 is the same name. Considering that leakage inductance exists between the inductor Lc1 and the inductor Lc2, a voltage spike absorbing branch can be added, the voltage spike absorbing branch comprises a resistor Rc1, a capacitor Cc1 and a diode Dc2, one end of the resistor Rc1 is simultaneously connected with one end of the inductor Lc1 and one end of the capacitor Cc1, the other end of the resistor Rc1 is simultaneously connected with the other end of the capacitor Cc1 and the cathode of the diode Dc2, and the anode of the diode Dc2 is connected with the other end of the inductor Lc 1. The third preferred version of the output current compensation branch has similar effects to the second preferred version of the output current compensation branch (Lb 2> Lb 1).
Still alternatively, the output current compensation branch includes an inductor Ld1, an inductor Ld2, an N-channel MOS tube Md1 and a diode Dd1, one end of the inductor Ld1 is connected to the port a of the output current compensation branch, the other end of the inductor Ld1 is simultaneously connected to one end of the inductor Ld2 and the anode of the diode Dd1, the cathode of the diode Dd1 is connected to the port b of the output current compensation branch, the other end of the inductor Ld2 is connected to the drain of the N-channel MOS tube Md1, the source of the N-channel MOS tube Md1 is connected to the source of the N-channel MOS tube M1, the gate of the N-channel MOS tube Md1 is connected to the port c of the output current compensation branch, the coupling relationship exists between the inductor Ld1 and the inductor Ld2, and one end of the inductor Ld1 and one end of the inductor Ld2 are the same name. Considering that leakage inductance exists between the inductor Ld1 and the inductor Ld2, a voltage spike absorbing branch can be added, the voltage spike absorbing branch comprises a resistor Rd1, a capacitor Cd1 and a diode Dd2, one end of the resistor Rd1 is simultaneously connected with one end of the inductor Ld2 and one end of the capacitor Cd1, the other end of the resistor Rd1 is simultaneously connected with the other end of the capacitor Cd1 and the cathode of the diode Dd2, and the anode of the diode Dd2 is connected with the other end of the inductor Ld 2. The fourth preferred version of the output current compensation branch has a similar effect as the second preferred version of the output current compensation branch (Lb 2< Lb 1).
Further, the controller is a soft switch controller, the voltage of the port g is vg, the voltage of the port c is vc, the switching period is T, the D is the duty ratio of vg, the Dc is the duty ratio of vc, the value ranges of D and Dc are all 0 to 1, the vg and vc satisfy the formulas (1) and (2), respectively, and n is an integer greater than or equal to 0:
The control strategy of using D as a main and Dc as an auxiliary is adopted, and the steps are as follows:
Step one: regulating D according to the direct current power supply Vi, a load RL or the output voltage Vo of the boost converter with the output current compensation branch, and setting vg according to a formula (1); meanwhile, dc=D is assigned, and vc is set according to the formula (2);
step two: keeping D and vg unchanged, adjusting the size of Dc, and setting vc according to formula (2) until the N channel MOS tube M1 accords with the working characteristics of zero voltage or quasi-zero voltage opening;
step three: and repeating the first step to the second step until the boost converter with the output current compensation branch circuit enters a steady state.
The controller adopts a singlechip, a DSP or an FPGA programmable device, such as: TMS32F28027.
The technical conception of the invention is as follows: by introducing an output current compensation branch, the output voltage ripple of a conventional Boost converter is improved. Meanwhile, the soft switch controller is adopted, and the whole circuit can work in a soft switch mode, so that the efficiency is improved.
The beneficial effects of the invention are mainly shown in the following steps: in combination with the soft switching controller, the boost converter with the output current compensation branch may have the characteristics of low output voltage ripple and high efficiency.
Drawings
Fig. 1 is a circuit block diagram of the present invention.
Fig. 2 is a circuit diagram of an output current compensation branch circuit employed in embodiment 1 of the present invention.
Fig. 3 is a circuit diagram of an output current compensation branch circuit employed in embodiment 2 of the present invention.
Fig. 4 is a circuit diagram of an output current compensation branch circuit employed in embodiment 3 of the present invention.
Fig. 5 is a circuit diagram of an output current compensation branch circuit employed in embodiment 4 of the present invention.
Fig. 6 is a timing chart of the soft switching control signals employed in embodiments 1 to 4 of the present invention.
Fig. 7 is a simulation waveform diagram of embodiment 1 of the present invention.
Fig. 8 is a simulation waveform diagram of embodiment 2 of the present invention.
Fig. 9 is a simulation waveform diagram of embodiment 3 of the present invention.
Fig. 10 is a simulation waveform diagram of embodiment 4 of the present invention.
Detailed Description
The invention is further described below with reference to the accompanying drawings.
Example 1
Referring to fig. 1, a boost converter with an output current compensation branch includes an inductor L1, an N-channel MOS tube M1, a diode D1, a capacitor Co, an output current compensation branch and a controller, wherein the current compensation branch has a port a, a port b and a port c, the controller has a port g and a port c, the positive end of a dc power supply Vi is connected with one end of the inductor L1, the other end of the inductor L1 is simultaneously connected with the drain of the N-channel MOS tube M1, the port a of the output current compensation branch and the anode of the diode D1, the cathode of the diode D1 is simultaneously connected with the port b of the output current compensation branch, one end of the capacitor Co and one end of a load RL, the other end of the load RL is simultaneously connected with the other end of the capacitor Co, the source of the N-channel MOS tube M1 and the negative end of the dc power supply Vi, the port c of the output current compensation branch is connected with the port c of the controller, and the port g of the controller is connected with the gate of the N-channel MOS tube M1;
In the output current compensation branch, when the N-channel MOS tube M1 is cut off, a part of current is separated from the inductor L1 through a port a of the N-channel MOS tube M1 for energy storage; when the N channel MOS tube M1 is conducted, energy is released through the port b of the N channel MOS tube M1, and current is provided for the capacitor Co and the load RL;
In the controller, the switching state of the N-channel MOS tube M1 is controlled through the port g, and the working state of energy storage or release of the output current compensation branch is controlled through the port c.
Referring to fig. 2, the output current compensation branch circuit includes an inductor La1, an N-channel MOS tube Ma1 and a diode Da1, one end of the inductor La1 is connected to a port a of the output current compensation branch circuit, the other end of the inductor La1 is connected to a drain electrode of the N-channel MOS tube Ma1 and an anode electrode of the diode Da1 at the same time, a cathode electrode of the diode Da1 is connected to a port b of the output current compensation branch circuit, a source electrode of the N-channel MOS tube Ma1 is connected to a source electrode of the N-channel MOS tube M1, and a gate electrode of the N-channel MOS tube Ma1 is connected to a port c of the output current compensation branch circuit.
Referring to fig. 6, the controller is a soft switch controller, assuming that the voltage at the port g is vg, the voltage at the port c is vc, the switching period is T, D is the duty cycle of vg, dc is the duty cycle of vc, the value ranges of D and Dc are 0 to 1, and vg and vc satisfy the formulas (1) and (2), respectively. The control strategy of using D as a main and Dc as an auxiliary is adopted, and the steps are as follows:
Step one: regulating D according to the direct current power supply Vi, a load RL or the output voltage Vo of the boost converter with the output current compensation branch, and setting vg according to a formula (1); meanwhile, dc=D is assigned, and vc is set according to the formula (2);
step two: keeping D and vg unchanged, adjusting the size of Dc, and setting vc according to formula (2) until the N channel MOS tube M1 accords with the working characteristics of zero voltage or quasi-zero voltage opening;
step three: and repeating the first step to the second step until the boost converter with the output current compensation branch circuit enters a steady state.
The controller adopts programmable devices such as a singlechip, a DSP or an FPGA, and the like, such as: TMS32F28027.
Fig. 7 is a typical simulation waveform diagram (d=0.8) of embodiment 1 of the present invention. As can be seen from fig. 7, the current iL1 of the inductor L1 is continuous, the current ia flowing into the output current compensation branch port a is intermittent, the output current io is intermittent, and the output voltage Vo > is the dc power source Vi. However, the output voltage ripple can be effectively reduced by charging the capacitor Co and the load RL up to 2 times (1 more than the conventional Boost converter) during one switching period T. When M1 is turned on and Ma1 is turned off, D1 is turned off, L1 is magnetized, and iL1 rises; da1 is conducted, la1 demagnetizes to provide energy for the capacitor Co and the load RL, ia=ib decreases until the value is 0, and the current im1=il1-ia flowing through M1 is less than or equal to iL1, so that the conduction loss of M1 is lower than that of a traditional Boost converter, and the reverse recovery loss of Da1 is 0, which is beneficial to improving efficiency. When M1 is cut off and Ma1 is conducted, D1 is conducted, L1 is demagnetized to provide energy for a capacitor Co and a load RL, and iL1 is lowered; da1 is cut off, la1 is magnetized, and ia rises; the current id1=il1-ia of diode D1 drops until 0, providing conditions for M1 to implement soft switching. When iD1 is reduced to 0, D1 is turned off, and the reverse recovery loss of D1 is 0, so that the efficiency is improved; ma1 is still on, and La1 resonates with the parasitic output capacitance of M1. When the drain voltage vM1 of M1 drops to 0 due to resonance, the controller turns on M1 and turns off Ma1 simultaneously, so that M1 realizes zero-voltage turn-on, and therefore turn-on loss of M1 is lower than that of a traditional Boost converter, which is beneficial to improving efficiency.
Example 2
Referring to fig. 1, 3 and 6, a boost converter with an output current compensation branch includes an inductor Lb1, an inductor Lb2, an N-channel MOS transistor Mb1 and a diode Db1, one end of the inductor Lb1 is connected to a port a of the output current compensation branch, the other end of the inductor Lb1 is connected to a drain of the N-channel MOS transistor Mb1, a source of the N-channel MOS transistor Mb1 is simultaneously connected to a source of the N-channel MOS transistor M1 and one end of the inductor Lb2, the other end of the inductor Lb2 is connected to an anode of the diode Db1, a cathode of the diode Db1 is connected to a port b of the output current compensation branch, a gate of the N-channel MOS transistor Mb1 is connected to a port c of the output current compensation branch, and one end of the inductor Lb1 and one end of the inductor Lb2 are in a coupling relationship.
Considering that leakage inductance exists between the inductor Lb1 and the inductor Lb2, the output current compensation branch further comprises a voltage spike absorption branch, the voltage spike absorption branch comprises a resistor Rb1, a capacitor Cb1 and a diode Db2, one end of the resistor Rb1 is connected with one end of the inductor Lb1 and one end of the capacitor Cb1 at the same time, the other end of the resistor Rb1 is connected with the other end of the capacitor Cb1 and the cathode of the diode Db2 at the same time, and the anode of the diode Db2 is connected with the other end of the inductor Lb 1.
Other structures (including a controller) of embodiment 2 are the same as those of embodiment 1, and the operation is similar to that of embodiment 1. But example 2 has a wider output current compensation range. When D is larger, lb2> Lb1 is taken to be more favorable for reducing output voltage ripple; taking Lb2< Lb1 is more advantageous for reducing the output voltage ripple when D is smaller.
Fig. 8 is a typical simulation waveform diagram of embodiment 2 of the present invention (d=0.2, lb2> lb 1). As can be seen from fig. 8, the current iL1 of the inductor L1 is continuous, the current ia flowing into the output current compensation branch port a is intermittent, the output current io is intermittent, and the output voltage Vo > is the dc power source Vi. However, the output voltage ripple can be effectively reduced by charging the capacitor Co and the load RL up to 2 times (1 more than the conventional Boost converter) during one switching period T. When M1 is turned on and Mb1 is turned off, D1 is turned off, L1 is magnetized, and iL1 rises; db1 is on, lb2 is magnetically discharged to energize the capacitor Co and the load RL, ia=0, ib drops to 0. When ib is reduced to 0, db1 is cut off, and the reverse recovery loss of Db1 is 0, which is advantageous in improving efficiency. When both M1 and Mb1 are turned off, D1 is turned on, L1 is demagnetized to energize the capacitor Co and the load RL, and iL1 is lowered. When M1 is cut off but Mb1 is switched on, D1 is still switched on, L1 still releases magnetism to provide energy for the capacitor Co and the load RL, and iL1 still falls; lb1 was magnetized and ia increased; the current id1=il1-ia of diode D1 drops until 0, providing conditions for M1 to implement soft switching. When iD1 is reduced to 0, D1 is turned off, and the reverse recovery loss of D1 is 0, so that the efficiency is improved; mb1 is still on, and the parasitic output capacitances of Lb1 and M1 resonate. When the drain voltage vM1 of M1 drops to 0 due to resonance, the controller turns on M1 and turns off Mb1 simultaneously, so that zero-voltage turn-on of M1 is realized, and therefore turn-on loss of M1 is lower than that of a traditional Boost converter, which is beneficial to improving efficiency.
Example 3
Referring to fig. 1,4 and 6, a boost converter with an output current compensation branch includes an inductor Lc1, an inductor Lc2, an N-channel MOS tube Mc1 and a diode Dc1, one end of the inductor Lc1 is connected to a port a of the output current compensation branch, the other end of the inductor Lc1 is connected to a drain of the N-channel MOS tube Mc1 and one end of the inductor Lc2 at the same time, the other end of the inductor Lc2 is connected to an anode of the diode Dc1, a cathode of the diode Dc1 is connected to a port b of the output current compensation branch, a source of the N-channel MOS tube Mc1 is connected to a source of the N-channel MOS tube M1, a gate of the N-channel MOS tube Mc1 is connected to a port c of the output current compensation branch, the inductor Lc1 and the inductor Lc2 have a coupling relationship, and one end of the inductor Lc1 and one end of the inductor Lc2 are the same name.
Considering that leakage inductance exists between the inductor Lc1 and the inductor Lc2, the output current compensation branch further comprises a voltage spike absorbing branch, the voltage spike absorbing branch comprises a resistor Rc1, a capacitor Cc1 and a diode Dc2, one end of the resistor Rc1 is connected with one end of the inductor Lc1 and one end of the capacitor Cc1 at the same time, the other end of the resistor Rc1 is connected with the other end of the capacitor Cc1 and the cathode of the diode Dc2 at the same time, and the anode of the diode Dc2 is connected with the other end of the inductor Lc 1.
Other structures (including the controller) of embodiment 3 are the same as those of embodiment 2, and the operation is similar to that of embodiment 2 when Lb2> Lb1 is taken.
Fig. 9 is a typical simulation waveform diagram (d=0.5) of embodiment 3 of the present invention. As can be seen from fig. 9, the current iL1 of the inductor L1 is continuous, the current ia flowing into the output current compensation branch port a is intermittent, the output current io is intermittent, and the output voltage Vo > is the dc power source Vi. However, the output voltage ripple can be effectively reduced by charging the capacitor Co and the load RL up to 2 times (1 more than the conventional Boost converter) during one switching period T. When M1 is turned on and Mc1 is turned off, D1 is turned off, L1 is magnetized, and iL1 rises; dc1 is conducted, the coupling inductors Lc1 and Lc2 jointly discharge magnetism to provide energy for the capacitor Co and the load RL, ia=ib drops to 0, and current im1=il1-ia flowing through M1 is less than or equal to iL1, so that the conduction loss of M1 is lower than that of a traditional Boost converter, and the efficiency is improved. When ib decreases to 0, dc1 is cut off, and the reverse recovery loss of Dc1 is 0, which is also advantageous for improving efficiency. When M1 is cut off and Mc1 is conducted, D1 is conducted, L1 is demagnetized to provide energy for a capacitor Co and a load RL, and iL1 is lowered; lc1 magnetizes, ia rises; the current id1=il1-ia of diode D1 drops until 0, providing conditions for M1 to implement soft switching. When iD1 is reduced to 0, D1 is turned off, and the reverse recovery loss of D1 is 0, so that the efficiency is improved; mc1 is still on, and Lc1 resonates with the parasitic output capacitance of M1. When the drain voltage vM1 of the M1 drops to 0 for a plurality of times due to resonance, the controller simultaneously turns on the M1 and turns off the Mc1, so that the M1 realizes zero-voltage turn-on, and therefore the turn-on loss of the M1 is lower than that of the traditional Boost converter, which is beneficial to improving the efficiency.
Example 4
Referring to fig. 1, 5 and 6, a boost converter including an output current compensation branch includes an inductor Ld1, an inductor Ld2, an N-channel MOS transistor Md1 and a diode Dd1, one end of the inductor Ld1 is connected to a port a of the output current compensation branch, the other end of the inductor Ld1 is simultaneously connected to one end of the inductor Ld2 and an anode of the diode Dd1, a cathode of the diode Dd1 is connected to a port b of the output current compensation branch, the other end of the inductor Ld2 is connected to a drain of the N-channel MOS transistor Md1, a source of the N-channel MOS transistor Md1 is connected to a source of the N-channel MOS transistor M1, a gate of the N-channel MOS transistor Md1 is connected to a port c of the output current compensation branch, the inductor Ld1 and the inductor Ld2 have a coupling relationship, and one end of the inductor Ld1 and one end of the inductor Ld2 are identical ends.
Considering that leakage inductance exists between the inductor Ld1 and the inductor Ld2, the output current compensation branch further comprises a voltage spike absorption branch, the voltage spike absorption branch comprises a resistor Rd1, a capacitor Cd1 and a diode Dd2, one end of the resistor Rd1 is simultaneously connected with one end of the inductor Ld2 and one end of the capacitor Cd1, the other end of the resistor Rd1 is simultaneously connected with the other end of the capacitor Cd1 and the cathode of the diode Dd2, and the anode of the diode Dd2 is connected with the other end of the inductor Ld 2.
Other structures (including the controller) of embodiment 4 are the same as those of embodiment 2, and the operation is similar to that of embodiment 2 when Lb2< Lb1 is taken.
Fig. 10 is a typical simulation waveform diagram (d=0.2) of embodiment 4 of the present invention. As can be seen from fig. 10, the current iL1 of the inductor L1 is continuous, the current ia flowing into the output current compensation branch port a is intermittent, the output current io is intermittent, and the output voltage Vo > is the dc power source Vi. However, the output voltage ripple can be effectively reduced by charging the capacitor Co and the load RL up to 2 times (1 more than the conventional Boost converter) during one switching period T. When M1 is turned on and Md1 is turned off, D1 is turned off, L1 is magnetized, and iL1 rises; dd1 is conducted, ld1 is magnetically released to provide energy for the capacitor Co and the load RL, ia=ib drops to 0, and current iM1=iL1-ia flowing through M1 is less than or equal to iL1, so that the conduction loss of M1 is lower than that of a traditional Boost converter, and the efficiency is improved. When ib decreases to 0, dd1 is cut off, and the reverse recovery loss of Dd1 is0, which is also advantageous for improving efficiency. When both M1 and Md1 are turned off, D1 is turned on, L1 is demagnetized to provide energy for the capacitor Co and the load RL, and iL1 is lowered. When M1 is cut off but Md1 is conducted, D1 is still conducted, L1 is still magnetized to provide energy for a capacitor Co and a load RL, and iL1 is still reduced; the coupling inductances Ld1 and Ld2 are jointly magnetized, and ia rises; the current id1=il1-ia of diode D1 drops until 0, providing conditions for M1 to implement soft switching. When iD1 is reduced to 0, D1 is turned off, and the reverse recovery loss of D1 is0, so that the efficiency is improved; md1 is still on, and Ld1 and Ld2 resonate with the parasitic output capacitance of M1. When the drain voltage vM1 of the M1 drops to the lowest point due to resonance, the controller simultaneously turns on the M1 and turns off the Md1, so that the M1 realizes quasi-zero voltage on, and therefore, the on loss of the M1 is lower than that of the traditional Boost converter, which is beneficial to improving the efficiency.
The embodiments described in the present specification are merely examples of implementation forms of the inventive concept, and the scope of protection of the present invention should not be construed as being limited to the specific forms set forth in the embodiments, but the scope of protection of the present invention and equivalent technical means that can be conceived by those skilled in the art based on the inventive concept.
Claims (7)
1. A boost converter comprising an output current compensation branch, characterized by: the boost converter with the output current compensation branch comprises an inductor L1, an N-channel MOS tube M1, a diode D1, a capacitor Co, an output current compensation branch and a controller, wherein the current compensation branch is provided with a port a, a port b and a port c, the controller is provided with a port g and a port c, the positive end of a direct current power supply Vi is connected with one end of the inductor L1, the other end of the inductor L1 is simultaneously connected with the drain electrode of the N-channel MOS tube M1, the port a of the output current compensation branch and the anode of the diode D1, the cathode of the diode D1 is simultaneously connected with the port b of the output current compensation branch, one end of the capacitor Co and one end of a load RL, the other end of the load RL is simultaneously connected with the other end of the capacitor Co, the source electrode of the N-channel MOS tube M1 and the negative end of the direct current power supply Vi, the port c of the output current compensation branch is connected with the port c of the controller, and the port g of the controller is connected with the grid electrode of the N-channel MOS tube M1;
In the output current compensation branch, when the N-channel MOS tube M1 is cut off, a part of current is separated from the inductor L1 through a port a of the N-channel MOS tube M1 for energy storage; when the N channel MOS tube M1 is conducted, energy is released through the port b of the N channel MOS tube M1, and current is provided for the capacitor Co and the load RL;
In the controller, the switching state of the N-channel MOS tube M1 is controlled through the port g, and the working state of energy storage or release of the output current compensation branch is controlled through the port c.
2. The boost converter with output current compensation branch of claim 1, wherein: the output current compensation branch circuit comprises an inductor La1, an N-channel MOS tube Ma1 and a diode Da1, one end of the inductor La1 is connected with a port a of the output current compensation branch circuit, the other end of the inductor La1 is simultaneously connected with a drain electrode of the N-channel MOS tube Ma1 and an anode of the diode Da1, a cathode of the diode Da1 is connected with a port b of the output current compensation branch circuit, a source electrode of the N-channel MOS tube Ma1 is connected with a source electrode of the N-channel MOS tube M1, and a grid electrode of the N-channel MOS tube Ma1 is connected with a port c of the output current compensation branch circuit.
3. The boost converter with output current compensation branch of claim 1, wherein: the output current compensation branch circuit comprises an inductor Lb1, an inductor Lb2, an N-channel MOS tube Mb1 and a diode Db1, one end of the inductor Lb1 is connected with a port a of the output current compensation branch circuit, the other end of the inductor Lb1 is connected with a drain electrode of the N-channel MOS tube Mb1, a source electrode of the N-channel MOS tube Mb1 is simultaneously connected with a source electrode of the N-channel MOS tube M1 and one end of the inductor Lb2, the other end of the inductor Lb2 is connected with an anode of the diode Db1, a cathode of the diode Db1 is connected with a port b of the output current compensation branch circuit, a grid electrode of the N-channel MOS tube Mb1 is connected with a port c of the output current compensation branch circuit, a coupling relation exists between the inductor Lb1 and the inductor Lb2, and one end of the inductor Lb1 and one end of the inductor Lb2 are homonymous ends.
4. The boost converter with output current compensation branch of claim 1, wherein: the output current compensation branch circuit comprises an inductor Lc1, an inductor Lc2, an N-channel MOS tube Mc1 and a diode Dc1, one end of the inductor Lc1 is connected with a port a of the output current compensation branch circuit, the other end of the inductor Lc1 is simultaneously connected with a drain electrode of the N-channel MOS tube Mc1 and one end of the inductor Lc2, the other end of the inductor Lc2 is connected with an anode of the diode Dc1, a cathode of the diode Dc1 is connected with a port b of the output current compensation branch circuit, a source of the N-channel MOS tube Mc1 is connected with a source of the N-channel MOS tube M1, a grid electrode of the N-channel MOS tube Mc1 is connected with a port c of the output current compensation branch circuit, the inductor Lc1 and the inductor Lc2 are in coupling relation, and one end of the inductor Lc1 and one end of the inductor Lc2 are homonymous ends.
5. The boost converter with output current compensation branch of claim 1, wherein: the output current compensation branch circuit comprises an inductor Ld1, an inductor Ld2, an N-channel MOS tube Md1 and a diode Dd1, one end of the inductor Ld1 is connected with a port a of the output current compensation branch circuit, the other end of the inductor Ld1 is simultaneously connected with one end of the inductor Ld2 and an anode of the diode Dd1, a cathode of the diode Dd1 is connected with a port b of the output current compensation branch circuit, the other end of the inductor Ld2 is connected with a drain electrode of the N-channel MOS tube Md1, a source electrode of the N-channel MOS tube Md1 is connected with a source electrode of the N-channel MOS tube M1, a grid electrode of the N-channel MOS tube Md1 is connected with a port c of the output current compensation branch circuit, a coupling relation exists between the inductor Ld1 and the inductor Ld2, and one end of the inductor Ld1 and one end of the inductor Ld2 are homonymous ends.
6. Boost converter with output current compensation branch according to one of claims 1to 5, characterized in that: the controller is a soft switch controller, the voltage of a port g is vg, the voltage of a port c is vc, the switching period is T, the D is the duty ratio of vg, the Dc is the duty ratio of vc, the value ranges of D and Dc are 0 to 1, the vg and the vc respectively satisfy the formulas (1) and (2), and n is an integer greater than or equal to 0:
The control strategy of using D as a main and Dc as an auxiliary is adopted, and the steps are as follows:
Step one: regulating D according to the direct current power supply Vi, a load RL or the output voltage Vo of the boost converter with the output current compensation branch, and setting vg according to a formula (1); meanwhile, dc=D is assigned, and vc is set according to the formula (2);
step two: keeping D and vg unchanged, adjusting the size of Dc, and setting vc according to formula (2) until the N channel MOS tube M1 accords with the working characteristics of zero voltage or quasi-zero voltage opening;
step three: and repeating the first step to the second step until the boost converter with the output current compensation branch circuit enters a steady state.
7. The boost converter with output current compensating leg of claim 6, wherein: the controller adopts a singlechip, a DSP or an FPGA programmable device.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910527609.7A CN110176860B (en) | 2019-06-18 | 2019-06-18 | Boost converter with output current compensation branch |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201910527609.7A CN110176860B (en) | 2019-06-18 | 2019-06-18 | Boost converter with output current compensation branch |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN110176860A CN110176860A (en) | 2019-08-27 |
| CN110176860B true CN110176860B (en) | 2024-05-28 |
Family
ID=67698542
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201910527609.7A Active CN110176860B (en) | 2019-06-18 | 2019-06-18 | Boost converter with output current compensation branch |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN110176860B (en) |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101854126A (en) * | 2009-03-31 | 2010-10-06 | 半导体元件工业有限责任公司 | Compensation method and circuit |
| CN105337499A (en) * | 2015-11-24 | 2016-02-17 | 中国电子科技集团公司第五十五研究所 | Underloading current compensation circuit of cuk type switching convertor |
| CN107924208A (en) * | 2015-08-04 | 2018-04-17 | 高通股份有限公司 | Switching regulaor current sensing circuit and method |
| CN109075697A (en) * | 2018-02-11 | 2018-12-21 | 深圳欣锐科技股份有限公司 | The ripple optimal control method and interlock circuit of pfc circuit output voltage |
| CN209930139U (en) * | 2019-06-18 | 2020-01-10 | 浙江工业大学之江学院 | Boost converter with output current compensation branch |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7915879B2 (en) * | 2008-06-30 | 2011-03-29 | Infineon Technologies Austria Ag | Switching converter including a rectifier element with nonlinear capacitance |
-
2019
- 2019-06-18 CN CN201910527609.7A patent/CN110176860B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101854126A (en) * | 2009-03-31 | 2010-10-06 | 半导体元件工业有限责任公司 | Compensation method and circuit |
| CN107924208A (en) * | 2015-08-04 | 2018-04-17 | 高通股份有限公司 | Switching regulaor current sensing circuit and method |
| CN105337499A (en) * | 2015-11-24 | 2016-02-17 | 中国电子科技集团公司第五十五研究所 | Underloading current compensation circuit of cuk type switching convertor |
| CN109075697A (en) * | 2018-02-11 | 2018-12-21 | 深圳欣锐科技股份有限公司 | The ripple optimal control method and interlock circuit of pfc circuit output voltage |
| CN209930139U (en) * | 2019-06-18 | 2020-01-10 | 浙江工业大学之江学院 | Boost converter with output current compensation branch |
Non-Patent Citations (1)
| Title |
|---|
| Analysis and Control of Ripple Eliminators in DC Systems;Xin Cao et al.;《2014 Sixth Annual IEEE Green Technologies Conference》;20140605;第 29-36 页 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN110176860A (en) | 2019-08-27 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN103296882B (en) | A kind of DC-DC controlled resonant converter with automatically equalizing voltage function | |
| CN103595258A (en) | Boost type soft switching resonant converter and frequency fixing control method thereof | |
| CN103904901A (en) | Phase-shift full-bridge converter circuit and control method | |
| CN105407583B (en) | Single-pole quasi-resonance LED driving device based on Buck-Boost circuit and Flyback circuit | |
| CN104980037A (en) | Secondary side adjustment type fixed frequency resonant converter and control method thereof | |
| CN105207486A (en) | Bidirectional resonance DC converter and control method thereof | |
| CN103441683A (en) | Active clamping forward power circuit | |
| CN110719035A (en) | Topological structure of single-stage DAB-LLC hybrid bidirectional DC-DC converter | |
| CN106787757A (en) | A kind of CLTCL resonance DCs converter | |
| CN103618444A (en) | Three-winding coupling inductance ZVS/ZCS double-tube boost converter | |
| CN110011537A (en) | A kind of switch converters and its control method | |
| CN105871219A (en) | Auxiliary pipe voltage clamp type soft switching push-pull direct-current converter | |
| CN203827175U (en) | Novel soft switching bi-directional DC-DC converter | |
| CN103595257A (en) | Isolation type direct-current buck converter with soft switching function and control method of isolation type direct-current buck converter | |
| CN110086342A (en) | A kind of switch converters and its control method | |
| CN101635510B (en) | Complex forward DC converter | |
| CN110138210B (en) | Sepic converter with output current compensation branch | |
| CN209930139U (en) | Boost converter with output current compensation branch | |
| CN209930140U (en) | Sepic converter with output current compensation branch | |
| CN110176860B (en) | Boost converter with output current compensation branch | |
| CN209930141U (en) | Buck-Boost converter with output current compensation branch | |
| CN104300780A (en) | Large power non-isolation DC/DC soft switching circuit | |
| CN110190749B (en) | Buck-Boost converter with output current compensation branch | |
| CN204906192U (en) | Boost module is recommended to wide region full cut -off ring high efficiency | |
| CN110098747B (en) | Flyback converter with output current compensation branch |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| TA01 | Transfer of patent application right |
Effective date of registration: 20240425 Address after: Phase II of Xiaoshan robot Town, 477 Hongxing Road, Xiaoshan Economic and Technological Development Zone, Xiaoshan District, Hangzhou City, Zhejiang Province, 310000 Applicant after: Zhejiang Environmental Protection Technology Co.,Ltd. azure Country or region after: China Address before: 312030 no.958, Yuezhou Avenue, Keqiao District, Shaoxing City, Zhejiang Province Applicant before: ZHIJIANG COLLEGE OF ZHEJIANG UNIVERSITY OF TECHNOLOGY Country or region before: China |
|
| TA01 | Transfer of patent application right | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |