CN105337499A - Underloading current compensation circuit of cuk type switching convertor - Google Patents
Underloading current compensation circuit of cuk type switching convertor Download PDFInfo
- Publication number
- CN105337499A CN105337499A CN201510823281.5A CN201510823281A CN105337499A CN 105337499 A CN105337499 A CN 105337499A CN 201510823281 A CN201510823281 A CN 201510823281A CN 105337499 A CN105337499 A CN 105337499A
- Authority
- CN
- China
- Prior art keywords
- output
- resistance
- receives
- pipe
- hysteresis comparator
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Landscapes
- Dc-Dc Converters (AREA)
Abstract
The invention relates to an underloading current compensation circuit of a cuk type switching convertor, which comprises a hysteresis comparator and a regulating tube, wherein the in-phase end of the hysteresis comparator is connected with a reference voltage Vref; the invert-phase end of the hysteresis comparator is connected with a feedback resistance string; an output end of the hysteresis comparator is connected to a grid of the regulating tube MP1; an input voltage is connected to a source electrode of the regulating tube MP1; a drain electrode of the regulating tube MP1 is connected to the output voltage of the cuk convertor. Under the underloading condition, when current on an output inductor is discharged to zero so that the output voltage is reduced to a certain threshold value, the output of the hysteresis comparator switches on the regulating tube MP1 to charge an output capacitor of the cuk convertor; when the output voltage of the convertor rises to a overturning threshold value again, the output of the hysteresis comparator is overturned again and the regulating tube is switched off. According to the invention, the underloading current compensation circuit of the cuk type switch convertor is capable of acquiring accurate voltage output under the heavy load condition and can also effectively compensate deviation of the output voltage under the underloading condition so as to obtain negative voltage output with low ripple wave and high precision.
Description
Technical field
The invention belongs to microelectronics and field of switch power, belong to one circle control and add the underloading current compensation circuit that III type compensates negative pressure cuk switch converters, be specifically related to a kind of underloading current compensation circuit of cuk type switch converters.
Background technology
The features such as Organic Light Emitting Diode (OrganicLightEmittingDiodeOLED) has softness, transparent, image quality is clear, energy-conserving and environment-protective, are considered to be the novel planar Display Technique of future generation of most potentiality.Consider for increasing luminous brightness to greatest extent, the negative electrode of OLED display needs negative voltage to power, thus the design of negative voltage chip becomes the main trend in this field.Cuk circuit adopts chopped wave technique, and have the advantages that output current ripple is low, this also makes cuk converter have a wide range of applications to the exigent occasion of ripple.
What current traditional cuk converter generally adopted is one circle control mode, but the loop gain of one circle control mode is low, and regulating power is poor, the inapplicable occasion very high to output voltage required precision.As shown in Figure 1, the converter loop gain that employing one circle control adds III type compensation is high, and regulating power is strong.But under underloading condition, when the second inductance L 2 discharges into zero, output capacitance C2 can by inductance to input capacitance C1 electric discharge, and output voltage can obviously fall, so that deflects away from default threshold range.
Summary of the invention
Object of the present invention is exactly add the converter loop of III type compensation under underloading condition for existing one circle control, when the second inductance L 2 discharges into zero, output capacitance C2 can be discharged to input capacitance C1 by inductance, output voltage can obviously fall, so that deflect away from the problem of default threshold range, design a kind of one circle control add III type compensate control loop effect under, output voltage is carried out under underloading condition to the underloading current compensation circuit of the cuk type switch converters of current compensation.
Technical scheme of the present invention is:
A kind of underloading current compensation circuit of cuk type switch converters, it is characterized in that: comprise band-gap reference, feedback resistance string, a hysteresis comparator and a PMOS electric current Correctional tube, the output Vref of band-gap reference receives the in-phase input end of hysteresis comparator COMP1, feedback resistance is concatenated into the inverting input of this hysteresis comparator COMP1, and the output of this hysteresis comparator COMP1 receives the grid of electric current Correctional tube MP1; The source electrode of this electric current Correctional tube MP1 meets input supply voltage VDD, and the drain electrode of electric current Correctional tube MP1 is received on the output voltage Vo of cuk converter.
Described resistance feedback string comprises the first resistance R1 and the second resistance R2, one end of this first resistance R1 is connected with one end of this second resistance R2 and produces feedback voltage V FB, this VFB end is connected with the in-phase input end of described hysteresis comparator COMP1 simultaneously, the other end of this first resistance R1 is connected with input supply voltage VDD, and the other end of this second resistance R2 is connected with cuk type switch converters output end vo.
Described hysteresis comparator COMP1 overturns the condition that will meet:
As VFB<90%Vref, the output of hysteresis comparator is turned over as low by height, opens electric current Correctional tube MP1;
As VFB>95%Vref, the output of hysteresis comparator is turned over as height by low, close current Correctional tube MP1;
Described electric current Correctional tube MP1 is PMOS.
The output Vref of described band-gap reference is connected to ground, three resistor satisfied following relations by the 6th resistance R6, the 7th resistance R7 that are connected in series, the 8th resistance R8:
R8=18*R7=18*R6；
The end that 6th resistance R6 is connected with the 7th resistance R7 receives the source of NMOS tube MN5, and the drain terminal of NMOS tube MN5 receives the in-phase input end of comparator COMP1, and the grid of NMOS tube MN5 receives the output of comparator COMP1; The end that 7th resistance R7 is connected with the 8th resistance R8 receives the source of NMOS tube MN4, the drain terminal of NMOS tube MN4 receives the in-phase input end of comparator COMP1, the grid of NMOS tube MN4 receives the output of inverter INV, and the output of comparator COMP1 is received in the input of this inverter INV; The anti-phase input termination feedback voltage V FB of comparator COMP1; Metal-oxide-semiconductor MP2, MP3, MN2 and MN3 form two inverters, the grid of MP2 with MN2 is connected and receives the output of comparator COMP1, the source of MP2 pipe meets supply voltage VDD, the source ground connection of MN2 pipe, MP2 pipe is connected with the drain terminal of MN2 pipe and receives the grid of MP3 pipe and MP4 pipe, the source of MP3 pipe meets supply voltage VDD, the source ground connection of MN3 pipe, MP3 pipe is connected with the drain terminal of MN3 pipe and receives the grid of MP1 pipe, the source electrode of Correctional tube MP1 meets input supply voltage VDD, and the drain electrode of Correctional tube MP1 is received on the output voltage Vo of cuk converter.
Advantage of the present invention and remarkable result:
(1) novel year of the present invention current compensation circuit effectively can trim departing from of output voltage under underloading condition.
(2) novel year of the present invention current compensation circuit structure is simple, and achieves its function preferably.
The present invention, compared with existing cuk converter, can obtain accurate voltage and export, also under underloading condition, can carry out effective compensation to departing from of output voltage under fully loaded transportation condition, thus obtains the high-precision negative voltage output of low ripple.
Accompanying drawing explanation
Fig. 1 is the CUK type switch converters schematic diagram adding III type compensation the existing monocycle.
Fig. 2 is the specific implementation of current compensation circuit of the present invention.
Fig. 3 is each node current voltage waveform not adding circuit of the present invention under underloading.
Fig. 4 is each node current voltage waveform after adding circuit of the present invention under underloading.
Embodiment
Below in conjunction with accompanying drawing, the invention will be further described.
As shown in Figure 1, one circle control adds III type compensation cuk type switch converters and comprises two stage power level circuit, and one circle control adds III type compensating circuit.Power stage comprises input inductance L 1, outputting inductance L2, input capacitance C1, output capacitance C2, power tube MN1, sustained diode 1, load resistance Ro and feedback resistance string R1, R2.One end of input inductance L 1 is connected with supply voltage VDD, and the other end connects one end of input capacitance C1 and the drain electrode of power tube MN1; The other end of input capacitance C1 connects one end of outputting inductance L2 and the anode of sustained diode 1, the negativing ending grounding of D1; One end of another termination output filter capacitor C2 of outputting inductance L2 is as the other end ground connection of output voltage Vo, output capacitance C2; Load resistance Ro mono-end is received output voltage Vo and is held, other end ground connection.The first order that inductance L 1, input capacitance C1 and power tube MN1 form power stage is inputted in whole power stage; The second level of the power stage that outputting inductance L2, input capacitance C2 and fly-wheel diode and load resistance Ro form, feedback resistance string comprises the first resistance R1 and the second resistance R2, one end of this first resistance is connected with one end of this second resistance, this end of this first resistance produces feedback signal VFB simultaneously, the other end of this first resistance is connected with input voltage, and the other end of this second resistance is connected with cuk converter output terminal Vo.Control section is made up of integrator, III type compensating network, comparator, rest-set flip-flop, feedback resistance string and load resistance.The end that integrator comprises resistance Rz, electric capacity Cz and operational amplifier E1, Rz receives the end of oppisite phase of E1, and the other end receives the anode of sustained diode 1; Electric capacity Cz is connected across end of oppisite phase and the output of E1, and K switch is connected in parallel on the two ends of electric capacity C, and wherein K switch is held by the Q_ of rest-set flip-flop and controlled, the in-phase end ground connection of E1.III type compensating network comprises error amplifier and two resistance-capacitance networks, the resistance-capacitance network of C11, C22 and R5 composition jumps to end of oppisite phase and the output of error amplifier, reference voltage V ref receives the end of oppisite phase of error amplifier by another resistance-capacitance network that compensating resistance R3, R4, C33 form, the homophase termination feedback signal VFB of error amplifier.Output (i.e. the output of the error amplifier) VEA_OUT of III type compensating network is connected to the end of oppisite phase of comparator COMP2, output (i.e. the output of the operational amplifier E1) VE1_OUT of integrator receives the in-phase end of comparator COMP2, the reset terminal R that rest-set flip-flop is received in the output of comparator holds, the set end S of rest-set flip-flop connects clock signal, the output Q of rest-set flip-flop receives the grid of power tube MN1 by drive circuit, control to produce duty cycle signals.
Be depicted as a kind of underloading current compensation circuit adding III type compensation negative pressure cuk switch converters for one circle control of the present invention in Fig. 1 dotted line frame, comprise band-gap reference, feedback resistance string, a hysteresis comparator and a PMOS electric current Correctional tube.The output Vref of band-gap reference receives the in-phase input end of hysteresis comparator COMP1, and feedback resistance is concatenated into the inverting input of this hysteresis comparator COMP1, and the output of this hysteresis comparator receives the grid of electric current Correctional tube MP1; The source electrode of this Correctional tube MP1 meets input supply voltage VDD, and the drain electrode of Correctional tube MP1 is received on the output voltage Vo of cuk converter.
Shown in Fig. 1 dotted line frame, circuit specific implementation is as shown in Figure 2: reference voltage V ref is connected to ground by resistance R6, R7, the R8 be connected in series, three resistor satisfied following relations:
R8=18*R7=18*R6；
The end that resistance R6 with R7 is connected receives the source of NMOS tube MN5, and the drain terminal of MN5 receives the in-phase input end of comparator COMP1, and the grid of MN5 receives the output of COMP1; The end that resistance R7 with R8 is connected receives the source of NMOS tube MN4, and the drain terminal of MN4 receives the in-phase input end of comparator COMP1, and the grid of MN4 receives the output of inverter INV, and the output of COMP1 is received in the input of this inverter; The anti-phase input termination feedback voltage V FB of comparator COMP1; Metal-oxide-semiconductor MP2, MP3, MN2 and MN3 form two inverters, the grid of MP2 with MN2 is connected and receives the output of COMP1, the source of MP2 pipe meets supply voltage VDD, the source ground connection of MN2 pipe, MP2 pipe is connected with the drain terminal of MN2 pipe and receives the grid of MP3 pipe and MP4 pipe, the source of MP3 pipe meets supply voltage VDD, the source ground connection of MN3 pipe, MP3 pipe is connected with the drain terminal of MN3 pipe and receives the grid of MP1 pipe, the source electrode of Correctional tube MP1 meets input supply voltage VDD, and the drain electrode of Correctional tube MP1 is received on the output voltage Vo of cuk converter
The course of work of circuit shown in Fig. 1 when fully loaded transportation condition is as follows: when the rising edge of clock arrives, the output Q set " 1 " of rest-set flip-flop, now power tube MN1 conducting, K switch disconnects, integrator collection diode D1 anode obtains voltage and starts integration, its output linearity rises, and now supply voltage VDD charges to along path 1 shown in Fig. 1 input inductance L 1, and input capacitance C1 and output capacitance C2 charges to along path 2 shown in Fig. 1 outputting inductance L2; When the output VE1_OUT of integrator is crossing with the output VEA_OUT of III type compensator, comparator reverses, switch closes, integrator resets, simultaneously metal-oxide-semiconductor MN1 disconnects, now supply voltage VDD and input inductance L 1 give input capacitance C1 charging along path 3 shown in Fig. 1, and outputting inductance L2 gives output capacitance C2 charging along path 4 shown in Fig. 1.
When under working in light-load mode time (in inductance L 2, current discharge is to zero), its work wave is as shown in Figure 3: when inductive current discharges into zero, output capacitance C2 can charge to conversely outputting inductance L2, diode D1 anode voltage VD1 is caused to fall, namely the electric charge on output capacitance C2 gives input capacitance C1 by inductance L 2 transfer, cause falling of voltage, beyond the threshold range deflecting away from permission.
Shown in course of work Fig. 4 of current compensation circuit shown in Fig. 1 dotted line frame: when output voltage Vo drops into 90% of Vref, the output MP1_G of comparator COMP1 by high tumble to low, open Correctional tube MP1 to charge to output capacitance C2, when output voltage rises to 95% of Vref, the output MP1_G of comparator COMP1 is turned to height by low again, close Correctional tube MP1, no longer mend electricity to output capacitance, thus ensure that output voltage no longer falls.
Feature of the present invention and content disclose as above, but those skilled in the art may make all replacement and the amendment that do not deviate from invention spirit based on explanation of the present invention.Therefore, protection scope of the present invention should be not limited to above-mentioned embodiment, and should comprise the various substitutions and modifications of the present invention that do not deviate from, and is contained by claims.
The part that the present invention does not relate to prior art that maybe can adopt same as the prior art is realized.
Claims (5)
1. the underloading current compensation circuit of a cuk type switch converters, it is characterized in that: comprise band-gap reference, feedback resistance string, a hysteresis comparator and a PMOS electric current Correctional tube, the output Vref of band-gap reference receives the in-phase input end of hysteresis comparator COMP1, feedback resistance is concatenated into the inverting input of this hysteresis comparator COMP1, and the output of this hysteresis comparator COMP1 receives the grid of electric current Correctional tube MP1; The source electrode of this electric current Correctional tube MP1 meets input supply voltage VDD, and the drain electrode of electric current Correctional tube MP1 is received on the output voltage Vo of cuk converter.
2. the underloading current compensation circuit of cuk type switch converters according to claim 1, it is characterized in that: described resistance feedback string comprises the first resistance R1 and the second resistance R2, one end of this first resistance R1 is connected with one end of this second resistance R2 and produces feedback voltage V FB, this VFB end is connected with the in-phase input end of described hysteresis comparator COMP1 simultaneously, the other end of this first resistance R1 is connected with input supply voltage VDD, and the other end of this second resistance R2 is connected with cuk type switch converters output end vo.
3. the underloading current compensation circuit of cuk type switch converters according to claim 1, is characterized in that: described hysteresis comparator COMP1 overturns the condition that will meet and is:
As VFB<90%Vref, the output of hysteresis comparator is turned over as low by height, opens electric current Correctional tube MP1;
As VFB>95%Vref, the output of hysteresis comparator is turned over as height by low, close current Correctional tube MP1.
4. the underloading current compensation circuit of the cuk type switch converters according to claim 1 and 2, is characterized in that: described electric current Correctional tube MP1 is PMOS.
5. the underloading current compensation circuit of cuk type switch converters according to claim 1, it is characterized in that: the output Vref of described band-gap reference is connected to ground, three resistor satisfied following relations by the 6th resistance R6, the 7th resistance R7 that are connected in series, the 8th resistance R8:
R8=18*R7=18*R6；
The end that 6th resistance R6 is connected with the 7th resistance R7 receives the source of NMOS tube MN5, and the drain terminal of NMOS tube MN5 receives the in-phase input end of comparator COMP1, and the grid of NMOS tube MN5 receives the output of comparator COMP1; The end that 7th resistance R7 is connected with the 8th resistance R8 receives the source of NMOS tube MN4, the drain terminal of NMOS tube MN4 receives the in-phase input end of comparator COMP1, the grid of NMOS tube MN4 receives the output of inverter INV, and the output of comparator COMP1 is received in the input of this inverter INV; The anti-phase input termination feedback voltage V FB of comparator COMP1; Metal-oxide-semiconductor MP2, MP3, MN2 and MN3 form two inverters, the grid of MP2 with MN2 is connected and receives the output of comparator COMP1, the source of MP2 pipe meets supply voltage VDD, the source ground connection of MN2 pipe, MP2 pipe is connected with the drain terminal of MN2 pipe and receives the grid of MP3 pipe and MP4 pipe, the source of MP3 pipe meets supply voltage VDD, the source ground connection of MN3 pipe, MP3 pipe is connected with the drain terminal of MN3 pipe and receives the grid of MP1 pipe, the source electrode of Correctional tube MP1 meets input supply voltage VDD, and the drain electrode of Correctional tube MP1 is received on the output voltage Vo of cuk converter.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510823281.5A CN105337499B (en) | 2015-11-24 | 2015-11-24 | A kind of underloading current compensation circuit of cuk types switch converters |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201510823281.5A CN105337499B (en) | 2015-11-24 | 2015-11-24 | A kind of underloading current compensation circuit of cuk types switch converters |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN105337499A true CN105337499A (en) | 2016-02-17 |
| CN105337499B CN105337499B (en) | 2018-01-16 |
Family
ID=55287849
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201510823281.5A Active CN105337499B (en) | 2015-11-24 | 2015-11-24 | A kind of underloading current compensation circuit of cuk types switch converters |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN105337499B (en) |
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN107425721A (en) * | 2017-06-13 | 2017-12-01 | 西安交通大学 | A kind of tri-state multi output interface circuit for solar energy collecting |
| CN108563275A (en) * | 2018-04-16 | 2018-09-21 | 电子科技大学 | A kind of no quiescent dissipation trims switching circuit |
| CN108649934A (en) * | 2018-05-31 | 2018-10-12 | 成都锐成芯微科技股份有限公司 | A kind of hysteresis comparator circuit |
| CN110176860A (en) * | 2019-06-18 | 2019-08-27 | 浙江工业大学之江学院 | The boost converter of the current compensation branch containing output |
| CN112290791A (en) * | 2020-05-18 | 2021-01-29 | 珠海市杰理科技股份有限公司 | Boost type hysteresis switch converter, control method, chip and electronic equipment |
| CN114546013A (en) * | 2022-01-26 | 2022-05-27 | 中山大学 | Reference starting circuit for detecting current by adopting comparator with mismatch |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20070064454A1 (en) * | 2005-09-21 | 2007-03-22 | Chen Isaac Y | Circuit and method for soft start from a residual voltage |
| CN101847928A (en) * | 2010-04-14 | 2010-09-29 | 广州市广晟微电子有限公司 | Quick starting circuit and method of low-noise linear regulator |
| CN102821520A (en) * | 2012-08-07 | 2012-12-12 | 广州晶锐信息技术有限公司 | LED (light-emitting diode) driving circuit and control method thereof |
| JP2013222516A (en) * | 2012-04-13 | 2013-10-28 | Panasonic Corp | Led lighting device, and vehicular lighting system and luminaire using the same |
| CN104038039A (en) * | 2014-06-20 | 2014-09-10 | 东南大学 | Starting circuit of monocyclic-control III-shaped compensation CUK-type switch converter |
-
2015
- 2015-11-24 CN CN201510823281.5A patent/CN105337499B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20070064454A1 (en) * | 2005-09-21 | 2007-03-22 | Chen Isaac Y | Circuit and method for soft start from a residual voltage |
| CN101847928A (en) * | 2010-04-14 | 2010-09-29 | 广州市广晟微电子有限公司 | Quick starting circuit and method of low-noise linear regulator |
| JP2013222516A (en) * | 2012-04-13 | 2013-10-28 | Panasonic Corp | Led lighting device, and vehicular lighting system and luminaire using the same |
| CN102821520A (en) * | 2012-08-07 | 2012-12-12 | 广州晶锐信息技术有限公司 | LED (light-emitting diode) driving circuit and control method thereof |
| CN104038039A (en) * | 2014-06-20 | 2014-09-10 | 东南大学 | Starting circuit of monocyclic-control III-shaped compensation CUK-type switch converter |
Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN107425721A (en) * | 2017-06-13 | 2017-12-01 | 西安交通大学 | A kind of tri-state multi output interface circuit for solar energy collecting |
| CN107425721B (en) * | 2017-06-13 | 2019-12-24 | 西安交通大学 | Three-state multi-output interface circuit for solar energy collection |
| CN108563275A (en) * | 2018-04-16 | 2018-09-21 | 电子科技大学 | A kind of no quiescent dissipation trims switching circuit |
| CN108649934A (en) * | 2018-05-31 | 2018-10-12 | 成都锐成芯微科技股份有限公司 | A kind of hysteresis comparator circuit |
| CN110176860A (en) * | 2019-06-18 | 2019-08-27 | 浙江工业大学之江学院 | The boost converter of the current compensation branch containing output |
| CN110176860B (en) * | 2019-06-18 | 2024-05-28 | 浙江天青环保科技有限公司 | Boost converter with output current compensation branch |
| CN112290791A (en) * | 2020-05-18 | 2021-01-29 | 珠海市杰理科技股份有限公司 | Boost type hysteresis switch converter, control method, chip and electronic equipment |
| CN114546013A (en) * | 2022-01-26 | 2022-05-27 | 中山大学 | Reference starting circuit for detecting current by adopting comparator with mismatch |
Also Published As
| Publication number | Publication date |
|---|---|
| CN105337499B (en) | 2018-01-16 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105337499A (en) | Underloading current compensation circuit of cuk type switching convertor | |
| US9960682B2 (en) | Single inductor positive and negative voltage output device | |
| CN102364855B (en) | Switch converter and control circuit and control method thereof | |
| US9525283B2 (en) | Output overvoltage protection method and circuit for switching power supply and switching power supply thereof | |
| CN110427064B (en) | DC-DC converter | |
| KR101366683B1 (en) | Power converter, power management circuit having the same, and method of power converting | |
| CN104638722B (en) | Battery charging system based on digital control and control circuit thereof | |
| US20110234188A1 (en) | Buck Converter with Internal Ripple Compensation | |
| US10056780B2 (en) | Power supply system, uninterruptible power supply system, and power supply method | |
| US20090034304A1 (en) | Inverter for grounded direct current source, more specifically for a photovoltaic generator | |
| TWI496399B (en) | Control module of constant on-time mode and voltage converting device thereof | |
| WO2022142625A1 (en) | Oscillator for switching converter, and switching converter | |
| CN103887958A (en) | DC-DC converter | |
| CN103051187A (en) | Switching power supply circuit under double ring control | |
| CN104184319A (en) | Charge pump circuit as well as control circuit and control method thereof | |
| CN103929048A (en) | Zero-crossing detection circuit of switching power supply | |
| CN107911022A (en) | A kind of control system of peak current mode cuk switch converters | |
| CN105356738B (en) | A kind of start-up circuit for cuk type switch converters | |
| CN110504826B (en) | LED driving system, ripple removing circuit and method | |
| TWI651922B (en) | Non-isolated transformer type single-phase converter | |
| CN102468754A (en) | Circuit and method for controlling power converter in current mode | |
| CN109639151A (en) | Constant-current control circuit and constant current control method for LLC resonant converter | |
| CN104038039B (en) | Starting circuit of monocyclic-control III-shaped compensation CUK-type switch converter | |
| CN101604906A (en) | Triangular-wave generator and switch regulator | |
| CN208112220U (en) | A kind of protective relaying device power supply power-fail holding realization circuit |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant | ||
| TR01 | Transfer of patent right |
Effective date of registration: 20190412 Address after: 211100 Room 202, Zhongguancun Software Park, No. 7 Yingcui Road, Jiangning Development Zone, Nanjing City, Jiangsu Province Patentee after: Nanjing Guozhao Photoelectric Technology Co., Ltd. Address before: 210016 No. 524 Zhongshan East Road, Nanjing, Jiangsu Province Patentee before: No.55 Inst., China Electronic Science and Technology Group Corp. |
|
| TR01 | Transfer of patent right |