CN109462421A - Signal timing recovery method and recovery device, signal demodulating method and demodulating system - Google Patents
Signal timing recovery method and recovery device, signal demodulating method and demodulating system Download PDFInfo
- Publication number
- CN109462421A CN109462421A CN201811231045.4A CN201811231045A CN109462421A CN 109462421 A CN109462421 A CN 109462421A CN 201811231045 A CN201811231045 A CN 201811231045A CN 109462421 A CN109462421 A CN 109462421A
- Authority
- CN
- China
- Prior art keywords
- signal
- timing error
- mark
- timing
- segment
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
- 238000011084 recovery Methods 0.000 title claims abstract description 85
- 238000000034 method Methods 0.000 title claims abstract description 58
- 238000012935 Averaging Methods 0.000 claims abstract description 18
- 238000005070 sampling Methods 0.000 claims description 43
- 238000004364 calculation method Methods 0.000 claims description 4
- 230000008054 signal transmission Effects 0.000 claims description 3
- 230000006641 stabilisation Effects 0.000 abstract description 7
- 238000011105 stabilization Methods 0.000 abstract description 7
- 230000033228 biological regulation Effects 0.000 abstract description 2
- 238000004422 calculation algorithm Methods 0.000 description 56
- 238000001914 filtration Methods 0.000 description 13
- 238000012545 processing Methods 0.000 description 12
- 238000010586 diagram Methods 0.000 description 10
- 230000006854 communication Effects 0.000 description 7
- 238000001228 spectrum Methods 0.000 description 7
- 238000012952 Resampling Methods 0.000 description 6
- 238000004891 communication Methods 0.000 description 6
- 230000002596 correlated effect Effects 0.000 description 4
- 230000001360 synchronised effect Effects 0.000 description 4
- 230000009471 action Effects 0.000 description 3
- 230000008569 process Effects 0.000 description 3
- 238000004088 simulation Methods 0.000 description 3
- 230000005540 biological transmission Effects 0.000 description 2
- 230000008859 change Effects 0.000 description 2
- 238000006243 chemical reaction Methods 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 2
- 239000000284 extract Substances 0.000 description 2
- PCTMTFRHKVHKIS-BMFZQQSSSA-N (1s,3r,4e,6e,8e,10e,12e,14e,16e,18s,19r,20r,21s,25r,27r,30r,31r,33s,35r,37s,38r)-3-[(2r,3s,4s,5s,6r)-4-amino-3,5-dihydroxy-6-methyloxan-2-yl]oxy-19,25,27,30,31,33,35,37-octahydroxy-18,20,21-trimethyl-23-oxo-22,39-dioxabicyclo[33.3.1]nonatriaconta-4,6,8,10 Chemical group C1C=C2C[C@@H](OS(O)(=O)=O)CC[C@]2(C)[C@@H]2[C@@H]1[C@@H]1CC[C@H]([C@H](C)CCCC(C)C)[C@@]1(C)CC2.O[C@H]1[C@@H](N)[C@H](O)[C@@H](C)O[C@H]1O[C@H]1/C=C/C=C/C=C/C=C/C=C/C=C/C=C/[C@H](C)[C@@H](O)[C@@H](C)[C@H](C)OC(=O)C[C@H](O)C[C@H](O)CC[C@@H](O)[C@H](O)C[C@H](O)C[C@](O)(C[C@H](O)[C@H]2C(O)=O)O[C@H]2C1 PCTMTFRHKVHKIS-BMFZQQSSSA-N 0.000 description 1
- 230000008901 benefit Effects 0.000 description 1
- 229910002056 binary alloy Inorganic materials 0.000 description 1
- 230000000875 corresponding effect Effects 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 238000001514 detection method Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000000605 extraction Methods 0.000 description 1
- 230000006872 improvement Effects 0.000 description 1
- 239000004615 ingredient Substances 0.000 description 1
- 230000010354 integration Effects 0.000 description 1
- 239000000203 mixture Substances 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004044 response Effects 0.000 description 1
- 239000004576 sand Substances 0.000 description 1
- 230000009466 transformation Effects 0.000 description 1
- 230000007704 transition Effects 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/69—Spread spectrum techniques
- H04B1/707—Spread spectrum techniques using direct sequence modulation
- H04B1/7073—Synchronisation aspects
- H04B1/7087—Carrier synchronisation aspects
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
- H04L27/2655—Synchronisation arrangements
- H04L27/2657—Carrier synchronisation
-
- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/26—Systems using multi-frequency codes
- H04L27/2601—Multicarrier modulation systems
- H04L27/2647—Arrangements specific to the receiver only
- H04L27/2655—Synchronisation arrangements
- H04L27/2662—Symbol synchronisation
Abstract
The present invention relates to a kind of signal timing recovery method and recovery devices, signal demodulating method and demodulating system, the signal timing recovery method, the following steps are included: receiving multi-segment signal, every segment signal includes multiple mark signals, multiple mark signal is sampled, and calculates the timing error of each mark signal；Averaging is summed up to the timing error of multiple mark signals in every segment signal, obtains the timing error average value of every segment signal；Timing error average value and the pre-determined threshold of every segment signal compare, when the number that the timing error average value of multi-segment signal is continuously more than or less than pre-determined threshold is more than preset times, sampled point adjustment points are calculated, and recovery is timed to each mark signal according to sampled point adjustment points.The problem of signal timing recovery method of the invention and recovery device, signal demodulating method and demodulating system can quickly determine Signal Regulation direction, and adjust stabilization, adjust there is no excessive adjustment or leakage.
Description
Technical field
The present invention relates to wireless communication field more particularly to a kind of signal timing recovery method and recovery devices, signal solution
Tune method and demodulating system.
Background technique
In software radio receiver, signal entrained by transmitting terminal is correctly recovered, receiving end must be known by
The start/stop time of each code element recovers binary system letter to carry out periodically sampling judgement in the intermediate time of each code element
Number.Signal in communication process delay be usually it is unknown, and due in transmission process noise, multipath effect etc. influence,
Cause the signal received asynchronous with local clock pulses, this just needs bit-synchronization algorithm, recovers with receiving symbol with frequency
With the clock signal of phase.Correct synchronised clock is the basis that receiving end correctly judges, and influences the important of error rate of system
Factor；There is no accurate bit-synchronization algorithm, it is then not possible to carry out reliable data transmission, the quality of bit synchronization performance directly affects
The performance of entire communication system.It realizes that there are many type of bit-synchronization algorithm, full simulation side can be divided into according to the difference of processing mode
Formula, Semi-digital mode and three kinds of bit-synchronization algorithm models of Digital Way are as shown in Figure 1.
Fig. 1 (a) model is that full simulation bit synchronization realizes technology, fixed by the bit synchronization for calculating input signal in analog domain
When control signal go control local clock, sampling is synchronized to signal.
Fig. 1 (b) model is half simulation synchronistic model, and the main thought of the model is by the signal after sampling by one
The digitized processing of series, extracts the deviation of input signal and local clock, changes local clock by this deviation
Phase reach bit synchronization.(a) (b) two ways requires the phase for changing local clock in due course, is unfavorable for high-speed figure letter
Number realization and integration degree it is lower.
Fig. 1 (c) is that the bit synchronization of Digital Way is current more commonly used method, the bit-synchronization algorithm ten of Digital Way
Divide the realization suitable for software radio.This method adopts the analog signal of input by a fixed local clock
Sample, the processing by the signal after sampling by total digitalization, which is realized, to be synchronized；It adopts this method, realizes simply, and convenient for number
Change and realize, the requirement to local clock substantially reduces.It is main to use the Gardner timing recovery algorithm based on interpolation method.
Gan Gardner timing recovery algorithm principle is as follows: Gardner timing recovery algorithm is the bit synchronization based on interpolation
Mode, in the bit-synchronization algorithm model of Digital Way, fixed local sampling clock cannot be guaranteed can be in the extreme point of signal
Place realizes sampling, samples at extreme value so needing to realize by changing resampling clock or input signal.Gardner timing is extensive
Double calculation method is exactly to be realized by way of changing input signal, carries out weight again using the maximum value that interpolation filter recovers signal
Sampling, Gardner timing recovery algorithm principle are as shown in Figure 2.
As shown in Fig. 2, input signal is discrete signal x (mTs), sample rate Ts, symbol period T, resampling clock is
Ti, resampling clock cycle T herei=n*T (n is a small integer).The basic thought of Gardner timing recovery algorithm is exactly,
Input signal x (mTs) pass through a D/A device and an analog filter h (t), digital signal is reverted into analog signal y
(t) resampling is carried out, synchronous output signal y (kT is obtainedi).Contained in interpolation filter model virtual D/A transformation and
Analog filter, as long as but have following three conditions, interpolation can be realized digitally completely.
Input sample sequence x (mTs)
Interpolation filter impulse response h (t)
Input sample time TsWith output sampling time Ti
That is, the D/A and analog filter in figure can be real by way of designing digital interpolation filter
It is existing.Here TsAnd TiFor two fixed variables, Ts/TiNot necessarily integer leads to represent the conversion process between them
It crosses conversion and obtains TiAnd TsRelationship as shown by the equation.
mkFor the integer part of ratio, a basic pointer can be regarded as, illustrate local resampling clock TiIt is to sample rate
TsInput signal the integral multiple resampling moment, and ukFor the fractional part of ratio, indicates filter and input signal is inserted
It is worth the moment.A kind of typical Gardner timing recovery algorithm structural block diagram is as shown in Figure 3.
The analog input signal x (t) that character rate is T is by local fixed clock cycle TsBecome discrete signal after sampling
x(mTs)(TsMeet the basic Sampling Theorem of Nyquist with T).Timing Error Detector is sent by the value that interpolation filter obtains
It obtains the phase error τ (n) of input signal and local clock, then noise and high frequency therein is filtered out by a loop filter
Obtained value e (n) feeding digital controlled oscillator is calculated integer samples moment m by ingredientkWith interpolation filter interpolation point position uk
To obtain timing output y (kTi)。
As can be seen from Figure 3 a complete timing recovery algorithm mainly by Timing Error Detector, loop filter,
Digital controlled oscillator and interpolation filter composition.Its loop filter and the loop filter of Carrier Synchronization Algorithm in previous chapter are set
Meter method is identical.
Existing gardner algorithm needs filtering interpolation, and the resource of consuming is relatively more, while being easy by filter order,
Coefficient is affected, and under different channel and noise situations, is constantly corrected to filter noise needs, design comparison is numerous
It is trivial.
Ganrder algorithm is a kind of the timing-error estimation for not needing first to carry out carrier synchronization.This method is one
The non-judgement pointing method of kind, basic thought is: the amplitude and change in polarity information of adjacent symbol optimum sampling point are extracted, then
In addition whether adjacent symbol transition point is zero this information, so that it may extract timing error from sampled signal.It is set in system
Gardner phaselocked loop is located at after Costas carrier synchronization phaselocked loop in meter, is generally mainly made of four parts: interpolater, when
Clock error extraction module, loop filter and controller module.The sampled point of mutually orthogonal I, Q two paths of signals passes through operation
A timing error sampling point can be generated during each symbol.Timing error sequence is filtered by loop by Timing Error Detection
Digital controlled oscillator is given after wave device, state modulator interpolation filter is generated by digital controlled oscillator, last interpolation filter is adopted
Sample moment adjustment, to complete entire symbol synchronization process.How timing error sequence generated by the sampled point that receives, this is
The key point of Gardner algorithm.And current ganrder algorithm needs interpolation filtering, compares consuming resource.
Therefore it provides a kind of signal timing recovery method and recovery device, signal demodulating method and demodulating system.
Summary of the invention
In view of the above problems, it proposes on the present invention overcomes the above problem or at least be partially solved in order to provide one kind
The signal timing recovery method and recovery device, signal demodulating method and demodulating system for stating problem, save traditional gardner algorithm
Filtering processing resource, can quickly determine the adjusting direction of system, and adjust stabilization, there is no excessive adjustment or
Person leaks the problem of adjusting.
According to an aspect of the present invention, a kind of signal timing recovery method is provided, comprising the following steps:
Multi-segment signal is received, every segment signal includes multiple mark signals, is sampled to multiple mark signal, and calculate
The timing error of each mark signal；
Averaging is summed up to the timing error of multiple mark signals in every segment signal, show that the timing of every segment signal misses
Poor average value；
Timing error average value and the pre-determined threshold of every segment signal compare, when the timing error average value of multi-segment signal
When the continuous number more than or less than pre-determined threshold is more than preset times, sampled point adjustment points are calculated, and according to sampled point tune
Integral point number is timed recovery to each mark signal.
Further, over-sampling is carried out to multiple mark signal, is calculated by the following formula adopting in each mark signal
Sampling point number:
BL=fS/Rb
Wherein, BL is the number of sampling points in each mark signal, fSFor sampling rate, Rb is character rate.
Further, it is calculated by the following formula the timing error of each mark signal:
Wherein, u (r) is the timing error of mark signal r,For the sampling of mark signal r and mark signal r-1
The interpolated value on the point road intermediate time I,For in the road sampled point intermediate time Q of mark signal r and mark signal r-1
Interpolation, xIIt (r) is the sampled point on the road I of mark signal r, xQIt (r) is the sampled point on the road Q of mark signal r, xIIt (r-1) is symbol
The sampled point on the road I of signal r-1, xQIt (r-1) is the sampled point on the road Q of mark signal r-1.
Further, it is summed up by timing error of the following formula to multiple mark signals in every segment signal and asks flat
It is equal:
Wherein, UiFor the average value of u (r) in i-th section of mark signal, P is i-th section of mark signal number, i=1,2 ....
Further, pre-determined threshold 0.
Further, recovery is timed to each mark signal according to sampled point adjustment points by following formula:
NewST=newST+sign (▽ ε) * move；
Wherein, newST is former sampling point position, and ▽ ε is the fractional part timing error factor, and sign (▽ ε) is tape symbol
The fractional part timing error factor, move is the points once moved, and sign (▽ ε) * move is sampled point adjustment points.
Further, it is calculated by the following formula the fractional part timing error factor:
Wherein, UiFor the average value of u (r) in i-th section of mark signal, ▽ εiFor the fractional part timing of i-th section of mark signal
Error factor.
According to another aspect of the present invention, a kind of signal timing recovery device realized such as the above method is provided, comprising:
The timing error computing module of mark signal, for receiving multi-segment signal, every segment signal includes multiple mark signals,
Multiple mark signal is sampled, and calculates the timing error of each mark signal；
Timing error mean value calculation module is summed up for the timing error to multiple mark signals in every segment signal
It is averaging, obtains the timing error average value of every segment signal；
Signal timing recovery module, timing error average value and pre-determined threshold for every segment signal compare, when more
When the number that the timing error average value of segment signal is continuously more than or less than pre-determined threshold is more than preset times, sampled point tune is calculated
Integral point number, and recovery is timed to each mark signal according to sampled point adjustment points.
According to another aspect of the invention, providing a kind of includes that the signal demodulation of above-mentioned signal timing recovery device such as is
System, comprising:
Signal pickup assembly for acquiring signal, and is sent to PN synchronization device；
PN synchronization device for carrying out PN synchronization to signal, and is sent to despreading device；
Despreading device for receiving and de-spreading to the signal after PN synchronization, and is sent to signal timing recovery dress
It sets；
Carrier synchronization device, the signal after bit synchronization for receiving the transmission of signal timing recovery device, and to the signal
Carry out carrier synchronization；
Signal demodulating equipment, for receiving and being demodulated to the signal after carrier synchronization, the signal after being demodulated.
It is according to the present invention also on the one hand to provide a kind of signal demodulating method realized based on above-mentioned signal demodulating system,
The following steps are included:
Acquire signal；
PN synchronization is carried out to the signal of acquisition；
Signal after PN synchronization is de-spread；
Multi-segment signal after receiving despreading, every segment signal includes multiple mark signals, is adopted to multiple mark signal
Sample, and calculate the timing error of each mark signal；
Averaging is summed up to the timing error of multiple mark signals in every segment signal, show that the timing of every segment signal misses
Poor average value；
Timing error average value and the pre-determined threshold of every segment signal compare, when the timing error average value of multi-segment signal
When the continuous number more than or less than pre-determined threshold is more than preset times, sampled point adjustment points are calculated, and according to sampled point tune
Integral point number is timed recovery to each mark signal；
Carrier synchronization is carried out to the signal after Timed Recovery；
Signal after carrier synchronization is demodulated, the signal after being demodulated.
The present invention has the advantage that compared with prior art
1. signal timing recovery method of the invention and recovery device, signal demodulating method and demodulating system are by repeatedly asking
It is averaging after taking timing error arithmetic to be superimposed and obtains average timing error, average timing error is judged, be more than pre- gating
It is overlapped judgement after limit, after the number that average timing error continues to exceed pre-determined threshold is greater than preset times, carries out primary true
Positive loop updates, so that the Timed Recovery of signal is not necessarily to filter coefficients, it is only necessary to and two-dimentional average algorithm can reach stable state,
The resource of the filtering processing of traditional gardner algorithm is saved, can quickly determine and adjust direction, and adjust stabilization, it will not
There are problems that excessively adjusting or leakage is adjusted；
2. in signal timing recovery method of the invention and recovery device, signal demodulating method and demodulating system
Gardner bit-synchronization algorithm can not depend on carrier synchronization device independently of carrier synchronization, thus significantly reduce signal solution
Algorithm is associated with bring algorithm complexity in tune.
Detailed description of the invention
Below in conjunction with drawings and examples, the invention will be further described.
Fig. 1 (a) is full analog form bit-synchronization algorithm model；
Fig. 1 (b) is Semi-digital mode bit-synchronization algorithm model；
Fig. 1 (c) is Digital Way bit-synchronization algorithm model；
Fig. 2 is Gardner timing recovery algorithm principle；
Fig. 3 is Gardner timing recovery algorithm structural block diagram；
Fig. 4 is the signal timing recovery method and step figure of the embodiment of the present invention；
Fig. 5 is the signal timing recovery method instance graph of the embodiment of the present invention；
Fig. 6 is that the average Ui numerical value obtained later and pre-determined threshold compare signal to u (r) each time in the embodiment of the present invention
Figure；
Fig. 7 is the direction schematic diagram that signal sampling point actually adjusts each time in the embodiment of the present invention；
Fig. 8 be the gardner sign synchronization of the embodiment of the present invention before sample amplitude；
Fig. 9 is the symbol amplitude after the gardner sign synchronization of the embodiment of the present invention；
Figure 10 is the signal timing recovery device block diagram of the embodiment of the present invention；
Figure 11 is the signal demodulating method block diagram of the embodiment of the present invention；
Figure 12 is the signal constellation (in digital modulation) figure after the gardner sign synchronization of the embodiment of the present invention；
Figure 13 is the signal demodulating system block diagram of the embodiment of the present invention.
Specific embodiment
Exemplary embodiments of the present disclosure are described in more detail below with reference to accompanying drawings.Although showing the disclosure in attached drawing
Exemplary embodiment, it being understood, however, that may be realized in various forms the disclosure without should be by embodiments set forth here
It is limited.On the contrary, these embodiments are provided to facilitate a more thoroughly understanding of the present invention, and can be by the scope of the present disclosure
It is fully disclosed to those skilled in the art.
Those skilled in the art of the present technique are appreciated that unless expressly stated, singular " one " used herein, " one
It is a ", " described " and "the" may also comprise plural form.It is to be further understood that being arranged used in specification of the invention
Diction " comprising " refer to that there are the feature, integer, step, operation, element and/or component, but it is not excluded that in the presence of or addition
Other one or more features, integer, step, operation, element, component and/or their group.
Those skilled in the art of the present technique are appreciated that unless otherwise defined, all terms used herein (including technology art
Language and scientific term), there is meaning identical with the general understanding of those of ordinary skill in fields of the present invention.Should also
Understand, those terms such as defined in the general dictionary, it should be understood that have in the context of the prior art
The consistent meaning of meaning, and unless otherwise will not be explained in an idealized or overly formal meaning by specific definitions.
Fig. 4 is the signal timing recovery method and step figure of the embodiment of the present invention, as shown in figure 4, signal provided by the invention
Timing recovery method, comprising the following steps:
Multi-segment signal is received, every segment signal includes multiple mark signals, is sampled to multiple mark signal, and calculate
The timing error of each mark signal；
Averaging is summed up to the timing error of multiple mark signals in every segment signal, show that the timing of every segment signal misses
Poor average value；
Timing error average value and the pre-determined threshold of every segment signal compare, when the timing error average value of multi-segment signal
When the continuous number more than or less than pre-determined threshold is more than preset times, sampled point adjustment points are calculated, and according to sampled point tune
Integral point number is timed recovery to each mark signal.
Wherein, pre-determined threshold and preset times are set as needed, such as pre-determined threshold can be 0, preset times can be with
It is 2~5 times.
Over-sampling is carried out to multiple mark signal, the number of sampling points being calculated by the following formula in each mark signal:
BL=fS/Rb
Wherein, BL is the number of sampling points in each mark signal, fSFor sampling rate, Rb is character rate.
It is calculated by the following formula the timing error of each mark signal:
Wherein, u (r) is the timing error of mark signal r,For the sampling of mark signal r and mark signal r-1
The interpolated value on the point road intermediate time I,For in the road sampled point intermediate time Q of mark signal r and mark signal r-1
Interpolation, xIIt (r) is the sampled point on the road I of mark signal r, xQIt (r) is the sampled point on the road Q of mark signal r, xIIt (r-1) is symbol
The sampled point on the road I of signal r-1, xQIt (r-1) is the sampled point on the road Q of mark signal r-1.
In practical applications, a symbol or a BIT are optionally oversampled, such as the sampling rate of signal is fs=
16mhz, character rate Rb=32khz, then over-sampling BL=fs/Rb=500, a QPSK symbol by BL=500 times of over-sampling,
So a symbol needs BL=500 sampling point to obtain this sign magnitude.Therefore x in formulaI(r),
xIIt (r-1) etc. is all BL point as a result, xI(r) and xI(r-1) BL point, x are differedI(r) and xI(r-1/2) BL/2 is differed
=250 points.Wherein, a BIT represents a symbol, and the two is of equal value, is all comprising BL sampled point.
Averaging is summed up by timing error of the following formula to multiple mark signals in every segment signal:
Wherein, UiFor the average value of u (r) in i-th section of mark signal, P is i-th section of mark signal number, i=1,2 ....
It is calculated by the following formula the fractional part timing error factor:
Wherein, UiFor the average value of u (r) in i-th section of mark signal, ▽ εiFor the fractional part timing of i-th section of mark signal
Error factor.Therefore, using tracking mode structure, according to the symbol of u (r) average value in one section of symbol to fractional part timing errorIt is adjusted.Δ ε is the stepping adjusted every time.Δ ε is bigger, and the traceable inclined range of code is bigger, but Timing error estimate value
Precision it is also lower, need when application to determine Δ ε according to actual requirement.Initial fractional part timing error factor ▽ εiIt is
Unknown, generally by ▽ εiIt is set as ▽ ε0=0.It and is not to obtain new ▽ ε each timeiJust remove more new signal immediately afterwards
Tandem, but ▽ εiGreater than certain numerical value, illustrate that a past direction continues for some time and be just adjusted | ▽ εi| > Num.
Recovery is timed to each mark signal according to sampled point adjustment points by following formula:
NewST=newST+sign (▽ ε) * move；
Wherein, newST is former sampling point position, and ▽ ε is the fractional part timing error factor, and sign (▽ ε) is tape symbol
The fractional part timing error factor, move is the points once moved, and sign (▽ ε) * move is sampled point adjustment points.
Signal timing recovery method of the invention after repeatedly seeking the superposition of timing error arithmetic by being averaged
Timing error judges that average timing error, more than judgement is overlapped after pre-determined threshold, average timing error continuously surpasses
The number for crossing pre-determined threshold is updated greater than primary really loop after preset times, is carried out, so that the Timed Recovery of signal is not necessarily to
Filter coefficients, it is only necessary to which two-dimentional average algorithm can reach stable state, save the money of the filtering processing of traditional gardner algorithm
The problem of source can quickly determine and adjust direction, and adjust stabilization, adjust there is no excessive adjustment or leakage, and energy
It is enough to be suitble to search plain optimum sampling point and correlated series superposition using large scale spread-spectrum signal.
Gardner bit-synchronization algorithm in signal timing recovery method of the invention can be disobeyed independently of carrier synchronization
Rely carrier synchronization device, thus significantly reduces algorithm association bring algorithm complexity, such gardner in signal demodulation
Algorithm can save the resource of the filtering processing of traditional gardner algorithm, can quickly determine the adjusting direction of system, and
The problem of adjusting and stablize, adjusting there is no excessive adjustment or leakage, has very big practicability.It is logical to can be widely applied for spread spectrum
Letter, the carrier wave communication systems such as BPSK/QPSK.
Fig. 5 is the signal timing recovery method instance graph of the embodiment of the present invention, as shown in figure 5, the first step, is arranged primary move
Average P_BIT quantity, the pre-determined threshold THr of setting adjustment zero are asked once in dynamic points move=1/8BIT, setting；Second
Step obtains the BIT sampled point of front one and indexes index1, and the signal arithmetic sum of index1 sampled point obtains x (r-1), current BIT
Sampled point indexes index3, and the signal arithmetic sum of index3 sampled point obtains x (r), and intermediate samples point indexes index2, index1
Second half section and index3 front half section group are combined into index2, and the signal arithmetic sum of index2 sampled point obtains x (r-1/2), for example, preceding
BIT (symbol) the sampled point index in face is ABCD (1,2,3,4), behind BIT index be EFGH (5,6,7,8), then middle position
Index is (3,4,5,6) CDEF, and signal output is x (r)；Third step, calculates the timing error of symbol r, and formula is
When running up to P_BIT symbol, P_BIT symbol calculates the flat of u (r) in this section of symbol as one section of symbol
Mean value U；According to the size relation of U and pre-determined threshold THr, when U is greater than THr, Δ ε=- 1, when U is less than-THr, Δ ε=1,
When U is between-THr and THr, Δ ε=0；▽ ε=Δ ε+▽ ε, generally by ▽ εiIt is set as ▽ ε0=0, when | ▽ εi| > Num
When, the position of sampled point is just adjusted, and assign ▽ ε again0=0.
In Fig. 5 key be to signal after multiple gardner calculating, seek once average, pass through average directionality
Judge the directionality adjusted, is carried out again after having asked average once smoothly, it is average so that this continuous multiple BIT adjusts the whole of direction
Body trend thus is avoided that since noise or interference cause the erroneous judgement of sense.Gear becomes 3 by pervious 2 grades simultaneously
Shelves increase a not regulation stall, enhance the stability of system and improve precision, need not be without adjusting.One BIT is represented
One symbol, the two is of equal value, is all comprising BL sampled point.The gardner tune of complete set is formed by above-mentioned 3 key points
Throttle journey.
Input signal is adjusted according to the timing error that Gardner algorithm is calculated, signal output speed adjusted
Rate is 2 times of character rates, including the value of optimum sampling point all the way, as the result output after sign synchronization.
Fig. 6 is that the average Ui numerical value obtained later and pre-determined threshold compare signal to u (r) each time in the embodiment of the present invention
Figure shakes still more violent, the initial stage as shown in fig. 6, Fig. 6 shows the numerical value being once averaging, and Ui is to a direction
Adjust, numerical value is all positive number, in after stage positive negative have an adjusting, direction changes.
Fig. 7 is the direction schematic diagram that signal sampling point actually adjusts each time in the embodiment of the present invention, and as shown in Figure 7 is every
The direction once actually adjusted, obtains an adjusting value added according to direction due to shaking each time, and it is continuous that this increases numerical value
Being added to preset times just can really be adjusted.Wherein, adjusting size is fixed, and 1 indicates backward to adjust, and 0 indicates not adjust, and -1
Expression is back adjusted.
Fig. 8 be the gardner sign synchronization of the embodiment of the present invention before sample amplitude, as shown in figure 8, gardner
Signal amplitude changes acutely before sign synchronization, at all can not demodulated signal.
Fig. 9 is the symbol amplitude after the gardner sign synchronization of the embodiment of the present invention, as shown in figure 9, being basis below
Signal amplitude after gardner sign synchronization, the signal amplitude are the amplitude after BL sampling point, meanwhile, BL's
For numerical values recited still constantly in adjusting, adjusting size and direction are sign (▽ ε) * move.
For embodiment of the method, for simple description, therefore, it is stated as a series of action combinations, but this field
Technical staff should be aware of, and embodiment of that present invention are not limited by the describe sequence of actions, because implementing according to the present invention
Example, some steps may be performed in other sequences or simultaneously.Secondly, those skilled in the art should also know that, specification
Described in embodiment belong to preferred embodiment, the actions involved are not necessarily necessary for embodiments of the present invention.
Figure 10 is the signal timing recovery device block diagram of the embodiment of the present invention, as shown in Figure 10, realization provided by the invention
Such as the signal timing recovery device of the above method, comprising:
The timing error computing module of mark signal, for receiving multi-segment signal, every segment signal includes multiple mark signals,
Multiple mark signal is sampled, and calculates the timing error of each mark signal；
Timing error mean value calculation module is summed up for the timing error to multiple mark signals in every segment signal
It is averaging, obtains the timing error average value of every segment signal；
Signal timing recovery module, timing error average value and pre-determined threshold for every segment signal compare, when more
When the number that the timing error average value of segment signal is continuously more than or less than pre-determined threshold is more than preset times, sampled point tune is calculated
Integral point number, and recovery is timed to each mark signal according to sampled point adjustment points.
The signal timing recovery device of the embodiment of the present invention is that two-stage is superimposed gardner loop optimum sampling point acquisition dress
It sets, two-stage superposition specifically: first is superimposed after being averaged, and averaging obtains U after repeatedly seeking the superposition of timing error u arithmetic；The
Second is that judging U, more than judgement is overlapped after certain thresholding THr, Ui carries out arithmetic superposition again, obtains more than Num times
Primary really loop is just carried out later to update.
Signal timing recovery device of the invention after repeatedly seeking the superposition of timing error arithmetic by being averaged
Timing error judges that average timing error, more than judgement is overlapped after pre-determined threshold, average timing error continuously surpasses
The number for crossing pre-determined threshold is updated greater than primary really loop after preset times, is carried out, so that the Timed Recovery of signal is not necessarily to
Filter coefficients, it is only necessary to which two-dimentional average algorithm can reach stable state, save the money of the filtering processing of traditional gardner algorithm
The problem of source can quickly determine and adjust direction, and adjust stabilization, adjust there is no excessive adjustment or leakage, and energy
It is enough to be suitble to search plain optimum sampling point and correlated series superposition using large scale spread-spectrum signal.
Gardner bit-synchronization algorithm in signal timing recovery device of the invention can be disobeyed independently of carrier synchronization
Rely carrier synchronization device, thus significantly reduces algorithm association bring algorithm complexity, such gardner in signal demodulation
Algorithm can save the resource of the filtering processing of traditional gardner algorithm, can quickly determine the adjusting direction of system, and
The problem of adjusting and stablize, adjusting there is no excessive adjustment or leakage, has very big practicability.It is logical to can be widely applied for spread spectrum
Letter, the carrier wave communication systems such as BPSK/QPSK.
For device embodiment, since it is basically similar to the method embodiment, related so being described relatively simple
Place illustrates referring to the part of embodiment of the method.
Figure 11 is the signal demodulating system block diagram of the embodiment of the present invention, and as shown in figure 11, provided by the invention includes as above
State the signal demodulating system of signal timing recovery device, comprising:
Signal pickup assembly for acquiring signal, and is sent to PN synchronization device；
PN synchronization device for carrying out PN synchronization to signal, and is sent to despreading device；
Despreading device for receiving and de-spreading to the signal after PN synchronization, and is sent to signal timing recovery dress
It sets；
Carrier synchronization device, the signal after bit synchronization for receiving the transmission of signal timing recovery device, and to the signal
Carry out carrier synchronization；
Signal demodulating equipment, for receiving and being demodulated to the signal after carrier synchronization, the signal after being demodulated.
In signal demodulating system of the invention, signal timing recovery device can not depend on load independently of carrier synchronization
Wave synchronizing device, thus significantly reducing algorithm association and bringing is algorithm complexity, and the substantially process flow of algorithm is as follows, connects
The chip signal that despreading comes is received, the search of BIT location boundary is carried out, then completes the superposition of more chip signals, export low speed
Data output.Gardner timing error is obtained according to previous signal and latter signal and M signal simultaneously, to timing
Error signal is averaging and smoothly obtains the adjustment of optimum sampling point.
Signal demodulating system of the invention obtains average timing by averaging after repeatedly seeking the superposition of timing error arithmetic
Error judges that average timing error, more than judgement is overlapped after pre-determined threshold, average timing error continues to exceed pre-
After the number of gating limit is greater than preset times, carries out primary really loop and update, so that the Timed Recovery of signal is without filtering
Interpolation, it is only necessary to which two-dimentional average algorithm can reach stable state, save the resource of the filtering processing of traditional gardner algorithm, energy
The problem of enough quickly determine adjusts direction, and adjusts stabilization, adjusts there is no excessive adjustment or leakage, and can be suitble to
Plain optimum sampling point and correlated series superposition are searched using large scale spread-spectrum signal.
Figure 12 is the signal constellation (in digital modulation) figure after the gardner sign synchronization of the embodiment of the present invention, and as shown in figure 12, code is same
In signal constellation (in digital modulation) figure after step, sign synchronization and carrier synchronization, the position of constellation point is concentrated very much, is solved at this time to signal
It adjusts, the bit error rate will be greatly reduced.
Figure 13 is the signal demodulating method block diagram of the embodiment of the present invention, as shown in figure 13, provided by the invention based on upper
State the signal demodulating method of signal demodulating system realization, comprising the following steps:
Acquire signal；
PN synchronization is carried out to the signal of acquisition；
Signal after PN synchronization is de-spread；
Multi-segment signal after receiving despreading, every segment signal includes multiple mark signals, is adopted to multiple mark signal
Sample, and calculate the timing error of each mark signal；
Averaging is summed up to the timing error of multiple mark signals in every segment signal, show that the timing of every segment signal misses
Poor average value；
Timing error average value and the pre-determined threshold of every segment signal compare, when the timing error average value of multi-segment signal
When the continuous number more than or less than pre-determined threshold is more than preset times, sampled point adjustment points are calculated, and according to sampled point tune
Integral point number is timed recovery to each mark signal；
Carrier synchronization is carried out to the signal after Timed Recovery；
Signal after carrier synchronization is demodulated, the signal after being demodulated.
Signal demodulating system of the invention obtains average timing by averaging after repeatedly seeking the superposition of timing error arithmetic
Error judges that average timing error, more than judgement is overlapped after pre-determined threshold, average timing error continues to exceed pre-
After the number of gating limit is greater than preset times, carries out primary really loop and update, so that the Timed Recovery of signal is without filtering
Interpolation, it is only necessary to which two-dimentional average algorithm can reach stable state, save the resource of the filtering processing of traditional gardner algorithm, energy
The problem of enough quickly determine adjusts direction, and adjusts stabilization, adjusts there is no excessive adjustment or leakage, and can be suitble to
Plain optimum sampling point and correlated series superposition are searched using large scale spread-spectrum signal.Device after such improvement is called that " two-stage is folded
Adding gardner loop-is to be averaging to obtain U after repeatedly seeking the superposition of timing error u arithmetic, and second is judged U, is more than
It is overlapped judgement after certain thresholding THr, Ui carries out arithmetic superposition again, just carries out after obtaining more than Num times primary real
Loop updates " optimum sampling device.
Gardner bit-synchronization algorithm in signal demodulating system of the invention can not depend on load independently of carrier synchronization
Wave synchronizing device thus significantly reduces algorithm association bring algorithm complexity, such gardner algorithm in signal demodulation
The resource of the filtering processing of traditional gardner algorithm can be saved, can quickly determine the adjusting direction of system, and adjust
The problem of stablizing, adjusting there is no excessive adjustment or leakage, has very big practicability.It can be widely applied for spread spectrum communication,
The carrier wave communication systems such as BPSK/QPSK.
The above embodiments are merely illustrative of the technical solutions of the present invention, rather than its limitations；Although with reference to the foregoing embodiments
Invention is explained in detail, those skilled in the art should understand that: it still can be to aforementioned each implementation
Technical solution documented by example is modified or equivalent replacement of some of the technical features；And these modification or
Replacement, the spirit and scope for technical solution of various embodiments of the present invention that it does not separate the essence of the corresponding technical solution.
Claims (10)
1. a kind of signal timing recovery method, which comprises the following steps:
Multi-segment signal is received, every segment signal includes multiple mark signals, is sampled to multiple mark signal, and calculate each symbol
The timing error of number signal；
Averaging is summed up to the timing error of multiple mark signals in every segment signal, show that the timing error of every segment signal is flat
Mean value；
Timing error average value and the pre-determined threshold of every segment signal compare, when the timing error average value of multi-segment signal is continuous
When number more than or less than pre-determined threshold is more than preset times, sampled point adjustment points are calculated, and point is adjusted according to sampled point
It is several that recovery is timed to each mark signal.
2. signal timing recovery method according to claim 1, which is characterized in that adopted to multiple mark signal
Sample, the number of sampling points being calculated by the following formula in each mark signal:
BL=fS/Rb
Wherein, BL is the number of sampling points in each mark signal, fSFor sampling rate, Rb is character rate.
3. signal timing recovery method according to claim 2, which is characterized in that be calculated by the following formula each symbol letter
Number timing error:
Wherein, u (r) is the timing error of mark signal r,For in the sampled point of mark signal r and mark signal r-1
Between moment I road interpolated value,For the interpolation on the road sampled point intermediate time Q of mark signal r and mark signal r-1
Value, xIIt (r) is the sampled point on the road I of mark signal r, xQIt (r) is the sampled point on the road Q of mark signal r, xI(r-1) believe for symbol
The sampled point on the road I of number r-1, xQIt (r-1) is the sampled point on the road Q of mark signal r-1.
4. signal timing recovery method according to claim 3, which is characterized in that by following formula in every segment signal
The timing error of multiple mark signals sums up averaging:
Wherein, UiFor the average value of u (r) in i-th section of mark signal, P is i-th section of mark signal number, i=1,2 ....
5. signal timing recovery method according to claim 4, which is characterized in that pre-determined threshold 0.
6. signal timing recovery method according to claim 5, which is characterized in that by following formula according to sampled point tune
Integral point number is timed recovery to each mark signal:
NewST=newST+sign (▽ ε) * move；
Wherein, newST is former sampling point position, and ▽ ε is the fractional part timing error factor, and sign (▽ ε) is the small of tape symbol
The number part timing error factor, move are the points once moved, and sign (▽ ε) * move is sampled point adjustment points.
7. signal timing recovery method according to claim 6, which is characterized in that be calculated by the following formula fractional part
The timing error factor:
Wherein, UiFor the average value of u (r) in i-th section of mark signal, ▽ εiFor the fractional part timing error of i-th section of mark signal
The factor.
8. a kind of signal timing recovery device for realizing method as described in claim 1 characterized by comprising
The timing error computing module of mark signal, for receiving multi-segment signal, every segment signal includes multiple mark signals, to this
Multiple mark signals are sampled, and calculate the timing error of each mark signal；
Timing error mean value calculation module sums up for the timing error to multiple mark signals in every segment signal and asks flat
, the timing error average value of every segment signal is obtained；
Signal timing recovery module, timing error average value and pre-determined threshold for every segment signal compare, when multistage is believed
Number timing error average value be continuously more than or less than pre-determined threshold number be more than preset times when, calculate sampled point adjust point
Number, and recovery is timed to each mark signal according to sampled point adjustment points.
9. a kind of signal demodulating system including signal timing recovery device as claimed in claim 8 characterized by comprising
Signal pickup assembly for acquiring signal, and is sent to PN synchronization device；
PN synchronization device for carrying out PN synchronization to signal, and is sent to despreading device；
Despreading device for receiving and de-spreading to the signal after PN synchronization, and is sent to signal timing recovery device；
Carrier synchronization device, the signal after bit synchronization for receiving the transmission of signal timing recovery device, and the signal is carried out
Carrier synchronization；
Signal demodulating equipment, for receiving and being demodulated to the signal after carrier synchronization, the signal after being demodulated.
10. a kind of signal demodulating method based on system described in claim 9, which comprises the following steps:
Acquire signal；
PN synchronization is carried out to the signal of acquisition；
Signal after PN synchronization is de-spread；
Multi-segment signal after receiving despreading, every segment signal includes multiple mark signals, is sampled to multiple mark signal, and
Calculate the timing error of each mark signal；
Averaging is summed up to the timing error of multiple mark signals in every segment signal, show that the timing error of every segment signal is flat
Mean value；
Timing error average value and the pre-determined threshold of every segment signal compare, when the timing error average value of multi-segment signal is continuous
When number more than or less than pre-determined threshold is more than preset times, sampled point adjustment points are calculated, and point is adjusted according to sampled point
It is several that recovery is timed to each mark signal；
Carrier synchronization is carried out to the signal after Timed Recovery；
Signal after carrier synchronization is demodulated, the signal after being demodulated.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201811231045.4A CN109462421B (en) | 2018-10-22 | 2018-10-22 | Signal timing recovery method and recovery device, signal demodulation method and demodulation system |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201811231045.4A CN109462421B (en) | 2018-10-22 | 2018-10-22 | Signal timing recovery method and recovery device, signal demodulation method and demodulation system |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN109462421A true CN109462421A (en) | 2019-03-12 |
| CN109462421B CN109462421B (en) | 2020-10-23 |
Family
ID=65608063
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201811231045.4A Active CN109462421B (en) | 2018-10-22 | 2018-10-22 | Signal timing recovery method and recovery device, signal demodulation method and demodulation system |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN109462421B (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110855317A (en) * | 2019-08-15 | 2020-02-28 | 熊军 | Non-uniform spread spectrum synchronization method |
| CN111130595A (en) * | 2019-12-23 | 2020-05-08 | 东方红卫星移动通信有限公司 | Low-earth-orbit satellite feed link timing synchronization method |
| CN112543064A (en) * | 2020-12-02 | 2021-03-23 | 武汉邮电科学研究院有限公司 | Clock recovery device and method for high-speed coherent optical communication system |
Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102355443A (en) * | 2011-08-18 | 2012-02-15 | 广州海格通信集团股份有限公司 | Method for realizing federated filtering and timing synchronization in digital communication system |
| CN104821871A (en) * | 2015-03-11 | 2015-08-05 | 南京航空航天大学 | 16 quadrature amplitude modulation (QAM) demodulation synchronization method |
| CN108306839A (en) * | 2018-01-16 | 2018-07-20 | 上海富芮坤微电子有限公司 | A kind of demodulator circuit and construction method applied to GFSK receivers |
-
2018
- 2018-10-22 CN CN201811231045.4A patent/CN109462421B/en active Active
Patent Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102355443A (en) * | 2011-08-18 | 2012-02-15 | 广州海格通信集团股份有限公司 | Method for realizing federated filtering and timing synchronization in digital communication system |
| CN104821871A (en) * | 2015-03-11 | 2015-08-05 | 南京航空航天大学 | 16 quadrature amplitude modulation (QAM) demodulation synchronization method |
| CN108306839A (en) * | 2018-01-16 | 2018-07-20 | 上海富芮坤微电子有限公司 | A kind of demodulator circuit and construction method applied to GFSK receivers |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110855317A (en) * | 2019-08-15 | 2020-02-28 | 熊军 | Non-uniform spread spectrum synchronization method |
| CN111130595A (en) * | 2019-12-23 | 2020-05-08 | 东方红卫星移动通信有限公司 | Low-earth-orbit satellite feed link timing synchronization method |
| CN111130595B (en) * | 2019-12-23 | 2021-10-15 | 东方红卫星移动通信有限公司 | Low-earth-orbit satellite feed link timing synchronization method |
| CN112543064A (en) * | 2020-12-02 | 2021-03-23 | 武汉邮电科学研究院有限公司 | Clock recovery device and method for high-speed coherent optical communication system |
| CN112543064B (en) * | 2020-12-02 | 2022-02-15 | 武汉邮电科学研究院有限公司 | Clock recovery device and method for high-speed coherent optical communication system |
Also Published As
| Publication number | Publication date |
|---|---|
| CN109462421B (en) | 2020-10-23 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN105245303B (en) | A kind of high-speed burst demodulation synchronization system | |
| CN105187348B (en) | Arbitrary velocity CPFSK signal timing synchronous method | |
| CN109462421A (en) | Signal timing recovery method and recovery device, signal demodulating method and demodulating system | |
| CN102170414B (en) | Demodulation and timing synchronization combined method for GFSK (Gauss Frequency Shift Key) | |
| CN107040488B (en) | The carrier wave tracing method and tracking device of Arctic ice area based on FPGA | |
| CN106842248A (en) | A kind of new method for improving Beidou receiver timing locating speed | |
| JP2001520484A (en) | Synchronization method and system for wireless communication | |
| CN107483380A (en) | A kind of OQPSK signal high-frequency offset carrier synchronous method based on multistage architecture | |
| JPH11168455A (en) | Digital pll circuit and signal reproducing method | |
| CN108989260A (en) | The digital time synchronization method of modified and device based on Gardner | |
| CN105871765A (en) | Wireless communication carrier wave tracking method based on FFT assistant S-PLL | |
| CN105162570B (en) | Time synchronization method and device for signal parallel processing | |
| CN106817333B (en) | High dynamic carrier synchronization method based on open-loop acquisition and Closed loop track | |
| CN106656400A (en) | Accurate frequency difference fast acquisition method in time delay jitter condition of PCMA system | |
| CN100452669C (en) | Early-late synchronizer having reduced timing jitter | |
| CN107528805B (en) | PSK signal synchronization method and device suitable for signal analyzer | |
| CN111917679B (en) | Method for downloading timing synchronization of carrier and symbol under low signal-to-noise ratio condition | |
| CN110061943A (en) | A kind of symbol timing synchronization method in mpsk signal demodulation | |
| CN110880964A (en) | Bit synchronization tracking system based on data conversion tracking loop | |
| CN108712190B (en) | Multi-carrier tracking method and tracking device | |
| CN114244674B (en) | Frequency offset estimation method and device for ultra-wideband baseband receiver | |
| CN1312875C (en) | PHS system position synchronous method based on digital lock phase ring and realizing device | |
| CN106059975B (en) | Novel method for inhibiting carrier synchronization and costas ring | |
| JP5761748B2 (en) | Symbol synchronization acquisition system and method | |
| CN105072070B (en) | A kind of digital broadband wireless signal synchronized algorithm |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant | ||
| CP03 | Change of name, title or address | ||
| CP03 | Change of name, title or address |
Address after: Room 109-111, 1 / F, 17 / F, Zhongguancun Software Park, 8 Dongbeiwang West Road, Haidian District, Beijing, 100193 Patentee after: Ruixinfeng Aerospace Technology (Beijing) Co.,Ltd. Country or region after: China Address before: Room 109-111, 1 / F, 17 / F, Zhongguancun Software Park, 8 Dongbeiwang West Road, Haidian District, Beijing, 100193 Patentee before: BEIJING RINFON TECHNOLOGY Co.,Ltd. Country or region before: China |