CN107171078A - Circularly polarization microstrip duplexed antenna - Google Patents
Circularly polarization microstrip duplexed antenna Download PDFInfo
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- H—ELECTRICITY
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Abstract
本发明公开了一种圆极化微带双工天线，包括微带贴片天线、两个馈电探针、双工功率分配网络、发送端口以及接收端口；两个所述馈电探针均与所述双工功率分配网络连接；所述双工功率分配网络包括功率分配微带线、发送微带带阻滤波器、发送阻抗变换微带线、接收微带带阻滤波器和接收阻抗变换微带线；所述馈电探针包括水平微带和垂直金属探针，所述垂直金属探针的一端连接所述水平微带的中心，所述垂直金属探针的另一端与所述功率分配微带线相连。本发明设计了一个具有双工功能的微带圆极化双工天线，天线的发射与接收使用的电磁波极化方式相同，均为左旋圆极化电磁波；同时，通过设置发送和接收微带带阻滤波器，实现了发送与接收端口间的高隔离度。
The invention discloses a circularly polarized microstrip duplex antenna, which includes a microstrip patch antenna, two feeding probes, a duplex power distribution network, a sending port and a receiving port; the two feeding probes are Connected with the duplex power distribution network; the duplex power distribution network includes a power distribution microstrip line, a transmission microstrip band-stop filter, a transmission impedance transformation microstrip line, a reception microstrip band-stop filter and a reception impedance transformation Microstrip line; the feeding probe includes a horizontal microstrip and a vertical metal probe, one end of the vertical metal probe is connected to the center of the horizontal microstrip, and the other end of the vertical metal probe is connected to the power The assigned microstrip line is connected. The present invention designs a microstrip circularly polarized duplex antenna with a duplex function. The electromagnetic wave polarization mode used for transmitting and receiving of the antenna is the same, and both are left-handed circularly polarized electromagnetic waves; The blocking filter realizes high isolation between transmit and receive ports.
Description
技术领域technical field
本发明涉及无线通信技术领域，特别涉及一种圆极化微带双工天线。The invention relates to the technical field of wireless communication, in particular to a circularly polarized microstrip duplex antenna.
背景技术Background technique
天馈系统是无线通信系统的最前端，是无线通信系统不可缺少的关键部件。天馈系统主要包括天线、滤波器和双工器，传统方法是三者单独设计，然后再进行连接。缺点是三者都需要独自的匹配网络与50欧姆馈线进行匹配，容易带来体积大、总量重的问题，同时，过多的匹配网络带来了损耗大的缺点。The antenna feeder system is the front end of the wireless communication system and an indispensable key component of the wireless communication system. The antenna feed system mainly includes antennas, filters and duplexers. The traditional method is to design the three separately and then connect them. The disadvantage is that all three need a separate matching network to match the 50 ohm feeder, which is likely to cause problems of large size and total weight. At the same time, too many matching networks bring the disadvantage of high loss.
随着无线通信的发展，通信系统越来越趋向于小型化和集成化，因此，一体化的天馈系统具有极大的需求。双工天线将天线、滤波器、双工器等前端器件联合进行设计，能够使得射频前端系统的结构更加紧凑，减少不必要的损耗引入，使得通信系统的小型化和集成化更加容易实现。With the development of wireless communication, the communication system tends to be miniaturized and integrated more and more. Therefore, there is a great demand for an integrated antenna-feeder system. Duplex antennas combine antennas, filters, duplexers and other front-end components to make the structure of the RF front-end system more compact, reduce unnecessary loss, and make the miniaturization and integration of the communication system easier to achieve.
在现有的双工天线中，实现双工天线主要利用多频天线联合双工器的设计方法实现滤波双工天线，或者通过多模天线联合滤波器的设计方法实现滤波双工天线。目前提出的双工天线主要是线极化双工天线，而且天线的发射接收频率间的间隔较大，端口隔离度一般在20-30dB之间，天线的增益在5dBi以下。In existing duplex antennas, the realization of duplex antennas mainly utilizes a multi-frequency antenna combined duplexer design method to realize a filtered duplex antenna, or a multi-mode antenna combined filter design method to realize a filtered duplex antenna. The currently proposed duplex antennas are mainly linearly polarized duplex antennas, and the interval between the transmitting and receiving frequencies of the antenna is relatively large, the port isolation is generally between 20-30dB, and the gain of the antenna is below 5dBi.
圆极化天线相对于线极化天线来说，其能够接收任意方向的电磁波，因此能够有效抵抗无线通信中的多径衰落效应以及克服由线极化天线引起的极化失配问题。因此，圆极化天线在RFID，GPS，北斗卫星系统等无线通信系统得到了广泛的应用。Compared with linearly polarized antennas, circularly polarized antennas can receive electromagnetic waves in any direction, so they can effectively resist the multipath fading effect in wireless communication and overcome the polarization mismatch problem caused by linearly polarized antennas. Therefore, circularly polarized antennas have been widely used in wireless communication systems such as RFID, GPS, and Beidou satellite system.
因此，目前的同极化双工天线总体来说存在端口隔离度不高，天线收发频率间隔较大，天线的增益不高的缺点。而且，目前的同极化双工天线基本上为线极化双工天线，比较少有圆极化双工天线。Therefore, the current co-polarized duplex antennas generally have the disadvantages of low port isolation, a relatively large interval between transmitting and receiving frequencies of the antenna, and low gain of the antenna. Moreover, the current co-polarized duplex antennas are basically linearly polarized duplex antennas, and there are relatively few circularly polarized duplex antennas.
发明内容Contents of the invention
本发明要解决的技术问题在于，提供一种圆极化微带双工天线，与现有的同极化双工天线相比，天线的发射与接收频率间隔较近，天线发射接收的端口隔离度高，并且天线的发射端口发射的电磁波和接收端口接收的电磁波均为圆极化波。The technical problem to be solved by the present invention is to provide a circularly polarized microstrip duplex antenna. Compared with the existing co-polarized duplex antenna, the transmitting and receiving frequency intervals of the antenna are closer, and the transmitting and receiving ports of the antenna are isolated. High degree, and the electromagnetic wave emitted by the transmitting port of the antenna and the electromagnetic wave received by the receiving port are both circularly polarized waves.
为解决上述技术问题，本发明提供如下技术方案：一种圆极化微带双工天线，包括微带贴片天线、两个馈电探针、具备双工功能的双工功率分配网络、发送端口以及接收端口；其中In order to solve the above technical problems, the present invention provides the following technical solutions: a circularly polarized microstrip duplex antenna, including a microstrip patch antenna, two feeding probes, a duplex power distribution network with duplex function, a transmission port and receiving port; where
两个所述馈电探针均与所述双工功率分配网络连接；both of said feed probes are connected to said duplex power distribution network;
所述双工功率分配网络包括功率分配微带线、发送微带带阻滤波器、发送阻抗变换微带线、接收微带带阻滤波器和接收阻抗变换微带线；所述发送微带带阻滤波器一端与所述发送端口相连、另一端通过所述发送阻抗变换微带线与所述功率分配微带线相连；所述接收微带带阻滤波器一端与接收端口相连、另一端通过所述接收阻抗变换微带线与所述功率分配微带线相连；The duplex power distribution network includes a power distribution microstrip line, a transmission microstrip band rejection filter, a transmission impedance conversion microstrip line, a reception microstrip band rejection filter and a reception impedance conversion microstrip line; One end of the rejection filter is connected to the transmission port, and the other end is connected to the power distribution microstrip line through the transmission impedance transformation microstrip line; one end of the reception microstrip band rejection filter is connected to the reception port, and the other end is through the The receiving impedance transformation microstrip line is connected to the power distribution microstrip line;
所述馈电探针包括水平微带和垂直金属探针，所述垂直金属探针的一端连接所述水平微带的中心，所述垂直金属探针的另一端与所述功率分配微带线相连。The feeding probe includes a horizontal microstrip and a vertical metal probe, one end of the vertical metal probe is connected to the center of the horizontal microstrip, and the other end of the vertical metal probe is connected to the power distribution microstrip line connected.
进一步地，所述馈电探针为T型馈电探针，即所述水平微带和垂直金属探针相互垂直连接。Further, the feeding probe is a T-shaped feeding probe, that is, the horizontal microstrip and the vertical metal probe are vertically connected to each other.
进一步地，所述发送微带带阻滤波器通过所述发送阻抗变换微带线与所述功率分配微带线相连；其中，发送阻抗变换微带线与功率分配微带线的连接位置处把功率分配微带线分成两段线，此两段线之间的长度之差为λg发/4；所述接收微带带阻滤波器通过所述接收阻抗变换微带线与所述功率分配微带线相连；其中，接收阻抗变换微带线与功率分配微带线的连接位置处同样把功率分配线分成两段线，此两段线的之间长度之差为λg收/4；其中，λg发为发送信号在所述功率分配微带线上的波长，λg收为接收信号在所述功率分配微带线上的波长。Further, the transmitting microstrip bandstop filter is connected to the power distribution microstrip line through the transmission impedance transformation microstrip line; wherein, the connection position between the transmission impedance transformation microstrip line and the power distribution microstrip line is The power distribution microstrip line is divided into two sections, and the difference in length between the two sections is λg /4; The microstrip line is connected; wherein, the power distribution line is also divided into two sections at the connection position between the receiving impedance transformation microstrip line and the power distribution microstrip line, and the difference in length between the two sections of lines is λ g /4; Wherein, λg is the wavelength of the transmitted signal on the power distribution microstrip line, and λg is the wavelength of the received signal on the power distribution microstrip line.
进一步地，所述发送微带带阻滤波器包括两段第一末端开路微带线和一段第一连接微带线，所述连接微带线的两端分别接两段所述第一末端开路微带线，所述第一末端开路微带线的长度和宽度使得频率为f发的发送信号能够通过、而频率为f收的接收信号不能通过，所述第一连接微带线的长度和宽度使得频率为f发的发送信号能够通过、而频率为f收的接收信号不能通过。Further, the transmitting microstrip bandstop filter includes two sections of first-end open-circuit microstrip lines and a section of first connecting microstrip line, and the two ends of the connecting microstrip line are respectively connected to two sections of the first-end open-circuit Microstrip line, the length and width of the first open-circuited microstrip line enable the transmission signal with frequency f to pass through, while the reception signal at frequency f cannot pass through, the length and width of the first connecting microstrip line The width is such that the transmitted signal at frequency f can pass, but the received signal at frequency f cannot pass through.
进一步地，所述接收微带带阻滤波器由两段第二末端开路微带线和一段第二连接微带线组成，所述第二连接微带线的两端分别接两段所述第二末端开路微带线，所述第二末端开路微带线的长度和宽度使得频率为f收的接收信号能够通过、而频率为f发的发送信号不能通过，所述第二连接微带线的长度和宽度使得频率为f收的接收信号能够通过、而频率为f发的发送信号不能通过。Further, the receiving microstrip bandstop filter is composed of two sections of second-end open-circuit microstrip lines and a section of second connection microstrip line, and the two ends of the second connection microstrip line are respectively connected to two sections of the first The two-end open-circuit microstrip line, the length and width of the second-end open-circuit microstrip line are such that the received signal with frequency f can pass through, and the transmitted signal with frequency f cannot pass through, and the second connected microstrip line The length and width of the channel allow the received signal with frequency f to pass through, but the transmitted signal with frequency f cannot pass through.
进一步地，所述发送微带带阻滤波器和所述接收微带带阻滤波器的工作通带相反，且所述发送微带带阻滤波器和所述接收微带带阻滤波器的阻带频率相反。Further, the working passbands of the sending microstrip band-stop filter and the receiving microstrip band-stop filter are opposite, and the stop bands of the sending microstrip band-stop filter and the receiving microstrip band-stop filter The frequency is reversed.
进一步地，所述发送阻抗变换微带线的长度和宽度满足以下要求：满足在频率为f收的接收信号条件下，在发送端口接匹配负载时，发送阻抗变换微带线与功率分配微带线的连接端的阻抗接近开路。Further, the length and width of the transmission impedance transformation microstrip line meet the following requirements: under the condition of receiving a signal at a frequency of f, when the transmission port is connected to a matching load, the transmission impedance transformation microstrip line and the power distribution microstrip The impedance of the connected end of the line is close to an open circuit.
进一步地，所述接收阻抗变换微带线的长度和宽度满足以下要求：满足在频率为f发的发送信号条件下，在接收端口接匹配负载时，接收阻抗变换微带线与功率分配微带线的连接端的阻抗接近开路。Further, the length and width of the receiving impedance transformed microstrip line meet the following requirements: under the condition of transmitting signals with a frequency of f, when the receiving port is connected to a matching load, the receiving impedance transformed microstrip line and the power distribution microstrip The impedance of the connected end of the line is close to an open circuit.
进一步地，所述发送阻抗变换微带线和接收阻抗变换微带线工作于不同频率；所述发送阻抗变换微带线为35.4Ω阻抗变换线，其长度为λg收/4；所述接收阻抗变换微带线也为35.4Ω阻抗变换线，其长度为λg发/4；其中，λg发为发送信号在所述功率分配微带线上的波长，λg收为接收信号在所述功率分配微带线上的波长。Further, the transmission impedance transformation microstrip line and the reception impedance transformation microstrip line work at different frequencies; the transmission impedance transformation microstrip line is a 35.4Ω impedance transformation line, and its length is λg/4; the reception The impedance transformation microstrip line is also a 35.4Ω impedance transformation line, and its length is λgfa /4; wherein, λgfa is the wavelength of the transmitted signal on the power distribution microstrip line, and λg is received as the wavelength of the received signal in the power distribution microstrip line. The power is distributed over the wavelengths on the microstrip line.
进一步地，所述的圆极化微带双工天线还包括两个平行放置的上层介质基板和下层介质基板，所述下层介质基板的上表面覆盖有金属的反射地板，底面设置双工功率分配网络；所述微带贴片天线印刷在所述上层介质基板上表面；所述探针的水平微带印刷在所述上层介质基板的下表面。Further, the circularly polarized microstrip duplex antenna also includes two parallel upper dielectric substrates and lower dielectric substrates, the upper surface of the lower dielectric substrate is covered with a metal reflective floor, and the bottom surface is provided with duplex power distribution network; the microstrip patch antenna is printed on the upper surface of the upper dielectric substrate; the horizontal microstrip of the probe is printed on the lower surface of the upper dielectric substrate.
采用上述技术方案后，本发明至少具有如下有益效果：After adopting the above technical solution, the present invention has at least the following beneficial effects:
1、本发明将圆极化天线的功率分配网络与双工网络设计结合在一起，设计了一个既具有双工功能、又具有功率分配功能的双工功率分配网络；天线的发射端口以及接收端口的功率分配以及信号的移相均通过一段共同的接近低频工作频带四分之一波长的功率分配微带线来实现，因此天线的结构比较紧凑；同时通过在发送端口设置发送微带带阻滤波器，在接收端口设置接收微带带阻滤波器，实现了发送与接收端口间的高隔离度；1. The present invention combines the power distribution network and duplex network design of circularly polarized antennas, and designs a duplex power distribution network with both duplex function and power distribution function; the transmitting port and receiving port of the antenna The power distribution and phase shift of the signal are realized through a common power distribution microstrip line close to the quarter wavelength of the low-frequency working frequency band, so the structure of the antenna is relatively compact; at the same time, by setting the transmission port at the transmission port device, and a receiving microstrip band-stop filter is set at the receiving port to achieve high isolation between the sending and receiving ports;
2、本发明发射与接收的信号均通过T型探针上的微带与贴片天线进行耦合，由于经过功率分分配微带线移相后，两个端口的信号在两个T型探针的水平微带上的相位均是微带为x方向的探针相位超前于微带为y方向上的探针，因此实现了发射接收同极化，且均为圆极化；2. The signals transmitted and received by the present invention are coupled through the microstrip on the T-type probe and the patch antenna. After the phase shift of the microstrip line through the power distribution distribution, the signals of the two ports are transmitted between the two T-type probes. The phase on the horizontal microstrip is that the phase of the probe in the x direction of the microstrip is ahead of the probe in the y direction of the microstrip, so the co-polarization of the transmission and reception is realized, and they are all circular polarization;
3、本发明发送接收互扰小，通过在发送微带带阻滤波器与功率分配微带线间插入发送阻抗变换微带线，发射支路不会对功率分配微带线上的接收信号产生影响；通过在接收微带带阻滤波器与功率分配微带线间插入接收阻抗变换微带线，能够使得在发送端口工作时，接收支路不会对功率分配微带线上的发送信号产生影响。因此，发送接收之间的互扰较小；3. The present invention transmits and receives little mutual interference. By inserting a transmission impedance conversion microstrip line between the transmission microstrip band-rejection filter and the power distribution microstrip line, the transmission branch will not generate a signal on the received signal on the power distribution microstrip line. Influence; by inserting the receiving impedance transformation microstrip line between the receiving microstrip band-stop filter and the power distribution microstrip line, it can make the receiving branch not produce the transmission signal on the power distribution microstrip line when the transmitting port is working. influences. Therefore, the mutual interference between sending and receiving is small;
4、现有的同极化双工天线，通常是基于带通滤波器的设计方法进行设计，而带通滤波器通带较关注于通带内的设计，在距离通带比较近的带外，抑制信号通过的效果一般不是很好，而想要提高带通滤波器的带外抑制通常需要增加带通滤波器的阶数，使得滤波器的设计更加复杂，尺寸增加；而本发明采用带阻滤波器的方法设计同极化的圆极化双工天线，其在距离通带较近的一侧的频带能够产生传输零点，抑制信号通过的效果较好，因此能实现比较小的发送接收频率间隔，并保持较好的发射接收隔离特性。4. Existing co-polarized duplex antennas are usually designed based on the design method of band-pass filters, while the pass-band of band-pass filters is more concerned with the design within the pass-band, and outside the band that is relatively close to the pass-band , the effect of suppressing the passage of the signal is generally not very good, and it is usually necessary to increase the order of the band-pass filter to improve the out-of-band suppression of the band-pass filter, which makes the design of the filter more complicated and increases in size; and the present invention uses a band-pass filter The circularly polarized duplex antenna with the same polarization is designed by the method of the rejection filter, which can generate a transmission zero point in the frequency band on the side closer to the passband, and the effect of suppressing the passage of the signal is better, so it can achieve a relatively small transmission and reception Frequency interval, and maintain good transmission and reception isolation characteristics.
附图说明Description of drawings
图1为本发明圆极化微带双工天线的总结构示意图以及主要组成部分的编号标注；Fig. 1 is the general structure schematic diagram of the circularly polarized microstrip duplex antenna of the present invention and the numbering label of main components;
图2为本发明圆极化微带双工天线的总结构示意图以及细化的编号标注；Fig. 2 is the general structural schematic diagram and the subdivided number label of the circularly polarized microstrip duplex antenna of the present invention;
图3为本发明圆极化微带双工天线的的正面剖视图；Fig. 3 is the front sectional view of the circularly polarized microstrip duplex antenna of the present invention;
图4为本发明圆极化微带双工天线的上层介质基板的俯视图；Fig. 4 is the plan view of the upper dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图5为本发明圆极化微带双工天线的上层介质基板的仰视图；Fig. 5 is the bottom view of the upper dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图6为本发明圆极化微带双工天线的下层介质基板的俯视图；6 is a top view of the lower dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图7为本发明圆极化微带双工天线的下层介质基板的仰视图；7 is a bottom view of the lower dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图8为本发明圆极化微带双工天线的上层介质基板上表面结构的尺寸标注图；Fig. 8 is a dimensional drawing of the upper surface structure of the upper dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图9为本发明圆极化微带双工天线的上层介质基板下表面结构的尺寸标注图；Fig. 9 is a dimensional drawing of the lower surface structure of the upper dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图10为本发明圆极化微带双工天线的下层介质基板上表面结构的尺寸标注图；Fig. 10 is a dimensional drawing of the upper surface structure of the lower dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图11为本发明圆极化微带双工天线的下层介质基板上功率分配线的尺寸标注图；Fig. 11 is a dimensional drawing of the power distribution line on the lower dielectric substrate of the circularly polarized microstrip duplex antenna of the present invention;
图12为本实施例发送带阻滤波器实例的仿真S参数曲线图；Fig. 12 is the simulation S-parameter curve diagram of the example of sending the band-stop filter of the present embodiment;
图13为本实施例接收带阻滤波器实例的仿真S参数曲线图；Fig. 13 is the simulation S-parameter curve diagram of the receiving band-stop filter example of the present embodiment;
图14为本实施例发送变换微带线连接发送微带带阻滤波器的仿真S参数、以及发送端口接匹配负载后的阻抗图；Fig. 14 is the simulated S parameter of the transmission transformation microstrip line connected to the transmission microstrip band-stop filter of the present embodiment, and the impedance diagram after the transmission port is connected to the matching load;
图15为本实施例接收变换微带线连接接收微带带阻滤波器的仿真S参数、以及接收端口接匹配负载后的阻抗图；Fig. 15 is the simulated S parameter of receiving transformed microstrip line connected to receiving microstrip bandstop filter and the impedance diagram after the receiving port is connected with matching load in this embodiment;
图16为本实施例圆极化微带双工天线的测试S参数曲线图；Fig. 16 is the test S parameter curve diagram of the circularly polarized microstrip duplex antenna of the present embodiment;
图17(a)为本实施例接收端口(2.2GHz)激励的xoz面仿真方向图；Fig. 17 (a) is the simulation direction diagram of the xoz plane excited by the receiving port (2.2GHz) of the present embodiment;
图17(b)为本实施例接收端口(2.2GHz)激励的yoz面仿真方向图；Fig. 17 (b) is the simulation direction diagram of the yoz plane excited by the receiving port (2.2GHz) of the present embodiment;
图18(a)为本实施例发送端口(2.4GHz)激励的xoz面仿真方向图；Fig. 18 (a) is the simulation direction diagram of the xoz plane excited by the sending port (2.4GHz) of this embodiment;
图18(b)为本实施例发送端口(2.4GHz)激励的yoz面仿真方向图；Fig. 18 (b) is the simulation direction diagram of the yoz plane excited by the sending port (2.4GHz) of the present embodiment;
图19为本实施例天线的仿真增益随频率变化曲线；FIG. 19 is a simulation gain curve of the antenna of this embodiment as a function of frequency;
图20为本实施例天线的仿真轴比随频率变化曲线图。FIG. 20 is a graph showing the variation of the simulated axial ratio with frequency of the antenna of this embodiment.
具体实施方式detailed description
需要说明的是，在不冲突的情况下，本申请中的实施例及实施例中的特征可以相互结合，下面结合附图和具体实施例对本申请作进一步详细说明。It should be noted that, in the case of no conflict, the embodiments in the present application and the features in the embodiments can be combined with each other. The present application will be further described in detail below in conjunction with the drawings and specific embodiments.
参照图1、图2及图3，本发明提供一种同极化的圆极化微带双工天线，包括一个正方形的微带贴片天线1、两个用于馈电的T型探针2、一个带有双工功能的功率分配网络3、发送端口31以及接收端口32，所述双工功率分配网络3包括功率分配微带线4、发送微带带阻滤波器7、发送阻抗变换微带线5、With reference to Fig. 1, Fig. 2 and Fig. 3, the present invention provides a kind of circularly polarized microstrip duplex antenna of copolarization, comprises a square microstrip patch antenna 1, two T-shaped probes for feeding 2, a power distribution network 3 with duplex function, sending port 31 and receiving port 32, described duplex power distribution network 3 includes power distribution microstrip line 4, sending microstrip band-stop filter 7, sending impedance transformation Microstrip line 5,
接收微带带阻滤波器8和接收阻抗变换微带线6。Receiving microstrip band-stop filter 8 and receiving impedance transformation microstrip line 6 .
发送微带带阻滤波器7的一端与发送端口31相连，另一端通过发送阻抗变换微带线5与功率分配微带线4在距离功率分配微带线两端的长度之差为λg发/4的位置处相连，λg发为发送信号在功率分配微带线4上的波长。One end of the sending microstrip bandstop filter 7 is connected to the sending port 31, and the other end is transformed by sending impedance between the microstrip line 5 and the power distribution microstrip line 4 at a distance between the two ends of the power distribution microstrip line. 4, and λg is the wavelength of the transmitted signal on the power distribution microstrip line 4.
接收微带带阻滤波器8的一端与接收端口32相连，另一端通过接收阻抗变换微带线6与功率分配微带线4在距离功率分配微带线两端的长度之差为λg收/4的位置处相连，λg收为接收信号在功率分配微带线4上的波长。One end of the receiving microstrip bandstop filter 8 is connected to the receiving port 32, and the other end transforms the microstrip line 6 and the power distribution microstrip line 4 at the distance between the two ends of the power distribution microstrip line. 4, and λ g is the wavelength of the received signal on the power distribution microstrip line 4.
发送阻抗变换微带线5和接收阻抗变换微带线6是左右两段工作在不同频率下的长度为λg收/4及λg发/4的35.4Ω阻抗变换线。微带阻抗变换线5、6之后分别是两段低阻抗传输线20、23，随后通过两段50Ω的传输线24、25连接到射频系统的两个端口。四段加载的L型终端开路枝节线18、19、21、22分别加载在两段低阻抗线20、23的两端，与两段低阻抗线组成了发送接收端口的两个带阻滤波器。两个带阻滤波器的工作通带与阻带频率正好相反。The transmitting impedance transforming microstrip line 5 and the receiving impedance transforming microstrip line 6 are 35.4Ω impedance transforming lines with the lengths of λ g receiving /4 and λ g sending /4 and working at different frequencies. The microstrip impedance transformation lines 5 and 6 are respectively followed by two sections of low-impedance transmission lines 20 and 23 , which are then connected to two ports of the radio frequency system through two sections of 50Ω transmission lines 24 and 25 . Four sections of loaded L-shaped terminal open stub lines 18, 19, 21, 22 are respectively loaded on the two ends of two sections of low-impedance lines 20, 23, and two sections of low-impedance lines form two band-stop filters of the transmitting and receiving ports . The working passband and stopband frequencies of the two bandstop filters are just opposite.
发送微带带阻滤波器7由两段末端开路的微带线18、19和一段连接微带线20组成，连接微带线20两端分别接两个开路微带线18、19。末端开路微带线18、19和连接微带线20的长度和宽度通过合理选择使得在频率为f发的发送信号能够通过、而频率为f收的接收信号不能通过。作为一个实例，当要求f发＝2.4GHz，f收＝2.2GHz时，可以采用相对介电常数为2.55、厚度为h＝0.8mm的介质板做基板，开路微带线18的长度取26.5mm、宽度取0.5mm，开路微带线19的长度取26.04mm、宽度取0.5mm，连接微带线20的长度取25.7mm、宽度取9mm，图12是这个时候的发送微带带阻滤波器的S参数，可以看到在频率为2.4GHz时其S12为-1.95dB、在频率为2.2GHz时其S12为-40.8dB，实现了通过发送信号而阻隔接收信号的功能。The transmitting microstrip bandstop filter 7 is composed of two sections of open-ended microstrip lines 18 and 19 and a section of connecting microstrip line 20 , and two open-circuit microstrip lines 18 and 19 are respectively connected to the two ends of the connecting microstrip line 20 . The length and width of the open-ended microstrip lines 18, 19 and the connecting microstrip line 20 are properly selected so that the transmitted signal at frequency f can pass through, while the received signal at frequency f cannot pass through. As an example, when requiring f to send out=2.4GHz, f receives =2.2GHz, can adopt relative permittivity to be 2.55, the dielectric plate that thickness is h=0.8mm is made substrate, the length of open-circuit microstrip line 18 gets 26.5mm , the width is 0.5mm, the length of the open microstrip line 19 is 26.04mm, the width is 0.5mm, the length of the connecting microstrip line 20 is 25.7mm, and the width is 9mm. Figure 12 is the sending microstrip bandstop filter at this time It can be seen that its S12 is -1.95dB when the frequency is 2.4GHz, and its S12 is -40.8dB when the frequency is 2.2GHz, which realizes the function of blocking the receiving signal by sending the signal.
接收微带带阻滤波器8由两段末端开路的微带线21、22和一段连接微带线23组成，连接微带线23两端分别接两个开路微带线21、22。末端开路微带线21、22和连接微带线23的长度和宽度通过合理选择使得在频率为f收的接收信号能够通过、而频率为f发的发送信号不能通过。作为一个实例，当要求f发＝2.4GHz，f收＝2.2GHz时，可以采用相对介电常数为2.55、厚度为h＝0.8mm的介质板做基板，开路微带线21的长度取26.8mm、宽度取0.5mm，开路微带线22的长度取26.19mm、宽度取0.5mm，连接微带线23的长度取25.5mm、宽度取14mm，图13是这个时候的接收微带带阻滤波器的S参数，可以看到在频率为2.2GHz时其S12为-1.65dB、在频率为2.4GHz时其S12为-41.5dB，实现了通过接收信号而阻隔发送信号的功能。The receiving microstrip bandstop filter 8 is composed of two sections of open-ended microstrip lines 21 and 22 and a section of connecting microstrip line 23, and two open-circuit microstrip lines 21 and 22 are respectively connected to the two ends of the connecting microstrip line 23. The length and width of the open-ended microstrip lines 21, 22 and the connecting microstrip line 23 are properly selected so that the received signal at frequency f can pass through, while the transmitted signal at frequency f cannot pass through. As an example, when requiring f to send out=2.4GHz, f to receive =2.2GHz, can adopt relative permittivity to be 2.55, the dielectric board that thickness is h=0.8mm makes substrate, the length of open-circuit microstrip line 21 gets 26.8mm , the width is 0.5mm, the length of the open circuit microstrip line 22 is 26.19mm, the width is 0.5mm, the length of the connecting microstrip line 23 is 25.5mm, and the width is 14mm. Figure 13 is the receiving microstrip bandstop filter at this time It can be seen that its S12 is -1.65dB when the frequency is 2.2GHz, and its S12 is -41.5dB when the frequency is 2.4GHz, which realizes the function of blocking the sending signal by receiving the signal.
发送阻抗变换微带线5通过适当选取其长度和宽度，保证对于频率为f收的接收信号而言，其在与功率分配微带线4的连接端的阻抗(发送端口31接匹配负载时)为很大(接近开路)，从而不影响频率为f收接收信号在功率分配微带线4上的传输。作为一个实例，当要求f发＝2.4GHz，f收＝2.2GHz时，可以采用相对介电常数为2.55、厚度为h＝0.8mm的介质板做基板，发送阻抗变换微带线5的长度取23.5mm、宽度取3.67mm，连接上述的发送微带带阻滤波器的实例，其S参数、以及发送端口31接匹配负载后的阻抗如图14所示。可以看到，在f收＝2.2GHz时，阻抗大于1000欧姆，而对于频率为f发＝2.4GHz的发送信号则衰减很少。Transmitting impedance transformation microstrip line 5 is by suitably selecting its length and width, guarantees that for the receiving signal that frequency is received , its impedance (when transmitting port 31 is connected to matching load) with the connection end of power distribution microstrip line 4 is It is very large (close to an open circuit), so as not to affect the transmission of the received signal at the frequency f on the power distribution microstrip line 4 . As an example, when f is required to send =2.4GHz, and f is received when=2.2GHz, can adopt relative permittivity to be 2.55, the dielectric plate that thickness is h=0.8mm is made substrate, and the length of transmitting impedance transformation microstrip line 5 is taken as 23.5mm, the width is 3.67mm, and the example of connecting the above-mentioned transmitting microstrip bandstop filter, its S parameters and the impedance after the transmitting port 31 is connected to the matched load are shown in FIG. 14 . It can be seen that the impedance is greater than 1000 ohms when f receive = 2.2 GHz, and the attenuation is very little for the transmit signal with frequency f transmit = 2.4 GHz.
接收阻抗变换微带线6通过适当选取其长度和宽度，保证对于频率为f发的发送信号而言，其在与功率分配微带线4的连接端的阻抗(接收端口32接匹配负载时)为很大(接近开路)，从而不影响频率为f发发送信号在功率分配微带线4上的传输。作为一个实例，f发＝2.4GHz，f收＝2.2GHz时，可以采用相对介电常数为2.55、厚度为h＝0.8mm的介质板做基板，接收阻抗变换微带线6的长度取19.5mm、宽度取3.67mm，连接上上述的接收微带带阻滤波器的实例，其S参数、以及接收端口32接匹配负载后的阻抗如图15所示。可以看到，在f收＝2.4GHz时，阻抗大于1000欧姆，而对于频率为f发＝2.2GHz的接收信号则衰减很少。The receiving impedance transformation microstrip line 6 ensures that for the transmission signal with frequency f, its impedance at the connection end with the power distribution microstrip line 4 (when the receiving port 32 is connected to a matching load) is by selecting its length and width appropriately. is very large (close to an open circuit), so that it does not affect the transmission of the transmitted signal at the frequency f on the power distribution microstrip line 4 . As an example, when f is sent out at 2.4GHz and f is received at 2.2GHz, a dielectric plate with a relative permittivity of 2.55 and a thickness of h=0.8mm can be used as the substrate, and the length of the receiving impedance transformation microstrip line 6 is 19.5mm , the width is 3.67 mm, and the above example of receiving microstrip band-stop filter is connected, its S parameters and the impedance after the receiving port 32 is connected to the matching load are shown in FIG. 15 . It can be seen that when f = 2.4GHz, the impedance is greater than 1000 ohms, and the attenuation is very little for the received signal with frequency f = 2.2GHz.
所述圆极化微带双工天线，还包括两个平行放置的上层介质基板9和下层介质基板11，下层介质基板11的上表面覆盖有金属的反射地板10，底面设置本天线的反相功率分配网络3。The circularly polarized microstrip duplex antenna also includes two upper dielectric substrates 9 and lower dielectric substrates 11 placed in parallel, the upper surface of the lower dielectric substrate 11 is covered with a metal reflective floor 10, and the bottom surface is provided with the anti-phase of the antenna. Power Distribution Network 3.
所述微带贴片天线1包括印刷在上层介质基板9上表面的正方形金属贴片1。The microstrip patch antenna 1 includes a square metal patch 1 printed on the upper surface of the upper dielectric substrate 9 .
所述的T型探针由印刷在上层介质基板9下表面的金属微带12、13和接在金属微带12、13中心的金属探针14、15组成，金属探针14、15的另一端分别穿过反射地板10和下层介质基板11上的通孔16、17与功率分配微带线4的两端相连。Described T-shaped probe is made up of the metal microstrip 12,13 that is printed on the lower surface of upper dielectric substrate 9 and the metal probe 14,15 that is connected at the center of metal microstrip 12,13, and the other of metal probe 14,15 One end is respectively connected to both ends of the power distribution microstrip line 4 through the through holes 16 and 17 on the reflective floor 10 and the lower dielectric substrate 11 .
当发送时，发送信号从发送端口31送入，经过发送微带带阻滤波器7和发送阻抗变换微带线5送入功率分配微带线。经过功率分配微带线的信号被以相同的幅度、相差90度的相位分配到两个T型的探针12、13、14、15处，并通过T型探针上的微带12、13耦合给辐射贴片1。由于两个微带12、13垂直放置，能够在辐射贴片上激励起两个空间相互正交的电磁波。又由于经过馈电网络到达两个微带12、13处的信号幅度相等，相位相差90度，因此能够在辐射贴片上激励起一个圆极化的电磁波。When sending, the sending signal is sent from the sending port 31, and sent to the power distribution microstrip line through the sending microstrip band-stop filter 7 and the sending impedance transformation microstrip line 5. The signal passing through the power distribution microstrip line is distributed to two T-shaped probes 12, 13, 14, and 15 with the same amplitude and 90-degree phase difference, and passes through the microstrips 12, 13 on the T-shaped probe. Coupled to radiating patch 1. Since the two microstrips 12 and 13 are placed vertically, two mutually orthogonal electromagnetic waves can be excited on the radiation patch. And because the amplitudes of the signals arriving at the two microstrips 12 and 13 through the feeding network are equal and the phases differ by 90 degrees, a circularly polarized electromagnetic wave can be excited on the radiation patch.
当接收时，接收信号从辐射贴片天线1处接收，并耦合给T型探针12、13、14、15。接收信号经过T型探针12、13、14、15后被送入到功率分配微带线4的两端。此时，功率分配微带线4两端的信号也是幅度相等，相位相差90度。功率分配微带线4两端的信号分别经过相位相差90度的功率分配微带线到达接收阻抗变换微带线6时刚好以相同的相位叠加，随后经过接收阻抗变换微带线6和接收微带带阻滤波器8，从接收端口32输出。When receiving, received signals are received from the radiating patch antenna 1 and coupled to T-probes 12 , 13 , 14 , 15 . The received signal is sent to both ends of the power distribution microstrip line 4 after passing through the T-shaped probes 12 , 13 , 14 , and 15 . At this time, the signals at both ends of the power distribution microstrip line 4 are also equal in amplitude and 90 degrees out of phase. The signals at both ends of the power distribution microstrip line 4 respectively pass through the power distribution microstrip line with a phase difference of 90 degrees and arrive at the receiving impedance transformation microstrip line 6. The band rejection filter 8 is output from the receiving port 32 .
图4、图5、图6、图7分别为两个介质基板上下表面的电气结构图，条纹填充部分为导体铜覆盖的结构，其余部分为介质基板。Figure 4, Figure 5, Figure 6, and Figure 7 are the electrical structure diagrams of the upper and lower surfaces of the two dielectric substrates, respectively. The stripe filling part is the structure covered by conductor copper, and the rest is the dielectric substrate.
图8、图9、图10、图11为各部分电气结构的尺寸标注图。Figure 8, Figure 9, Figure 10, and Figure 11 are dimensioned drawings of the electrical structure of each part.
结合图2、图8、图9、图10、图11的尺寸标注，本实施例中天线的具体参数如下：两个介质板的材料和尺寸相同，厚度c为0.8mm，宽度b为120mm，长度a为120mm。两个介质板之间的高度h为8mm。正方形贴片的边长1a及距离介质板边缘的间距分别为47.5mm、36.25mm。两个用于耦合的细长微带长2a、宽2b，距离介质板边缘的距离2c分别为2mm、6.5mm、49mm。功率分配网络的主要尺寸4a、4b、4c、4d分别为27.85mm、2.3mm、4.75mm、2.18mm。两段35.4Ω的阻抗变换线的长度5a和6a分别为23.5mm及19.5mm，宽度5b、6b均为3.67mm。四段末端开路的L型枝节线的宽度18b均为0.5mm，长度18a、19a、21a、22a分别为26.5mm、26.04mm、26.8mm、26.19mm。两段低阻抗传输的长度20a、23a和宽度20b、23b分别为25.7mm、25.5mm、9mm、14mm。连接到端口的两段传输线的长度24a、25a分别为9.65mm、13.85mm，宽度分别为2.25mm。该天线的发送端口31工作在2.4GHz的频带。接收端口32工作在2.2GHz的频带。在两个频带内，两个端口的隔离度均大于43dB，如图16所示。两个工作频带范围内，天线的增益基本上都大于6dBi，交叉极化大于15dB，如天线的仿真测试方向图17、图18所示。在天线的接收端口32工作时，天线在发送端口31工作频率2.2GHz处的增益为6.1dBi，而在发送端口31工作频率2.4GHz处的增益则迅速下降到了-30dBi以下，增益差达到了35dB以上，如图19。同理，在天线的发送端口31工作时，天线在发送端口31工作频率2.4GHz处的增益为6.9dBi，而在接收端口32工作频率2.2GHz处的增益也迅速下降到了-30dBi以下，增益差同样达到了35dB以上，如图19所示，图中所示的端口1代表发送端口31、端口2代表接收端口32。在天线的发送端口31工作时，天线在发送端口31工作频率范围内，轴比小于1.8dB；在天线的发送端口31工作时，天线在发送端口31工作频率范围内，轴比小于2.2dB，如图20所示，图中所示的端口1代表发送端口31、端口2代表接收端口32，天线的两个端口均显示了良好的圆极化特性。Combined with the dimensions in Figure 2, Figure 8, Figure 9, Figure 10, and Figure 11, the specific parameters of the antenna in this embodiment are as follows: the materials and dimensions of the two dielectric plates are the same, the thickness c is 0.8 mm, and the width b is 120 mm. The length a is 120mm. The height h between the two dielectric plates is 8mm. The side length 1a of the square patch and the distance from the edge of the dielectric board are 47.5 mm and 36.25 mm, respectively. The two elongated microstrips used for coupling are 2a long and 2b wide, and the distance 2c from the edge of the dielectric plate is 2mm, 6.5mm, and 49mm, respectively. The main dimensions 4a, 4b, 4c, 4d of the power distribution network are 27.85mm, 2.3mm, 4.75mm, 2.18mm respectively. The lengths 5a and 6a of the two 35.4Ω impedance transformation lines are 23.5mm and 19.5mm respectively, and the widths 5b and 6b are both 3.67mm. The width 18b of the four open-ended L-shaped stub lines is 0.5mm, and the lengths 18a, 19a, 21a, and 22a are 26.5mm, 26.04mm, 26.8mm, and 26.19mm, respectively. The lengths 20a, 23a and widths 20b, 23b of the two sections of low-impedance transmission are 25.7mm, 25.5mm, 9mm, and 14mm, respectively. The lengths 24a, 25a of the two transmission lines connected to the ports are 9.65mm, 13.85mm respectively, and the widths are 2.25mm respectively. The transmitting port 31 of the antenna works in the frequency band of 2.4GHz. The receiving port 32 works in the frequency band of 2.2GHz. In both frequency bands, the isolation of the two ports is greater than 43dB, as shown in Figure 16. In the two operating frequency bands, the gain of the antenna is basically greater than 6dBi, and the cross-polarization is greater than 15dB, as shown in the simulation test pattern diagrams 17 and 18 of the antenna. When the receiving port 32 of the antenna is working, the gain of the antenna at the working frequency of the sending port 31 at 2.2GHz is 6.1dBi, while the gain at the working frequency of the sending port 31 at 2.4GHz drops rapidly to below -30dBi, and the gain difference reaches 35dB Above, as shown in Figure 19. Similarly, when the transmitting port 31 of the antenna is working, the gain of the antenna at the operating frequency of 2.4GHz at the transmitting port 31 is 6.9dBi, and the gain at the operating frequency of 2.2GHz at the receiving port 32 also drops rapidly to below -30dBi, the gain difference Also reached more than 35dB, as shown in FIG. 19 , the port 1 shown in the figure represents the sending port 31 , and the port 2 represents the receiving port 32 . When the transmitting port 31 of the antenna is working, the antenna is within the operating frequency range of the transmitting port 31, and the axial ratio is less than 1.8dB; when the transmitting port 31 of the antenna is working, the antenna is within the operating frequency range of the transmitting port 31, and the axial ratio is less than 2.2dB. As shown in FIG. 20 , port 1 shown in the figure represents the transmitting port 31 , and port 2 represents the receiving port 32 , and both ports of the antenna show good circular polarization characteristics.
尽管已经示出和描述了本发明的实施例，对于本领域的普通技术人员而言，可以理解的是，在不脱离本发明的原理和精神的情况下可以对这些实施例进行多种等效的变化、修改、替换和变型，本发明的范围由所附权利要求及其等同范围限定。While embodiments of the present invention have been shown and described, it will be understood by those skilled in the art that various equivalents can be made to these embodiments without departing from the principles and spirit of the invention. Changes, modifications, substitutions and variations, the scope of the present invention is defined by the appended claims and their equivalents.
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