CN106252872B - Co-polarized microstrip duplex antenna array - Google Patents
Co-polarized microstrip duplex antenna array Download PDFInfo
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- CN106252872B CN106252872B CN201610861115.9A CN201610861115A CN106252872B CN 106252872 B CN106252872 B CN 106252872B CN 201610861115 A CN201610861115 A CN 201610861115A CN 106252872 B CN106252872 B CN 106252872B
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/24—Combinations of antenna units polarised in different directions for transmitting or receiving circularly and elliptically polarised waves or waves linearly polarised in any direction
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
- H01Q13/08—Radiating ends of two-conductor microwave transmission lines, e.g. of coaxial lines, of microstrip lines
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
- H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
- H01Q21/061—Two dimensional planar arrays
- H01Q21/065—Patch antenna array
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Abstract
The invention discloses a co-polarized microstrip duplex antenna array, which comprises two identical microstrip patch antennas which are symmetrically arranged and an inverse power distribution network with a duplex function, wherein the inverse power distribution network comprises a power distribution microstrip line, a sending microstrip band elimination filter, a sending impedance conversion microstrip line, a receiving microstrip band elimination filter and a receiving impedance conversion microstrip line; one end of the sending microstrip band elimination filter is connected with the sending port, and the other end of the sending microstrip band elimination filter is connected with the power distribution microstrip line through the sending impedance transformation microstrip line; one end of the receiving microstrip band elimination filter is connected with the receiving port, and the other end of the receiving microstrip band elimination filter is connected with the power distribution microstrip line through the receiving impedance transformation microstrip line. The invention designs a duplex power distribution network which has the duplex function and the power distribution function, and the antenna has the advantages of compact structure and higher gain. Meanwhile, the high isolation between the transmitting port and the receiving port is realized by arranging the transmitting microstrip band elimination filter and the receiving microstrip band elimination filter.
Description
Technical Field
The invention belongs to the technical field of wireless communication, and particularly relates to a co-polarized microstrip duplex antenna array.
Background
The antenna feeder system is the foremost end of the wireless communication system and is an indispensable key component of the wireless communication system. The antenna feed system comprises an antenna, a filter and a duplexer, and the traditional method is that the antenna, the filter and the duplexer are designed independently and then connected by a radio frequency cable. The three are matched with a 50 ohm feeder line through an independent matching network, so that the problems of large size and heavy total weight are caused, and meanwhile, the defect of large loss is caused by excessive matching networks.
With the development of wireless communication, the communication system tends to be more miniaturized and integrated, and therefore, an integrated antenna feeder system has a great demand. The duplex antenna jointly designs the front-end devices such as the antenna, the filter, the duplexer and the like, so that the structure of a radio frequency front-end system is more compact, unnecessary loss introduction is reduced, and the miniaturization and integration of a communication system are easier to realize.
In the prior art, an antenna capable of realizing a duplex function (simultaneous transmission and reception of signals) is mainly a dual-polarized antenna, signals transmitted and received by the antenna of the type adopt different polarization modes, and transmission and reception of the antenna can work in the same frequency band or different frequency bands. However, in most communication systems, transmission and reception are often required to be co-polar and the transmission and reception patterns are required to be as uniform as possible. Therefore, it is necessary to develop a diplexing antenna with the same polarization.
At present, the design of the co-polarized duplex antenna mainly utilizes a microstrip patch or a slot structure to radiate two modes with the same polarization. Through isolation between modes, or adding a resonance structure in a feed network, and forming a filter antenna with a radiation structure, the isolation degree of the ports between two same-polarization working frequencies is realized. The interval between the transmitting frequency and the receiving frequency of the currently proposed co-polarized duplex antenna is relatively large, the port isolation is generally between 20dB and 30dB, and the gain of the antenna is below 5 dBi. Therefore, the existing co-polarization duplex antenna has the disadvantages of low port isolation, large antenna transmitting and receiving frequency interval and low antenna gain on the whole.
Disclosure of Invention
The invention aims to overcome the defects of the prior art and provide a co-polarized microstrip duplex antenna array, compared with the prior co-polarized duplex antenna, the co-polarized microstrip duplex antenna array has the advantages that the transmitting frequency and the receiving frequency of the antenna are closer, the isolation degree of the transmitting and receiving ports of the antenna is high, and the gain of the antenna is higher.
The purpose of the invention is realized by the following technical scheme: the co-polarization microstrip duplex antenna array comprises two identical microstrip patch antennas which are symmetrically arranged and an inverse power distribution network with a duplex function, wherein the inverse power distribution network comprises a power distribution microstrip line, a sending microstrip band rejection filter, a sending impedance conversion microstrip line, a receiving microstrip band rejection filter and a receiving impedance conversion microstrip line; one end of the sending microstrip band elimination filter is connected with the sending port, and the other end of the sending microstrip band elimination filter is connected with the power distribution microstrip line through the sending impedance transformation microstrip line; one end of the receiving microstrip band elimination filter is connected with the receiving port, and the other end of the receiving microstrip band elimination filter is connected with the power distribution microstrip line through the receiving impedance transformation microstrip line.
Preferably, the sending microstrip band-stop filter is arranged at a distance lambda from the central point of the power distribution microstrip line through the sending impedance conversion microstrip line and the power distribution microstrip line g hair At position/4 is connected, λ g hair The wavelength of the sending signal on the power distribution microstrip line.
Preferably, the receiving microstrip band-stop filter converts the microstrip line and the power distribution microstrip line through the receiving impedance and is located on the other side of the central point of the power distribution microstrip line and is lambda from the central point g harvesting At position/4 is connected, λ g harvesting The wavelength of the received signal on the power distribution microstrip line.
Specifically, the co-polarization microstrip duplex antenna array further comprises an upper dielectric substrate and a lower dielectric substrate which are arranged in parallel, wherein a metal reflection floor is covered on the upper surface of the lower dielectric substrate, and a reverse phase power distribution network is arranged on the bottom surface of the lower dielectric substrate; the microstrip patch antenna comprises two rectangular metal patches printed on the upper surface of an upper-layer dielectric substrate and a T-shaped probe for exciting the microstrip patch antenna, wherein the T-shaped probe consists of a metal microstrip printed on the surface of the upper-layer dielectric substrate and a metal probe connected to the center of the metal microstrip, and the other end of the metal probe penetrates through holes in a reflection floor and a lower-layer dielectric substrate respectively and is connected with two ends of a power distribution microstrip line.
Preferably, the sending microstrip band-stop filter consists of two sections of tail end open-circuit microstrip lines and one section of connecting microstrip line, two ends of the connecting microstrip line are respectively connected with the two tail end open-circuit microstrip lines, and the lengths and the widths of the tail end open-circuit microstrip line and the connecting microstrip line enable the frequency to be f Hair-like device Can pass through the transmission signal of (f) Harvesting machine Cannot pass through.
Preferably, the receiving microstrip band-stop filter consists of two sections of tail end open-circuit microstrip lines and one section of connecting microstrip line, two ends of the connecting microstrip line are respectively connected with the two tail end open-circuit microstrip lines, and the lengths and the widths of the tail end open-circuit microstrip line and the connecting microstrip line enable the frequency to be f Harvesting machine Can pass through a received signal of frequency f Hair-like device Cannot pass the transmission signal of (1).
Furthermore, the transmission microstrip band-stop filter and the reception microstrip band-stop filter have the working passband opposite to the stopband frequency.
Preferably, the length and width of the transmission impedance transformation microstrip line satisfy the following requirements: ensuring for a frequency f Harvesting machine When the transmission port is connected to the matching load, the impedance of the connection terminal to the power distribution microstrip line approaches an open circuit. So as not to affect the frequency f Harvesting machine And transmitting the received signal on the power distribution microstrip line.
Preferably, the length and width of the receiving impedance transformation microstrip line meet the following requirements: ensuring for a frequency f Hair-like device When the receiving port is connected to the matching load, the impedance of the connection end with the power distribution microstrip line approaches an open circuit. So as not to affect the frequency f Hair-like device And transmitting the sending signal on the power distribution microstrip line.
Furthermore, the transmitting impedance conversion microstrip line and the receiving impedance conversion microstrip line are two sections of left and right working at different frequencies and have the length of lambda g harvesting A/4 and lambda g hair A 50 omega impedance transformation line of/4.
Compared with the prior art, the invention has the following advantages and beneficial effects:
1. the invention combines the power distribution network of the array antenna with the duplex network design, and designs the duplex power distribution network which has the duplex function and the power distribution function. The structure of the antenna is compact. Meanwhile, the transmitting microstrip band-stop filter is arranged at the transmitting port, and the receiving microstrip band-stop filter is arranged at the receiving port, so that high isolation between the transmitting port and the receiving port is realized. Meanwhile, the antenna array is designed, so that the gain of the antenna is improved.
2. The signals transmitted and received are coupled with the patch antenna through the micro-strip on the T-shaped probe, the polarization direction of the signals is the same as the direction of the coupling micro-strip, and the same polarization of transmitting and receiving is realized.
3. The invention has small mutual interference of sending and receiving, and the transmitting branch circuit can not influence the receiving signal on the power distribution microstrip line by inserting the transmitting impedance conversion microstrip line between the transmitting microstrip band elimination filter and the power distribution microstrip line. By inserting the receiving impedance conversion microstrip line between the receiving microstrip band rejection filter and the power distribution microstrip line, the receiving branch does not affect the sending signal on the power distribution microstrip line when the sending port (port 1) works. Therefore, mutual interference between transmission and reception is small.
4. The existing co-polarization duplex antenna is usually designed based on a design method of a band-pass filter, while the passband of the band-pass filter focuses on the design in the passband, and the effect of inhibiting signals from passing through is generally not good outside a band which is closer to the passband, so that the frequency interval of sending and receiving is generally far so as to obtain better port isolation. The invention adopts the band elimination filter method to design the co-polarized duplex antenna, and the effect of inhibiting the signal from passing through is better outside the band which is close to the passband, thereby realizing smaller sending and receiving frequency interval and keeping better sending and receiving isolation characteristics.
Drawings
FIG. 1 is a general schematic diagram of the present embodiment and the numbering labels of the main components;
FIG. 2 is a general schematic diagram and a detailed numbering label of the present embodiment;
fig. 3 is a front sectional view of the antenna of the present embodiment;
FIG. 4 is a top view of the upper dielectric substrate of the present embodiment;
FIG. 5 is a bottom view of the upper dielectric substrate of the present embodiment;
FIG. 6 is a top view of the lower dielectric substrate of the present embodiment;
FIG. 7 is a bottom view of the lower dielectric substrate of the present embodiment;
FIG. 8 is a dimension chart of the upper surface structure of the upper dielectric substrate according to the present embodiment;
FIG. 9 is a drawing illustrating dimension marks of the lower surface structure of the upper dielectric substrate in this embodiment;
FIG. 10 is a drawing illustrating dimension marks of the upper surface structure of the lower dielectric substrate in this embodiment;
fig. 11 is a graph of simulated S-parameter of an example of the transmission band reject filter of the present embodiment;
FIG. 12 is a simulated S-parameter plot of an example of a receive band reject filter of the present embodiment;
fig. 13 is an impedance diagram of the simulated S parameter of the microstrip transmission band-stop filter connected by the transmission transforming microstrip line and the transmission port (port 1) connected to the matching load in this embodiment;
fig. 14 is an impedance diagram of the simulated S parameter of the microstrip-line band-stop filter and the receiving port (port 2) connected to the matching load in this embodiment;
fig. 15 is a test S parameter graph of the antenna of the present embodiment;
fig. 16 (a) is an E-plane test pattern excited at the antenna port 2 (2.2 GHz) of the present embodiment;
fig. 16 (b) is an H-plane test pattern excited by the antenna port 2 (2.2 GHz) of the present embodiment;
fig. 17 (a) is an E-plane test pattern excited by the antenna port 1 (2.4 GHz) of the present embodiment;
fig. 17 (b) is an H-plane test pattern excited by the antenna port 1 (2.4 GHz) of the present embodiment;
fig. 18 is a test gain versus frequency curve of the antenna of this embodiment.
Detailed Description
The present invention will be described in further detail with reference to examples and drawings, but the present invention is not limited thereto.
Referring to fig. 1, fig. 2 and fig. 3, the same-polarization microstrip duplex antenna array of this embodiment includes two identical microstrip patch antennas 1 symmetrically disposed and an inverse power distribution network 2 with a duplex function, where the inverse power distribution network 2 includes a power distribution microstrip line 3, a sending microstrip band rejection filter 4, a sending impedance transformation microstrip line 6, a receiving microstrip band rejection filter 5, and a receiving impedance transformation microstrip line 7.
One end of the sending microstrip band elimination filter 4 is connected with a sending port (port 1), and the other end is separated from the center of the power distribution microstrip line by a sending impedance conversion microstrip line 6 and a power distribution microstrip line 3Point lambda g hair At position/4 is connected, λ g hair The wavelength on the power distribution microstrip line 3 is used for transmitting signals.
One end of the receiving microstrip band elimination filter 5 is connected with a receiving port (port 2), and the other end is connected with the power distribution microstrip line 3 at the other side of the central point of the power distribution microstrip line and is separated from the central point by a lambda through a receiving impedance conversion microstrip line 7 g harvesting At position/4 is connected, λ g harvesting The wavelength on the power distribution microstrip line 3 is used for receiving signals.
The transmission impedance transformation microstrip line 6 and the reception impedance transformation microstrip line 7 are two sections of left and right working at different frequencies and have the length of lambda g harvesting A/4 and lambda g hair A 50 omega impedance transformation line of/4. The microstrip impedance transformation line 6,7 is followed by two low impedance transmission lines 21, 22, respectively, which are then connected to two ports of the radio frequency system via two 50 Ω transmission lines 25, 26. The four loaded L-shaped terminal open- circuit branch wires 19, 20, 23 and 24 are respectively loaded at two ends of the two low- impedance wires 21 and 22, and form two band-stop filters of the transmitting and receiving port with the two low-impedance wires. The working pass band and stop band frequencies of the two band-stop filters are opposite.
The sending microstrip band elimination filter 4 is composed of two sections of microstrip lines 19 and 23 with open-circuit tail ends and a section of connecting microstrip line 21, and two open- circuit microstrip lines 19 and 23 are respectively connected with two ends of the connecting microstrip line 21. The lengths and widths of the end open-circuited microstrip lines 19, 23 and the connecting microstrip line 21 are chosen appropriately so that at a frequency f Hair-like device Can pass through the transmission signal of (f) Harvesting machine Cannot pass through. As an example, when f is required Hair-like device ＝2.4GHz，f Harvesting machine When =2.2GHz, a dielectric plate with a relative dielectric constant of 2.55 and a thickness of h =0.8mm may be used as the substrate, the length of the open-circuit microstrip line 19 is 25.7mm, the width is 0.5mm, the length of the open-circuit microstrip line 23 is 26.5mm, the width is 0.5mm, the length of the connection microstrip line 21 is 25.7mm, and the width is 7mm, fig. 11 shows the S parameter of the transmission microstrip band stop filter at this time, and it can be seen that S12 is-1.94 dB at a frequency of 2.4GHz and S12 is-35.45 dB at a frequency of 2.2GHz, thereby realizing a function of blocking a received signal by transmitting a signal.
The receiving microstrip band elimination filter 5 is composed of two sections of microstrip lines 20 and 24 with open-circuit tail ends and a section of connecting microstrip line 22, and two ends of the connecting microstrip line 22 are respectively connected with the two open- circuit microstrip lines 20 and 24. The lengths and widths of the end open-circuited microstrip lines 20, 24 and the connecting microstrip line 22 are chosen appropriately so that at a frequency f Harvesting machine Can pass through a received signal of frequency f Hair-like device Cannot pass the transmission signal of (1). As an example, when f is required Hair-like device ＝2.4GHz，f Harvesting machine In the case of =2.2GHz, a dielectric board having a relative dielectric constant of 2.55 and a thickness of h =0.8mm may be used as the substrate, the length of the open microstrip line 20 is 26.5mm, the width thereof is 0.5mm, the length of the open microstrip line 24 is 25.9mm, the width thereof is 0.5mm, the length of the connection microstrip line 22 is 25.5mm, and the width thereof is 13mm, and fig. 12 shows the S parameter of the microstrip band elimination filter, where S12 is-1.22 dB at a frequency of 2.2GHz and S12 is-38.07 dB at a frequency of 2.4GHz, and a function of blocking a transmission signal by a reception signal is realized.
The length and width of the transmission impedance conversion microstrip line 6 are properly selected to ensure f for the frequency Harvesting machine The impedance of the connection terminal to the power distribution microstrip line 3 (when the transmission port (port No. 1) is connected to a matching load) is large (close to open circuit), and thus the frequency f is not affected Harvesting machine Transmission of the reception signal on the power distribution microstrip line 3. As an example, when f is required Hair-like device ＝2.4GHz，f Harvesting machine If =2.2GHz, a dielectric plate with a relative dielectric constant of 2.55 and a thickness of h =0.8mm may be used as the substrate, the length of the transmission impedance transformation microstrip line 6 is 24mm, and the width thereof is 2.25mm, and the example of the transmission microstrip band-stop filter described above is connected, and the S parameter and the impedance of the transmission port (port 1) after being connected to the matching load are as shown in fig. 13. It can be seen that at f Harvesting machine An impedance of more than 1000 ohms for a frequency of f, =2.2GHz Hair-like device The transmission signal of =2.4GHz is attenuated little.
The length and width of the receiving impedance conversion microstrip line 7 are properly selected to ensure f for the frequency Hair-like device The impedance of the transmission signal at the connection end with the power distribution microstrip line 3 (connection)Receive port (port 2) is connected to a matched load) is very large (close to open circuit) so as not to affect frequency f Hair-like device Transmission of the transmission signal on the power distribution microstrip line 3. As an example, f Hair-like device ＝2.4GHz，f Harvesting machine If =2.2GHz, a dielectric plate with a relative dielectric constant of 2.55 and a thickness of h =0.8mm may be used as the substrate, the length of the receive impedance transformation microstrip line 7 is 20mm, and the width thereof is 2.25mm, and the S parameter and the impedance of the receive port (port 2) connected to the matching load are shown in fig. 14. It can be seen that at f Harvesting machine Impedance is greater than 1000 ohms for 2.4GHz and f for frequency Hair-like device The received signal of =2.2GHz is attenuated little.
The co-polarization microstrip duplex antenna array further comprises an upper dielectric substrate 8 and a lower dielectric substrate 10 which are arranged in parallel, the upper surface of the lower dielectric substrate 10 is covered with a metal reflection floor 9, and the bottom surface is provided with the reverse phase power distribution network 2 of the antenna.
The microstrip patch antenna 1 comprises two rectangular metal patches 11 and 12 printed on the upper surface of an upper-layer dielectric substrate 8 and a T-shaped probe for exciting the microstrip patch antenna. The T-shaped probes are composed of metal micro-strips 13 and 14 printed on the lower surface of the upper-layer dielectric substrate 8 and metal probes 15 and 16 connected to the centers of the metal micro-strips 13 and 14, and the other ends of the metal probes 15 and 16 respectively penetrate through holes 17 and 18 on the reflecting floor 9 and the lower-layer dielectric substrate 10 to be connected with the two ends of the power distribution micro-strip line 3.
During transmission, a transmission signal is sent from a transmission port (port 1), and is sent to a power distribution microstrip line through a transmission microstrip band elimination filter 4 and a transmission impedance transformation microstrip line 6. The signals passing through the power distribution microstrip line are distributed to the two T-shaped probes 13, 14, 15, 16 with the same amplitude and opposite phases (the phases are different by 180 degrees), and are coupled to the radiation patches 11, 12 through the microstrips 13, 14 on the T-shaped probes. Because the two patches 11 and 12 are symmetrically placed and excited, the electromagnetic waves coupled by the micro-strips 13 and 14 can generate a phase difference of 180 degrees again at the two patches, so that the phases of the signals radiated by the two radiation patches 11 and 12 are the same, the signals can be superposed in the positive Z direction of the antenna in the same direction, and a higher antenna gain is generated. The polarization direction of the electromagnetic wave radiated by the antenna is the same as the direction of the long sides of the coupling microstrips 13, 14.
When received, received signals are received from the two radiating patch antennas 11, 12 and coupled to the T-shaped probes 13, 14, 15, 16. The polarization direction of the received electromagnetic wave is the same as the direction of the long sides of the coupling microstrips 13, 14. The reception signal is sent to both ends of the power distribution microstrip line 3 after passing through the T-shaped probes 13, 14, 15, and 16. At this time, the signals at the two ends of the power distribution microstrip line 3 are also equal in amplitude and 180 degrees out of phase. Signals at two ends of the power distribution microstrip line 3 are superposed in the same phase when reaching the receiving impedance conversion microstrip line 7 through the power distribution microstrip line with the phase of 180 degrees, and then are output from a receiving port (port 2) through the receiving impedance conversion microstrip line 7 and the receiving microstrip band elimination filter 5.
Fig. 4, 5, 6, and 7 are electrical structural diagrams of the upper and lower surfaces of two dielectric substrates, respectively, and the stripe-filled portion is a structure covered with conductive copper, and the rest is a dielectric substrate.
Fig. 8, 9 and 10 are dimension diagrams of the electrical structure of each part.
With reference to the dimensioning marks of fig. 2, 8, 9, and 10, the specific parameters of the antenna in this embodiment are as follows: the two dielectric boards are FR4 boards, the thickness c is 0.8mm, the width b is 130mm, and the length a is 200mm. The height h between the two dielectric sheets is 6mm. The rectangular patches have sides 1a, 1b of 49mm, 50mm respectively, and a spacing 1c of 49.5mm. The length 2a, the width 2b and the distance 2c of the two slender micro-strips for coupling are respectively 2mm,6.5mm and 69.5mm. The power distribution network is symmetrical left and right, and the main sizes of the power distribution network are 3a,4a,5a,6a and 3b, respectively, 28.5mm,21.78mm,22.73mm,27.3mm and 1.27mm. The lengths 7a and 8a of the two 50 omega impedance transformation lines are 24mm and 20mm, respectively, and the width 7b is 2.25mm. The widths 4b of the four open-ended L-shaped branch lines are all 0.5mm, and the lengths 9a,10a,13a and 14a are respectively 25.7mm,26.5mm and 25.9mm. The length 11a,12a and the width 5b,6b of the two-stage low-impedance transmission are respectively 25.7mm,25.5mm,7mm,13mm. The two lengths of transmission line connected to the ports are 28.83mm,33.03mm in length and 2.25mm in width respectively. Port 1 of the antenna operates in the 2.4GHz band as a transmit port. Port 2 operates in the 2.2GHz band as a receive port. The isolation of both ports is greater than 33dB in both bands, as in fig. 15. The gain of the antenna is substantially greater than 9.5dBi and the cross-polarization is greater than 20dB for both operating frequency band ranges, as shown by the simulated test patterns 16, 17 of the antenna. When the port 2 of the antenna is working, the gain of the antenna at the working frequency 2.2GHz of the port 2 is 10dBi, while the gain at the working frequency 2.4GHz of the port 1 is rapidly reduced to be below-25 dBi, and the gain difference reaches more than 30dB, as shown in FIG. 18. Similarly, when the port 1 of the antenna is working, the gain of the antenna at the working frequency 2.4GHz of the port 1 is 9.8dBi, and the gain at the working frequency 2.2GHz of the port 2 also rapidly drops below-25 dBi, and the gain difference reaches above 30dB, as shown in fig. 18. This side demonstrates the higher port isolation between the two ports of the duplex antenna.
The above embodiments are preferred embodiments of the present invention, but the present invention is not limited to the above embodiments, and any other changes, modifications, substitutions, combinations, and simplifications which do not depart from the spirit and principle of the present invention should be construed as equivalents thereof, and all such changes, modifications, substitutions, combinations, and simplifications are intended to be included in the scope of the present invention.
Claims (9)
1. The co-polarization microstrip duplex antenna array is characterized by comprising two identical microstrip patch antennas which are symmetrically arranged and an inverted power distribution network with a duplex function, wherein the inverted power distribution network comprises a power distribution microstrip line, a sending microstrip band elimination filter, a sending impedance conversion microstrip line, a receiving microstrip band elimination filter and a receiving impedance conversion microstrip line; one end of the sending microstrip band elimination filter is connected with the sending port, and the other end of the sending microstrip band elimination filter is connected with the power distribution microstrip line through the sending impedance transformation microstrip line; one end of the receiving microstrip band elimination filter is connected with the receiving port, and the other end of the receiving microstrip band elimination filter is connected with the power distribution microstrip line through the receiving impedance transformation microstrip line;
the co-polarization microstrip duplex antenna array further comprises an upper dielectric substrate and a lower dielectric substrate which are arranged in parallel, the upper surface of the lower dielectric substrate is covered with a metal reflecting floor, and the bottom surface of the lower dielectric substrate is provided with an inverse power distribution network; the microstrip patch antenna comprises two rectangular metal patches printed on the upper surface of an upper-layer dielectric substrate and a T-shaped probe for exciting the microstrip patch antenna, wherein the T-shaped probe consists of a metal microstrip printed on the surface of the upper-layer dielectric substrate and a metal probe connected to the center of the metal microstrip, and the other end of the metal probe penetrates through holes in a reflection floor and a lower-layer dielectric substrate respectively and is connected with two ends of a power distribution microstrip line.
2. The co-polarized microstrip duplex antenna array of claim 1 wherein the transmit microstrip band reject filter is configured to pass the transmit impedance transformation microstrip line and the power distribution microstrip line at a distance λ from a center point of the power distribution microstrip line g hair At position/4 is connected, λ g hair The wavelength of the sending signal on the power distribution microstrip line.
3. The co-polarized microstrip duplex antenna array as claimed in claim 1, wherein the receive microstrip band reject filter passes through the receive impedance transformation microstrip line and the power distribution microstrip line on the other side of the center point of the power distribution microstrip line and λ from the center point g harvesting At position/4 is connected, λ g harvesting The wavelength of the received signal on the power distribution microstrip line.
4. The co-polarized microstrip duplex antenna array according to claim 1 or 2, wherein the transmitting microstrip band stop filter is composed of two end open-circuited microstrip lines and a connecting microstrip line, the two ends of the connecting microstrip line are respectively connected to the two end open-circuited microstrip lines, and the lengths and widths of the end open-circuited microstrip line and the connecting microstrip line are such that the frequency is f Hair-like device Can pass through the transmission signal of (f) Harvesting machine Cannot pass through.
5. The co-polarized microstrip duplex antenna array as claimed in claim 1 or 3, wherein the receiving microstrip band stop filter is composed of two sections of open-ended microstrip lines at the ends and one section of connecting microstrip line at the endsRespectively connected with two open-circuit microstrip lines at the tail ends, wherein the length and the width of the open-circuit microstrip line at the tail end and the connection microstrip line enable the frequency to be f Harvesting machine Can pass through a received signal of frequency f Hair-like device Cannot pass the transmission signal of (1).
6. The co-polarized microstrip duplex antenna array as claimed in claim 1, wherein the operational pass band of the transmit microstrip band stop filter and the receive microstrip band stop filter are opposite to the stop band frequency.
7. The co-polarized microstrip duplex antenna array of claim 1 wherein the length and width of the transmit impedance transformation microstrip line meet the following requirements: ensuring for a frequency f Harvesting machine When the transmission port is connected to the matching load, the impedance of the connection terminal to the power distribution microstrip line approaches an open circuit.
8. The co-polarized microstrip duplex antenna array of claim 1 wherein the length and width of the receive impedance transforming microstrip line meet the following requirements: ensuring for a frequency f Hair-like device When the receiving port is connected to the matching load, the impedance of the connection end with the power distribution microstrip line approaches an open circuit.
9. The co-polarized microstrip duplex antenna array of claim 1 wherein the transmit and receive impedance transformation microstrip lines are such that the two left and right center points of the power distribution microstrip line operate at different frequencies with a length λ g receive A/4 and lambda g hair A 50 Ω impedance transformation line of/4.
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| CN107171078B (en) * | 2017-04-28 | 2023-11-24 | 华南理工大学 | Circularly polarized microstrip duplex antenna |
| CN107302130A (en) * | 2017-05-11 | 2017-10-27 | 广东通宇通讯股份有限公司 | Aerial array, Anneta module and its microband antenna unit |
| CN107134645B (en) * | 2017-05-23 | 2023-03-21 | 华南理工大学 | FDD antenna based on dual-mode resonator |
| CN107369899B (en) * | 2017-07-18 | 2023-03-21 | 华南理工大学 | Filtering antenna array based on multi-mode resonator |
| WO2019047091A1 (en) * | 2017-09-07 | 2019-03-14 | 广东通宇通讯股份有限公司 | Base station antenna and antenna array module thereof |
| CN108400449A (en) * | 2018-03-19 | 2018-08-14 | 重庆大学 | A kind of three array element Microstrip Planar Array Antennas row of high degree of isolation |
| CN108847865A (en) * | 2018-08-24 | 2018-11-20 | 南京濠暻通讯科技有限公司 | A kind of Anneta module for the 5th third-generation mobile communication mimo system |
| EP3734757B1 (en) * | 2019-05-02 | 2023-05-17 | Nokia Solutions and Networks Oy | A multi-band antenna arrangement |
| US11509060B2 (en) | 2019-10-21 | 2022-11-22 | City University Of Hong Kong | Filter-antenna and method for making the same |
| CN116722360B (en) * | 2023-08-10 | 2023-10-31 | 广东工业大学 | Stacked high-isolation full-duplex antenna based on deep learning optimization and communication equipment |
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| US5068669A (en) * | 1988-09-01 | 1991-11-26 | Apti, Inc. | Power beaming system |
| US8854159B2 (en) * | 2011-03-20 | 2014-10-07 | King Saud University | Triple-mode microstrip filter |
| CN102403562A (en) * | 2011-11-02 | 2012-04-04 | 华南理工大学 | Powder divider integrating a dual-frequency bandpass filter |
| CN103887583B (en) * | 2012-12-21 | 2016-09-14 | 京信通信系统（中国）有限公司 | Micro-strip triplexer |
| CN105140645A (en) * | 2015-08-26 | 2015-12-09 | 电子科技大学 | Harmonic suppressing antenna |
| CN206076497U (en) * | 2016-09-28 | 2017-04-05 | 华南理工大学 | Same polarization micro-strip duplexed antenna array |
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