CN106253657B - Power factor correcting converter mean value current control method and its device - Google Patents
Power factor correcting converter mean value current control method and its device Download PDFInfo
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- CN106253657B CN106253657B CN201610720055.9A CN201610720055A CN106253657B CN 106253657 B CN106253657 B CN 106253657B CN 201610720055 A CN201610720055 A CN 201610720055A CN 106253657 B CN106253657 B CN 106253657B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The output voltage of converter and voltage reference value are generated signal V by a kind of power factor correcting converter mean value current control method and its device in each switch periods start time by compensatore, the output voltage of rectifier bridge is obtained into signal V by amplifierc, by VeAnd VcSignal I is obtained by multiplierc；By the output voltage and I of the output voltage of rectifier bridge and output current, convertercIt is sent into duty cycle generator, signal d is calculated by duty ratio algorithmxAnd dy, control sequential V is generated using pulse width modulatorP1And VP2；By the output voltage and I of the output voltage of rectifier bridge and output current, convertercIt is sent into determining device and selector, selects VP1Or VP2；Control the conducting and shutdown of converter switches pipe.The present invention is suitable for multiple power factor correction converter topology, and in wide input voltage and wide loading range, converter keeps good power factor emendation function and higher working efficiency, and possesses quick load transient response speed.
Description
Technical field
The present invention relates to the control method of PFC (Power Factor Correction, PFC) converter and
Realization device belongs to power electronic equipment field, specially a kind of pfc converter mean value current control method and its device.
Background technology
With the development of power electronic technique, the utilization of power electronic equipment is more and more extensive.Power electronic equipment includes
There are all kinds of nonlinear devices and energy storage device, is directly accessed public electric wire net in use, power network current can be made to generate distortion, i.e.,
It is filled with a large amount of harmonic waves in power grid, has severely impacted the normal operation of grid supply quality and other electrical equipments,
The damage of electrical equipment can even be caused.
In order to ensure the normal power supply of public electric wire net, needs to use PFC technologies, that is, use filter.Filter can divide
For passive filter and active filter, passive filter has many advantages, such as that simple in structure, at low cost, reliability is high and EMI is small,
But its size and weight are big, and working performance is changed by working frequency, load variation and input voltage variation are influenced.Active filter
The PFC performance of wave device is good, and power factor can reach 90% or more, makes input current close to sine.Active filter
Wave device can work under wider input voltage range and broadband, and its volume and weight is small, can stabilize the output voltage
Value.Therefore, active PFC technologies are widely used in the industry.
The control method of traditional active PFC converter is divided into frequency control and fixed-frequency control, and frequency control is mainly electricity
Flow Hysteresis control；Fixed-frequency control mainly has peak value comparison method and Average Current Control.The work(of current hysteresis-band control pfc converter
Rate factor is high, fast response time, but working frequency is not fixed, and output filter is difficult to design；Peak value comparison method PFC transformation
The power factor of device is relatively low, cannot be satisfied the requirement of total harmonic distortion (Total Harmonic Distortion, THD), and
The control method is quite sensitive to noise；Average Current Control pfc converter has the THD of higher power factor and very little,
To insensitive for noise, and can be adapted for continuous current mode conduction mode (continuous conduction mode,
) and intermittent conductive pattern (discontinuous conduction mode, DCM) CCM.However, Average Current Control uses
Two PI compensators, therefore the transient response speed of Average Current Control is slower.Wherein, outer shroud PI compensators are exported for adjusting
Voltage makes it stable；Inner ring PI compensators are for making inductive current follow reference value；Inner ring PI compensation is substituted with other methods
Device can effectively improve transient response speed.
Invention content
The object of the present invention is to provide a kind of pfc converter mean value current control method and its device, it is allowed to have simultaneously
Higher power factor (Power Factor, PF) value, faster transient response speed and higher efficiency are suitable for all kinds of bases
This pfc converter topology.
The technical scheme adopted by the invention for realizing the object of the invention is as follows：
A kind of power factor correcting converter mean value current control method, in each switch periods start time, detection is whole
The output voltage for flowing the output voltage and output current and the power factor correcting converter of bridge, respectively obtains signal Vs、In
And Vn；By VsIt is sent into amplifier and obtains signal Vc, by VnWith voltage reference value VrefIt is sent into compensator and obtains signal Ve, by VcAnd Ve
It is sent into multiplier and obtains signal Ic；By In、Vs、IcAnd VnIt is sent into the first duty cycle generator and obtains signal dx1And dx2, by dx1With
dx2It is sent into the first pulse width modulator and obtains signal VP1；By In、Vs、IcAnd VnIt is sent into the second duty cycle generator and obtains signal dy1With
dy2, by dy1And dy2It is sent into the second pulse width modulator and obtains signal VP2；By In、Vs、IcAnd VnIt is sent into determining device and obtains signal Vj；It will
VP1、VP2And VjIt is sent into selector and obtains signal VP, to control conducting and the pass of the power factor correcting converter switching tube
It is disconnected.
Further, described by In、Vs、IcAnd VnIt is sent into the first duty cycle generator and obtains signal dx1And dx2Method be,
It is equal to I according to the inductor current value at the end of current switch periodcAnd dx1Equal to dx2, the first duty cycle generator calculating dx1
And dx2, dx1=dx2=0.5 [K1+K2(Ic-In)]；It is described by In、Vs、IcAnd VnIt is sent into the second duty cycle generator and obtains signal
dy1And dy2Method be, according to the inductor current value at the end of current switch period be equal to IcAnd inductance in current switch period
The average value of electric current is equal to Ic, the second duty cycle generator calculating dy1And dy2, dy1=K3In+(K4In 2+K5Ic 2+K6Ic)1/2,dy2
=K7Ic；Wherein K1、K2、K3、K4、K5、K6And K7It is and signal Vn、VsAnd the inductive current of the power factor correcting converter
The relevant coefficient of ripple.
A kind of power factor correcting converter mean value current control device, including the inspection of current detection circuit IS, first voltage
Slowdown monitoring circuit VS1, second voltage detection circuit VS2, compensator EC, amplifier GA, multiplier MUL, the first duty cycle generator
DG1, the second duty cycle generator DG2, the first pulse width modulator DP1, the second pulse width modulator DP2, determining device JU and selector
CH；First voltage detection circuit VS1, amplifier GA, multiplier MUL are sequentially connected；Second voltage detection circuit VS2, compensator
EC, multiplier MUL are sequentially connected；Current detection circuit IS and the first duty cycle generator DG1, determining device JU, the second duty ratio
Generator DG2 is respectively connected with；First voltage detection circuit VS1 and the first duty cycle generator DG1, determining device JU, the second duty
It is respectively connected with than generator DG2；Second voltage detection circuit VS2 is accounted for the first duty cycle generator DG1, determining device JU, second
Sky is respectively connected with than generator DG2；Multiplier MUL and the first duty cycle generator DG1, determining device JU, the second duty ratio generate
Device DG2 is respectively connected with；First duty cycle generator DG1, the first pulse width modulator DP1, selector CH are sequentially connected；Determining device JU
It is connected with selector CH；Second duty cycle generator DG2, the second pulse width modulator DP2, selector CH are sequentially connected.
Compared with prior art, the beneficial effects of the invention are as follows：
One, compared with the pfc converter of traditional Average Current Control, pfc converter of the invention is in each switch periods
When beginning, the inductive current average value in the period is calculated, and realized to average by way of controlling switching tube conducting and shutdown
The tracking of value improves the PF values of pfc converter.
Two, compared with the pfc converter of traditional Average Current Control, pfc converter of the invention changes in load
When, the time of switching tube conducting and shutdown in each switch periods is effectively had adjusted according to duty ratio algorithm, makes inductive current
Value quickly follows average value, improves the load transient performance of pfc converter.
Three, compared with the pfc converter of traditional Average Current Control, pfc converter of the invention is in input voltage zero passage
When, the distortion of inductive current is reduced, to reduce loss, improves the efficiency of pfc converter.
Description of the drawings
Fig. 1 is the signal flow block diagram of one method of the embodiment of the present invention.
Fig. 2 is the circuit structure block diagram of the embodiment of the present invention one.
Fig. 3 a are the first pulse width modulator DP1 algorithm schematic diagrames of the embodiment of the present invention one.
Fig. 3 b are the second pulse width modulator DP2 algorithm schematic diagrames of the embodiment of the present invention one.
Input voltage V when Fig. 4 is one pfc converter steady operation of the embodiment of the present inventioninWith input current IinTime domain
Simulation waveform.
Fig. 5 is the PF being respectively adopted when of the invention and tradition Average Current Control pfc converter changes with load resistance
It is worth curve graph.
Fig. 6 is when of the invention and tradition Average Current Control pfc converter is respectively adopted with input voltage amplitude to change
PF value curve graphs.
Fig. 7 a are one pfc converter of embodiment of the present invention output voltage wink when load resistance jumps to 400 Ω by 100 Ω
State time-domain-simulation oscillogram.
Fig. 7 b are defeated when load resistance jumps to 400 Ω by 100 Ω using the pfc converter of traditional Average Current Control
Go out voltage transient time-domain-simulation oscillogram.
Fig. 8 a are one pfc converter of embodiment of the present invention output voltage wink when load resistance jumps to 400 Ω by 500 Ω
State time-domain-simulation oscillogram.
Fig. 8 b are defeated when load resistance jumps to 400 Ω by 500 Ω using the pfc converter of traditional Average Current Control
Go out voltage transient time-domain-simulation oscillogram.
Fig. 9 is that the pfc converter of of the invention and traditional Average Current Control is respectively adopted with the efficiency song loaded when changing
Line chart.
Figure 10 is the circuit structure diagram of the embodiment of the present invention two.
Specific implementation mode
Further detailed description is done to the present invention below by specific example with reference.
Embodiment one
Fig. 1 shows that a kind of specific implementation mode of the invention is：Pfc converter mean value current control method and its device,
Including current detection circuit IS, first voltage detection circuit VS1, second voltage detection circuit VS2, compensator EC, amplifier GA,
Multiplier MUL, the first duty cycle generator DG1, the second duty cycle generator DG2, the first pulse width modulator DP1, the second pulsewidth
Modulator DP2, determining device JU and selector CH compositions；Current detection circuit IS is used to obtain the output current information of rectifier bridge
In, output voltage information Vs of the first voltage detection circuit VS1 for obtaining rectifier bridges, second voltage detection circuit VS2 is for obtaining
Take converter TD output voltage information Vn, compensator EC is for generating error signal Ve, determining device JU is for generating selection signal
Vj, decision circuitry is operated in CCM or DCM, and the first duty cycle generator DG1 is for generating CCM duty cycle signals dx1And dx2, the
Two duty cycle generator DG2 are for generating DCM duty cycle signals dy1And dy2, the first pulse width modulator DP1 is for generating CCM's
Control sequential VP1；Second pulse width modulator DP2 is used to generate the control sequential V of DCMP2, selector CH for select CCM or
The control sequential of DCM, and export control signal VP, control the turn-on and turn-off of pfc converter TD switching tubes.
Its course of work is, by VnWith preset reference voltage VrefCompensator EC is sent into for generating error signal Ve；It puts
Big device GA is used for scaling rectifier bridge output voltage signal Vs, obtain rectifier bridge output voltage reference signal Vc；By VcAnd VeFeeding multiplies
Musical instruments used in a Buddhist or Taoist mass obtains inductive current average value reference signal Ic, it is used for duty cycle signals dx1And dx2、dy1And dy2Calculating and selection letter
Number VjCalculating；First duty cycle generator DG1 is used to generate the first pulse width modulator DP1 and calculates required duty cycle signals dx1
And dx2, dx1=dx2=0.5 [K1+K2(Ic-In)]；Second duty cycle generator DG2 is by generating based on the second pulse width modulator DP2
Duty cycle signals d needed for calculatingy1And dy2, dy1=K3In+(K4In 2+K5Ic 2+K6Ic)1/2,dy2=K7Ic；Determining device JU is for generating
Selection signal Vj, decision circuitry is operated in CCM or DCM, works as VjWhen=1, circuit is operated in CCM, works as VjWhen=0, circuit work
In DCM；Wherein K1、K2、K3、K4、K5、K6And K7It is and signal Vn、VsAnd the inductive current of the power factor correcting converter
The relevant coefficient of ripple.When first pulse width modulator DP1 is used to generate CCM when the control of converter TD switching tube turn-on and turn-off
Sequence VP1；The control sequential V of converter TD switching tube turn-on and turn-off when second pulse width modulator DP2 is used to generate DCMP2；Selection
Device CH is used for according to selection signal VjSelect control sequential VP1Or VP2, and generate control signal VP。
Above-mentioned K1、K2、K3、K4、K5、K6And K7Expression it is as follows： Wherein TsFor
Switch periods, m1And m2The respectively rate of rise and descending slope of inductive current variation, i.e.,：
Fig. 2 shows the realization devices of the pfc converter mean value current control of this example, by converter TD and control device group
At.
Its working process and principle of the device of this example are：
When each switch periods start, the output voltage and output current and converter of detection converter TD rectifier bridges
The output voltage of TD obtains signal Vs、InAnd Vn；By VsV is obtained by amplifierc, by VnAnd VrefError is obtained by compensator
Signal Ve, by VcAnd VeSignal I is obtained by multiplierc；By In、Vs、IcAnd VnIt is sent into the first duty cycle generator and obtains signal
dx1And dx2, by dx1And dx2It is sent into the first pulse width modulator and obtains signal VP1；By In、Vs、IcAnd VnIt is sent into the generation of the second duty ratio
Device obtains signal dy1And dy2, by dy1And dy2It is sent into the second pulse width modulator and obtains signal VP2；By In、Vs、IcAnd VnIt is sent into and judges
Device obtains signal Vj；By VP1、VP2And VjIt is sent into selector and obtains signal VP, control leading for power factor correcting converter switching tube
Logical and shutdown.
Fig. 3 a are duty ratio dx1And dx2Schematic diagram is generated, the operation principle of the first duty cycle generator DG1 is：Each open
When the pass period starts, duty ratio d is calculatedx1And dx2, design conditions are：1. the inductor current value etc. at the end of current switch period
In Ic, 2. two sections of duty ratios are equal.Duty ratio d is calculatedx1=dx2=0.5 [K1+K2(Ic-In)], wherein K1And K2It is two
With signal Vn、VsAnd the relevant coefficient of inductive current ripple.Fig. 3 b are duty ratio dy1And dy2Generate schematic diagram, the second duty ratio
The operation principle of generator DG2 is：When each switch periods start, duty ratio d is calculatedy1And dy2, design conditions are：1. current
Inductor current value at the end of switch periods is equal to Ic, 2. the average value of inductive current is equal to I in current switch periodc.It calculates
To duty ratio dy1=K3In+(K4In 2+K5Ic 2+K6Ic)1/2,dy2=K7Ic, wherein K3、K4、K5、K6And K7It is and signal Vn、VsAnd
The relevant coefficient of inductive current ripple.
The converter TD of this example is Boost pfc converters.
Time-domain-simulation analysis is carried out to the method for this example with PSIM simulation softwares, it is as a result as follows.
Input voltage V when Fig. 4 is one pfc converter steady operation of the embodiment of the present inventioninWith input current IinTime domain
Simulation waveform.Input current waveform is close to sine at this time, and does not have phase difference with input voltage, realizes PFC
Function.Simulated conditions：Input voltage VinIt is the alternating voltage that amplitude is 200V, frequency is 50Hz, reference voltage Vref=4V
(corresponding output voltage 400V), inductance L=200 μ H, capacitance C=470 μ F (its equivalent series resistance is 1m Ω), load resistance R
=100 Ω, switch periods Ts=20 μ s, compensator parameter KP=0.1, KI=5.
Fig. 5 is that the pfc converter of of the invention and traditional Average Current Control is respectively adopted with the PF value songs loaded when changing
Line chart.Simulated conditions are identical as Fig. 4, and the variation range of load resistance is the Ω of 50 Ω~500.When load resistance is larger, two kinds
Pfc converter has similar PF values under control method.When load resistance is more than 200 Ω, with the increase of load resistance, two
The PF values of pfc converter reduce under kind control method；When load resistance is less than 200 Ω, with the reduction of load resistance, pass
The PF values of system Average Current Control pfc converter reduce, and the PF values of the present invention increase.In resistance variation range, this
The PF values of invention are above 99%.Therefore pfc converter using the present invention has good PF values under different loads.
Fig. 6 is when of the invention and tradition Average Current Control pfc converter is respectively adopted with input voltage amplitude to change
PF value curve graphs.Simulated conditions are identical as Fig. 4, and input voltage amplitude variation range is 180V~250V.With input voltage
When the reduction of amplitude, the PF values of the lower pfc converter of two kinds of controls reduce, but the PF values of the present invention are above the average electricity of tradition
The PF values of flow control pfc converter, and it is maintained at 99.5% or more.Therefore the present invention has well under different input voltage amplitudes
Power factor emendation function.
Fig. 7 a and Fig. 7 b are respectively that the pfc converter of of the invention, traditional Average Current Control is jumped in load resistance by 100 Ω
Output voltage transient state time-domain-simulation oscillogram when changing to 400 Ω, converter simulated conditions are identical as Fig. 4.At this point, converter works
Pattern is DCM by CCM variations.For Fig. 7 it is found that after load variation, two kinds of control methods can make voltage stabilization in 400V, and tradition is flat
Equal current control pfc converter is restored to 400V by the time of 0.22s；Pfc converter using the present invention is by 0.1s's
Time is restored to 400V, and the output voltage peak value fluctuation of the present invention is less than traditional Average Current Control, it can thus be appreciated that this hair
It is bright to possess faster load transient response speed.
Fig. 8 a and Fig. 8 b are respectively that the pfc converter of of the invention, traditional Average Current Control is jumped in load resistance by 500 Ω
Output voltage transient state time-domain-simulation oscillogram when changing to 400 Ω, converter simulated conditions are identical as Fig. 4.At this point, the equal work of converter
Make in DCM.As shown in Figure 8, regulating time of the invention is 0.8s, and the regulating time of traditional Average Current Control is 1.3s.This
The output voltage valley fluctuation of invention is about 4V, and the output voltage valley fluctuation of traditional Average Current Control is about 7V.Comparison can
Know, when pfc converter is operated in DCM, the present invention has better load transient performance.
Fig. 9 is that the pfc converter of of the invention and traditional Average Current Control is respectively adopted with the efficiency song loaded when changing
Line chart.Converter simulated conditions are identical as Fig. 4, and the variation range of load resistance is the Ω of 50 Ω~500.With the increasing of load resistance
Add, the efficiency of the lower pfc converter of two kinds of controls reduces.In entire load variation, compared to traditional Average Current Control, originally
Invention has higher efficiency, and efficiency is above 90%.It follows that pfc converter using the present invention possess it is higher
Working efficiency.
Embodiment two
As shown in Figure 10, this example and embodiment one are essentially identical, are a difference in that：This example control converter TD be
Buck-boost pfc converters.
The present invention is in addition to it can be used for the pfc converter in above example, it can also be used to flyback pfc converter, half-bridge PFC
In the pfc converters topologys such as converter, full-bridge pfc converter.
Claims (1)
1. a kind of power factor correcting converter mean value current control method, it is characterised in that：When each switch periods start
It carves, detects the output voltage of the output voltage and output current and the power factor correcting converter of rectifier bridge, respectively
To signal Vs、InAnd Vn；By VsIt is sent into amplifier and obtains signal Vc, by VnWith voltage reference value VrefIt is sent into compensator and obtains signal
Ve, by VcAnd VeIt is sent into multiplier and obtains signal Ic；By In、Vs、IcAnd VnIt is sent into the first duty cycle generator and obtains signal dx1With
dx2, by dx1And dx2It is sent into the first pulse width modulator and obtains signal VP1；By In、Vs、IcAnd VnThe second duty cycle generator is sent into obtain
To signal dy1And dy2, by dy1And dy2It is sent into the second pulse width modulator and obtains signal VP2；By In、Vs、IcAnd VnDetermining device is sent into obtain
To signal Vj；By VP1、VP2And VjIt is sent into selector and obtains signal VP, to control the power factor correcting converter switching tube
Conducting and shutdown；
It is described by In、Vs、IcAnd VnIt is sent into the first duty cycle generator and obtains signal dx1And dx2Method be, according to current switch
Inductor current value when end cycle is equal to IcAnd dx1Equal to dx2, the first duty cycle generator calculating dx1And dx2, dx1=dx2
=0.5 [K1+K2(Ic-In)]；It is described by In、Vs、IcAnd VnIt is sent into the second duty cycle generator and obtains signal dx1And dx2Method
It is that I is equal to according to the inductor current value at the end of current switch periodcAnd in current switch period inductive current it is flat between
Equal to Ic, the second duty cycle generator calculating dy1And dy2, dy1=(K3In 2+K4In+K5Ic 2+K6Ic)1/2,dy2=K7Ic；Above-mentioned K1、
K2、K3、K4、K5、K6And K7Expression it is as follows：
Wherein TsFor switch periods, m1And m2The respectively rate of rise and descending slope of inductive current variation, i.e.,：Wherein K1、K2、K3、K4、K5、K6And K7It is and signal Vn、VsAnd the PFC becomes
The relevant coefficient of inductive current ripple of parallel operation.
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| CN109921625B (en) * | 2019-03-25 | 2023-09-08 | 西南交通大学 | PFC converter pulse frequency modulation mean current control method and device |
| CN113315391A (en) * | 2021-04-29 | 2021-08-27 | 武汉华海通用电气有限公司 | Digital PFC circuit |
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| CN101252311A (en) * | 2007-02-23 | 2008-08-27 | 英特尔公司 | Adaptive controller with mode tracking and parametric estimation for digital power converters |
| CN102904439A (en) * | 2012-10-13 | 2013-01-30 | 华南理工大学 | Mixed control method for direct current (DC)-direct current (DC) convertor |
| CN104917358A (en) * | 2014-03-12 | 2015-09-16 | Det国际控股有限公司 | Duty-ratio controller |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101252311A (en) * | 2007-02-23 | 2008-08-27 | 英特尔公司 | Adaptive controller with mode tracking and parametric estimation for digital power converters |
| CN102904439A (en) * | 2012-10-13 | 2013-01-30 | 华南理工大学 | Mixed control method for direct current (DC)-direct current (DC) convertor |
| CN104917358A (en) * | 2014-03-12 | 2015-09-16 | Det国际控股有限公司 | Duty-ratio controller |
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