CN106253657A - Power factor correcting converter average current control method and device thereof - Google Patents
Power factor correcting converter average current control method and device thereof Download PDFInfo
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- CN106253657A CN106253657A CN201610720055.9A CN201610720055A CN106253657A CN 106253657 A CN106253657 A CN 106253657A CN 201610720055 A CN201610720055 A CN 201610720055A CN 106253657 A CN106253657 A CN 106253657A
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
A kind of power factor correcting converter average current control method and device thereof, in each switch periods start time, produce signal V with voltage reference value through compensator by the output voltage of changere, the output voltage of rectifier bridge is obtained signal V through amplifierc, by VeAnd VcSignal I is obtained through multiplierc；By the output voltage of rectifier bridge and output electric current, the output voltage of changer and IcSend into duty cycle generator, be calculated signal d by dutycycle algorithmxAnd dy, then produce control sequential V through pulse width modulatorP1And VP2；By the output voltage of rectifier bridge and output electric current, the output voltage of changer and IcSend into diagnosis apparatus and selector, select VP1Or VP2；Control conducting and the shutoff of converter switches pipe.The present invention is applicable to multiple power factor correction converter topology, and in wide input voltage and wide loading range, changer keeps good power factor emendation function and higher work efficiency, and has quick load transient response speed.
Description
Technical field
The present invention relates to PFC (Power Factor Correction, PFC) changer control method and
Realize device, belong to power electronic equipment field, be specially a kind of pfc converter average current control method and device thereof.
Background technology
Along with the development of Power Electronic Technique, the utilization of power electronic equipment is more and more extensive.Power electronic equipment comprises
There are all kinds of nonlinear device and energy storage device, when being directly accessed public electric wire net use, power network current can be made to produce distortion, i.e.
In electrical network, it is filled with a large amount of harmonic wave, severely impacts the normal operation of grid supply quality and other electrical equipments,
Even can cause the damage of electrical equipment.
In order to ensure the normal power supply of public electric wire net, need to use PFC technology, i.e. use wave filter.Wave filter can divide
For passive filter and active filter, passive filter has the advantages such as simple in construction, low cost, reliability height and EMI are little,
But its size and weight are big, service behaviour is changed by operating frequency change, load change and input voltage to be affected.Active filter
The PFC performance of ripple device is good, and its power factor can arrive more than 90%, makes input current close to sinusoidal.Active filter
Ripple device can work under wider input voltage range and broadband, and its volume and weight is little, can regulated output voltage
Value.Therefore, active PFC technology is widely used in the industry.
The control method of traditional active PFC converter is divided into VFC and fixed-frequency control, VFC predominantly electricity
Stream Hysteresis control；Fixed-frequency control mainly has peak value comparison method and Average Current Control.The merit of current hysteresis-band control pfc converter
Rate factor is high, fast response time, but operating frequency is not fixed, and output filter is difficult to design；Peak value comparison method PFC converts
The power factor of device is relatively low, it is impossible to meet the requirement of total harmonic distortion (Total Harmonic Distortion, THD), and
This control method is the most sensitive to noise；Average Current Control pfc converter has higher power factor and the least THD,
To insensitive for noise, and go for continuous current mode conduction mode (continuous conduction mode,
And intermittent conductive pattern (discontinuous conduction mode, DCM) CCM).But, Average Current Control employs
Two PI compensators, therefore the transient response speed of Average Current Control is slower.Wherein, outer shroud PI compensator is used for regulating output
Voltage, makes it stable；Internal ring PI compensator is used for making inductive current follow reference value；Substitute internal ring PI with additive method to compensate
Device, can be effectively improved transient response speed.
Summary of the invention
It is an object of the invention to provide a kind of pfc converter average current control method and device thereof, be allowed to have simultaneously
Higher power factor (Power Factor, PF) value, faster transient response speed and higher efficiency, it is adaptable to all kinds of bases
This pfc converter topology.
It is as follows that the present invention realizes the technical scheme that its goal of the invention used:
A kind of power factor correcting converter average current control method, in each switch periods start time, detects whole
The output voltage of stream bridge and output electric current and the output voltage of described power factor correcting converter, respectively obtain signal Vs、In
And Vn；By VsSend into amplifier and obtain signal Vc, by VnWith voltage reference value VrefSend into compensator and obtain signal Ve, by VcAnd Ve
Send into multiplier and obtain signal Ic；By In、Vs、IcAnd VnSend into the first duty cycle generator and obtain signal dx1And dx2, by dx1With
dx2Send into the first pulse width modulator and obtain signal VP1；By In、Vs、IcAnd VnSend into the second duty cycle generator and obtain signal dy1With
dy2, by dy1And dy2Send into the second pulse width modulator and obtain signal VP2；By In、Vs、IcAnd VnSend into diagnosis apparatus and obtain signal Vj；Will
VP1、VP2And VjSend into selector and obtain signal VP, in order to control conducting and the pass of described power factor correcting converter switching tube
Disconnected.
Further, described by In、Vs、IcAnd VnSend into the first duty cycle generator and obtain signal dx1And dx2Method be,
According to the inductor current value at the end of current switch period equal to IcAnd dx1Equal to dx2, the first duty cycle generator calculates dx1
And dx2, dx1=dx2=0.5 [K1+K2(Ic-In)]；Described by In、Vs、IcAnd VnSend into the second duty cycle generator and obtain signal
dy1And dy2Method be, according to the inductor current value at the end of current switch period equal to IcAnd current switch period internal inductance
The meansigma methods of electric current is equal to Ic, the second duty cycle generator calculates dy1And dy2, dy1=K3In+(K4In 2+K5Ic 2+K6Ic)1/2,dy2
=K7Ic；Wherein K1、K2、K3、K4、K5、K6And K7It is and signal Vn、VsAnd the inductive current of described power factor correcting converter
The coefficient that ripple is relevant.
A kind of power factor correcting converter average current control device, including current detection circuit IS, the first voltage inspection
Slowdown monitoring circuit VS1, the second voltage detecting circuit VS2, compensator EC, amplifier GA, multiplier MUL, the first duty cycle generator
DG1, the second duty cycle generator DG2, the first pulse width modulator DP1, the second pulse width modulator DP2, diagnosis apparatus JU and selector
CH；First voltage detecting circuit VS1, amplifier GA, multiplier MUL are sequentially connected；Second voltage detecting circuit VS2, compensator
EC, multiplier MUL are sequentially connected；Current detection circuit IS and the first duty cycle generator DG1, diagnosis apparatus JU, the second dutycycle
Maker DG2 is respectively connected with；First voltage detecting circuit VS1 and the first duty cycle generator DG1, diagnosis apparatus JU, the second duty
It is respectively connected with than maker DG2；Second voltage detecting circuit VS2 and the first duty cycle generator DG1, diagnosis apparatus JU, second account for
Sky is respectively connected with than maker DG2；Multiplier MUL and the first duty cycle generator DG1, diagnosis apparatus JU, the second dutycycle generate
Device DG2 is respectively connected with；First duty cycle generator DG1, the first pulse width modulator DP1, selector CH are sequentially connected；Diagnosis apparatus JU
It is connected with selector CH；Second duty cycle generator DG2, the second pulse width modulator DP2, selector CH are sequentially connected.
Compared with prior art, the invention has the beneficial effects as follows:
One, compared with the pfc converter of tradition Average Current Control, the pfc converter of the present invention is in each switch periods
During beginning, calculate the inductive current meansigma methods in this cycle, and realize averagely by the way of shutoff by controlling switching tube conducting
The tracking of value, improves the PF value of pfc converter.
Two, compared with the pfc converter of tradition Average Current Control, the pfc converter of the present invention changes in load
Time, in effectively have adjusted each switch periods according to dutycycle algorithm, switching tube turns on and the time turned off, and makes inductive current
Value quickly follows meansigma methods, improves the load transient performance of pfc converter.
Three, compared with the pfc converter of tradition Average Current Control, the pfc converter of the present invention is in input voltage zero passage
Time, reduce the distortion of inductive current, thus decrease loss, improve the efficiency of pfc converter.
Accompanying drawing explanation
Fig. 1 is the signal flow block diagram of the embodiment of the present invention one method.
Fig. 2 is the circuit structure block diagram of the embodiment of the present invention one.
Fig. 3 a is the first pulse width modulator DP1 algorithm schematic diagram of the embodiment of the present invention one.
Fig. 3 b is the second pulse width modulator DP2 algorithm schematic diagram of the embodiment of the present invention one.
Fig. 4 is the input voltage V during embodiment of the present invention one pfc converter steady operationinWith input current IinTime domain
Simulation waveform figure.
Fig. 5 is the pfc converter being respectively adopted the present invention and tradition Average Current Control PF when changing with load resistance
Value curve chart.
Fig. 6 is that the pfc converter being respectively adopted the present invention and tradition Average Current Control is when changing with input voltage amplitude
PF value curve chart.
Fig. 7 a is the embodiment of the present invention one pfc converter output voltage wink when load resistance is jumped to 400 Ω by 100 Ω
State time-domain-simulation oscillogram.
Fig. 7 b is that the pfc converter of employing tradition Average Current Control is defeated when load resistance is jumped to 400 Ω by 100 Ω
Go out voltage transient time-domain-simulation oscillogram.
Fig. 8 a is the embodiment of the present invention one pfc converter output voltage wink when load resistance is jumped to 400 Ω by 500 Ω
State time-domain-simulation oscillogram.
Fig. 8 b is that the pfc converter of employing tradition Average Current Control is defeated when load resistance is jumped to 400 Ω by 500 Ω
Go out voltage transient time-domain-simulation oscillogram.
Fig. 9 is that the pfc converter being respectively adopted the present invention and tradition Average Current Control is bent with efficiency during load change
Line chart.
Figure 10 is the circuit structure diagram of the embodiment of the present invention two.
Detailed description of the invention
Below by concrete example with reference, the present invention is done further detailed description.
Embodiment one
Fig. 1 illustrates, a kind of detailed description of the invention of the present invention is: pfc converter average current control method and device thereof,
Including current detection circuit IS, the first voltage detecting circuit VS1, the second voltage detecting circuit VS2, compensator EC, amplifier GA,
Multiplier MUL, the first duty cycle generator DG1, the second duty cycle generator DG2, the first pulse width modulator DP1, the second pulsewidth
Manipulator DP2, diagnosis apparatus JU and selector CH composition；Current detection circuit IS is for obtaining the output current information of rectifier bridge
In, the first voltage detecting circuit VS1 is for obtaining output voltage information V of rectifier bridges, the second voltage detecting circuit VS2 is used for obtaining
Take changer TD output voltage information Vn, compensator EC is used for generating error signal Ve, it is judged that device JU is used for generating selection signal
Vj, it is judged that circuit is operated in CCM or DCM, and the first duty cycle generator DG1 is used for producing CCM duty cycle signals dx1And dx2, the
Two duty cycle generator DG2 are used for producing DCM duty cycle signals dy1And dy2, the first pulse width modulator DP1 is for producing CCM's
Control sequential VP1；Second pulse width modulator DP2 is for producing control sequential V of DCMP2, selector CH be used for selecting CCM or
The control sequential of DCM, and export control signal VP, control the turn-on and turn-off of pfc converter TD switching tube.
Its work process is, by VnWith default reference voltage VrefSend into compensator EC to be used for generating error signal Ve；Put
Big device GA is for scaling rectifier bridge output voltage signal Vs, obtain rectifier bridge output voltage reference signal Vc；By VcAnd VeFeeding is taken advantage of
Musical instruments used in a Buddhist or Taoist mass obtains inductive current meansigma methods reference signal Ic, for duty cycle signals dx1And dx2、dy1And dy2Calculating and select letter
Number VjCalculating；First duty cycle generator DG1 is for producing the duty cycle signals d needed for the first pulse width modulator DP1 calculatesx1
And dx2, dx1=dx2=0.5 [K1+K2(Ic-In)]；Second duty cycle generator DG2 is by producing based on the second pulse width modulator DP2
Duty cycle signals d needed for calculationy1And dy2, dy1=K3In+(K4In 2+K5Ic 2+K6Ic)1/2,dy2=K7Ic；Diagnosis apparatus JU is used for generating
Select signal Vj, it is judged that circuit is operated in CCM or DCM, works as VjWhen=1, circuit is operated in CCM, works as VjWhen=0, circuit works
At DCM；Wherein K1、K2、K3、K4、K5、K6And K7It is and signal Vn、VsAnd the inductive current of described power factor correcting converter
The coefficient that ripple is relevant.First pulse width modulator DP1 for produce CCM time changer TD switching tube turn-on and turn-off control time
Sequence VP1；Second pulse width modulator DP2 is control sequential V of changer TD switching tube turn-on and turn-off in time producing DCMP2；Select
Device CH is for according to selecting signal VjSelect to control sequential VP1Or VP2, and produce control signal VP。
Above-mentioned K1、K2、K3、K4、K5、K6And K7Expression as follows: Wherein TsFor
Switch periods, m1And m2It is respectively the rate of rise and the descending slope of inductive current change, it may be assumed that
Fig. 2 illustrates, what the pfc converter average electric current of this example controlled realizes device, by changer TD and control device group
Become.
Its work process of the device of this example and principle be:
When each switch periods starts, the output voltage of detection changer TD rectifier bridge and output electric current and changer
The output voltage of TD, obtains signal Vs、InAnd Vn；By VsV is obtained through amplifierc, by VnAnd VrefError is obtained through compensator
Signal Ve, by VcAnd VeSignal I is obtained through multiplierc；By In、Vs、IcAnd VnSend into the first duty cycle generator and obtain signal
dx1And dx2, by dx1And dx2Send into the first pulse width modulator and obtain signal VP1；By In、Vs、IcAnd VnSend into the second dutycycle to generate
Device obtains signal dy1And dy2, by dy1And dy2Send into the second pulse width modulator and obtain signal VP2；By In、Vs、IcAnd VnSend into and judge
Device obtains signal Vj；By VP1、VP2And VjSend into selector and obtain signal VP, control leading of power factor correcting converter switching tube
Lead to and turn off.
Fig. 3 a is dutycycle dx1And dx2Generating schematic diagram, the operation principle of the first duty cycle generator DG1 is: Mei Gekai
When the pass cycle starts, calculate dutycycle dx1And dx2, design conditions are: the 1. inductor current value etc. at the end of current switch period
In Ic, 2. two sections of dutycycles are equal.It is calculated dutycycle dx1=dx2=0.5 [K1+K2(Ic-In)], wherein K1And K2It it is two
With signal Vn、VsAnd the coefficient that inductive current ripple is relevant.Fig. 3 b is dutycycle dy1And dy2Generate schematic diagram, the second dutycycle
The operation principle of maker DG2 is: when each switch periods starts, and calculates dutycycle dy1And dy2, design conditions are: the most current
Inductor current value at the end of switch periods is equal to Ic, 2. the meansigma methods of current switch period internal inductance electric current is equal to Ic.Calculate
To dutycycle dy1=K3In+(K4In 2+K5Ic 2+K6Ic)1/2,dy2=K7Ic, wherein K3、K4、K5、K6And K7It is and signal Vn、VsAnd
The coefficient that inductive current ripple is relevant.
The changer TD of this example is Boost pfc converter.
With PSIM simulation software, the method for this example being carried out time-domain-simulation analysis, result is as follows.
Fig. 4 is the input voltage V during embodiment of the present invention one pfc converter steady operationinWith input current IinTime domain
Simulation waveform figure.Now input current waveform is close to sinusoidal, and does not has phase contrast with input voltage, it is achieved that PFC
Function.Simulated conditions: input voltage VinBe amplitude be 200V, frequency be the alternating voltage of 50Hz, reference voltage Vref=4V
(corresponding output voltage 400V), inductance L=200 μ H, electric capacity C=470 μ F (its equivalent series resistance is 1m Ω), load resistance R
=100 Ω, switch periods Ts=20 μ s, compensator parameter is KP=0.1, KI=5.
Fig. 5 is that the pfc converter being respectively adopted the present invention and tradition Average Current Control is bent with PF value during load change
Line chart.Simulated conditions is identical with Fig. 4, and the excursion of load resistance is 50 Ω～500 Ω.When load resistance is bigger, two kinds
Under control method, pfc converter has similar PF value.When load resistance is more than 200 Ω, along with the increase of load resistance, two
Plant the PF value of pfc converter under control method all to reduce；When load resistance is less than 200 Ω, along with the reduction of load resistance, pass
The PF value of system Average Current Control pfc converter reduces, and the PF value of the present invention increases.In resistance variation range, this
The PF value of invention is above 99%.Therefore the pfc converter using the present invention the most all has good PF value.
Fig. 6 is that the pfc converter being respectively adopted the present invention and tradition Average Current Control is when changing with input voltage amplitude
PF value curve chart.Simulated conditions is identical with Fig. 4, and input voltage amplitude excursion is 180V～250V.Along with input voltage
During the reduction of amplitude, two kinds of PF values controlling lower pfc converters all reduce, but to be above tradition the most electric for the PF value of the present invention
The PF value of flow control pfc converter, and it is maintained at more than 99.5%.Therefore the present invention has good under different input voltage amplitudes
Power factor emendation function.
Fig. 7 a and Fig. 7 b is respectively the present invention, the pfc converter of tradition Average Current Control is jumped by 100 Ω at load resistance
Changing to output voltage transient state time-domain-simulation oscillogram during 400 Ω, changer simulated conditions is identical with Fig. 4.Now, changer work
Pattern is changed to DCM by CCM.Fig. 7 understands, and after load change, two kinds of control methods all can make voltage stabilization at 400V, and tradition is flat
All electric current control pfc converters return to 400V through the time of 0.22s；Use the pfc converter of the present invention through 0.1s's
Time returns to 400V, and the output voltage peak value fluctuation of the present invention is less than tradition Average Current Control, it can thus be appreciated that this
Bright have faster load transient response speed.
Fig. 8 a and Fig. 8 b is respectively the present invention, the pfc converter of tradition Average Current Control is jumped by 500 Ω at load resistance
Changing to output voltage transient state time-domain-simulation oscillogram during 400 Ω, changer simulated conditions is identical with Fig. 4.Now, the equal work of changer
Make at DCM.As shown in Figure 8, the regulating time of the present invention is 0.8s, and the regulating time of tradition Average Current Control is 1.3s.This
The output voltage valley fluctuation of invention is about 4V, and the output voltage valley fluctuation of tradition Average Current Control is about 7V.Contrast can
Knowing, when pfc converter is operated in DCM, the present invention has more preferable load transient performance.
Fig. 9 is that the pfc converter being respectively adopted the present invention and tradition Average Current Control is bent with efficiency during load change
Line chart.Changer simulated conditions is identical with Fig. 4, and the excursion of load resistance is 50 Ω～500 Ω.Increasing along with load resistance
Adding, two kinds of efficiency controlling lower pfc converter all reduce.In whole load change, compared to tradition Average Current Control, this
Invention has higher efficiency, and efficiency is above 90%.It follows that use the pfc converter of the present invention to have higher
Work efficiency.
Embodiment two
As shown in Figure 10, this example is essentially identical with embodiment one, is a difference in that: the changer TD that this example controls is
Buck-boost pfc converter.
The present invention in addition to the pfc converter that can be used in above example it can also be used to flyback pfc converter, half-bridge PFC
In the pfc converter topologys such as changer, full-bridge pfc converter.
Claims (3)
1. a power factor correcting converter average current control method, it is characterised in that: when each switch periods starts
Carve, the output voltage of detection rectifier bridge and output electric current and the output voltage of described power factor correcting converter, respectively
To signal Vs、InAnd Vn；By VsSend into amplifier and obtain signal Vc, by VnWith voltage reference value VrefSend into compensator and obtain signal
Ve, by VcAnd VeSend into multiplier and obtain signal Ic；By In、Vs、IcAnd VnSend into the first duty cycle generator and obtain signal dx1With
dx2, by dx1And dx2Send into the first pulse width modulator and obtain signal VP1；By In、Vs、IcAnd VnSend into the second duty cycle generator to obtain
To signal dy1And dy2, by dy1And dy2Send into the second pulse width modulator and obtain signal VP2；By In、Vs、IcAnd VnFeeding diagnosis apparatus obtains
To signal Vj；By VP1、VP2And VjSend into selector and obtain signal VP, in order to control described power factor correcting converter switching tube
Conducting and shutoff.
Power factor correcting converter average current control method the most according to claim 1, it is characterised in that: described general
In、Vs、IcAnd VnSend into the first duty cycle generator and obtain signal dx1And dx2Method be, at the end of current switch period
Inductor current value equal to IcAnd dx1Equal to dx2, the first duty cycle generator calculates dx1And dx2, dx1=dx2=0.5 [K1+K2
(Ic-In)]；Described by In、Vs、IcAnd VnSend into the second duty cycle generator and obtain signal dy1And dy2Method be, according to currently
Inductor current value at the end of switch periods is equal to IcAnd the meansigma methods of current switch period internal inductance electric current is equal to Ic, second
Duty cycle generator calculates dy1And dy2, dy1=K3In+(K4In 2+K5Ic 2+K6Ic)1/2,dy2=K7Ic；Wherein K1、K2、K3、K4、K5、
K6And K7It is and signal Vn、VsAnd the coefficient that the inductive current ripple of described power factor correcting converter is relevant.
3. a power factor correcting converter average current control device, it is characterised in that: include current detection circuit IS,
One voltage detecting circuit VS1, the second voltage detecting circuit VS2, compensator EC, amplifier GA, multiplier MUL, the first dutycycle
Maker DG1, the second duty cycle generator DG2, the first pulse width modulator DP1, the second pulse width modulator DP2, diagnosis apparatus JU and
Selector CH；First voltage detecting circuit VS1, amplifier GA, multiplier MUL are sequentially connected；Second voltage detecting circuit VS2,
Compensator EC, multiplier MUL are sequentially connected；Current detection circuit IS and the first duty cycle generator DG1, diagnosis apparatus JU, second
Duty cycle generator DG2 is respectively connected with；First voltage detecting circuit VS1 and the first duty cycle generator DG1, diagnosis apparatus JU,
Two duty cycle generator DG2 are respectively connected with；Second voltage detecting circuit VS2 and the first duty cycle generator DG1, diagnosis apparatus JU,
Second duty cycle generator DG2 is respectively connected with；Multiplier MUL and the first duty cycle generator DG1, diagnosis apparatus JU, the second duty
It is respectively connected with than maker DG2；First duty cycle generator DG1, the first pulse width modulator DP1, selector CH are sequentially connected；Sentence
Disconnected device JU is connected with selector CH；Second duty cycle generator DG2, the second pulse width modulator DP2, selector CH are sequentially connected.
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|---|---|---|---|---|
| CN109921625A (en) * | 2019-03-25 | 2019-06-21 | 西南交通大学 | A kind of pfc converter pulse frequency modulated mean value current control method and device |
| CN109921625B (en) * | 2019-03-25 | 2023-09-08 | 西南交通大学 | PFC converter pulse frequency modulation mean current control method and device |
| CN113315391A (en) * | 2021-04-29 | 2021-08-27 | 武汉华海通用电气有限公司 | Digital PFC circuit |
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| CN106253657B (en) | 2018-07-31 |
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