CN102624206B - Self-adaptive continuous-flow control method and device for pseudo continuous conductive mode switch converter - Google Patents
Self-adaptive continuous-flow control method and device for pseudo continuous conductive mode switch converter Download PDFInfo
- Publication number
- CN102624206B CN102624206B CN201210115359.4A CN201210115359A CN102624206B CN 102624206 B CN102624206 B CN 102624206B CN 201210115359 A CN201210115359 A CN 201210115359A CN 102624206 B CN102624206 B CN 102624206B
- Authority
- CN
- China
- Prior art keywords
- signal
- current
- circuit
- pccm
- multiplier
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
Images
Landscapes
- Rectifiers (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a self-adaptive continuous-flow control method and a device ACD for a pseudo continuous conductive mode (PCCM) switch converter. A self-adaptive reference current is synthesized by calculating inductance current and outputted current of the PCCM switch converter, the self-adaptive reference current is compared with an inductance current so as to control the connection and disconnection of a continuous-flow switch tube of the PCCM switch converter. The self-adaptive continuous-flow control method and the device can be used for controlling different continuous-flow switch tubes of the PCCM switch converters with different topological structures and can be matched with any control method and any device of a main switch pipe of the PCCM switch converter. The self-adaptive continuous-flow control method and the device have advantages that no compensation network is needed, simplicity in control can be realized, the instantaneous response speed is fast, and the efficiency is high.
Description
Technical field
The present invention relates to a kind of control method and device thereof of switch converters, be specially a kind of pseudo-continuous conduction mode switch converters self adaptation afterflow control method and realize the device ACD of described self adaptation afterflow control method.
Background technology
Along with the development of power electronic device technology and electric electronic current change technology, as the switch power technology of power electronics key areas, become the focus of application and research.Switch power technology uses switch converters to carry out transformation of electrical energy, meets various electricity consumption requirements.Switching Power Supply has the outstanding advantages such as volume is little, lightweight, efficiency is high, power density is large, is widely used in the fields such as computer, communication apparatus, electron detection device, battery charger.
Switching Power Supply mainly consists of switch converters and controller two parts.Switch converters is called again power main circuit, mainly contains Buck(step-down), Boost(boosts), Buck-Boost(buck), the various topological structures such as normal shock, flyback, half-bridge, full-bridge.Traditional switch converters is usually operated at continuous current mode conduction mode (CCM) and interrupted conduction mode (DCM).CCM switch converters can transmit more Power supply load, in, large-power occasions is widely applied.But because it adopts larger inductance value, have that mapping is poor, inductance volume is large, high in cost of production shortcoming.The inductive current of DCM switch converters remains for some time zero in each switch periods, and the average power that inductance stores and transmits is limited, is applicable to small-power occasion.In sum, CCM and DCM switch converters are all only applicable to specific load or power bracket.Pseudo-continuous conduction mode (PCCM) switch converters has been taken into account the advantage of CCM and DCM switch converters, is applicable to wide load or broad power band.
Controller is used for the operating state of monitoring switch converter, and produces control wave control switch pipe, regulates the energy of supply load to stablize output.The control method of switch converters mainly contains the control methods such as voltage-type, current mode, pulse train.In recent years, increasing application scenario requires its power supply to have transient response speed fast, while switching between standby, dormancy, normal operation as some microprocessors, transient current speed is up to 130A/ us, and this just requires its power supply to have fast transient response speed to meet the demand of load.Traditional voltage-type control implementation is simple, but its dynamic responding speed is slower, has been difficult to meet this demand of load.Novel pulse sequence control method is by controller generation high-energy control impuls or low-yield control impuls, switching tube to be controlled, and has good capability of fast response.Its weak point is: adopt the time of afterflow of fixing reference current control PCCM switch converters continued flow switch pipe longer, transducer effciency is poor, and when load or power change on a large scale, control system can lose stable or cisco unity malfunction.
Summary of the invention
The object of this invention is to provide a kind of PCCM switch converters self adaptation afterflow control method, make it to have transient response speed and higher transducer effciency fast simultaneously, be applicable to the PCCM switch converters of various topological structures.
The present invention is achieved in that provides a kind of PCCM switch converters self adaptation afterflow control method, it is characterized in that:
A, detect the inductive current of pseudo-continuous conduction mode PCCM switch converters, select a sampling pulse signal, inductive current is sampled/kept, obtain inductive current value, and be multiplied by variable coefficient, obtain first signal;
The output current of b, detection PCCM switch converters, and be multiplied by another variable coefficient, obtain secondary signal; First signal and secondary signal are sent into signal computing circuit simultaneously synthesizes, its synthetic result is as adaptive reference electric current, adaptive reference electric current and inductive current are compared, with this, control conducting and the shutoff of PCCM switch converters continued flow switch pipe.
According to the pseudo-continuous conduction mode PCCM of one of the present invention switch converters self adaptation afterflow control method, it is characterized in that: adaptive reference electric current carries out signal operation by first signal and secondary signal and synthesizes.
The present invention provides a kind of device of the control method that realizes above-mentioned PCCM switch converters simultaneously, it is characterized in that: first signal modulate circuit FSC, secondary signal modulate circuit SSC, signal computing circuit SO, pulse signal producer PG and drive circuit DR, consist of; Described first signal modulate circuit FSC is connected with signal computing circuit SO and pulse signal producer PG, secondary signal modulate circuit SSC is connected with signal computing circuit SO, signal computing circuit SO is connected with pulse signal producer PG, and pulse signal producer PG is connected with drive circuit DR.
According to device ACD of the present invention, it is characterized in that, described first signal modulate circuit FSC is comprised of current detection circuit CS1, sampling pulse generator SP, sampling/retainer SH, variable gain generator VG1 and multiplier MU1; Current detection circuit CS1, sampling/retainer SH, multiplier MU1 are connected successively; Sampling pulse generator SP is connected with sampling/retainer SH; Variable gain generator VG1 is connected with multiplier MU1.
According to device ACD of the present invention, it is characterized in that, described secondary signal modulate circuit SSC is comprised of current detection circuit CS2, variable gain generator VG2 and multiplier MU2; Current detection circuit CS2 is connected with multiplier MU2; Variable gain generator VG2 is connected with multiplier MU2.
The invention has the advantages that:
One, compared with the control method of existing PCCM switch converters, PCCM switch converters output voltage ripple of the present invention is little, and inductive current ripple is little, thereby has good steady-state behaviour.
Two, compared with the control method of existing PCCM switch converters, PCCM switch converters of the present invention is when load changes, the variation of output current changes the size of adaptive reference electric current immediately, thereby dynamically control afterflow value size and the time of afterflow length of the continued flow switch pipe of PCCM switch converters, when guaranteeing PCCM switch converters stability, improved mapping and the efficiency of PCCM switch converters.
Three, compared with the control method of existing PCCM switch converters, PCCM switch converters of the present invention is when input voltage changes, inductive current changes immediately, changed the size of adaptive reference electric current simultaneously, thereby dynamically control afterflow value size and the time of afterflow length of the continued flow switch pipe of PCCM switch converters, when guaranteeing PCCM switch converters stability, improved mapping and the efficiency of PCCM switch converters.
Four, controller is directly compared with adaptive reference electric current with inductive current, without compensating network, has simplified the design of control loop, controls simply, has strengthened the stability of a system and dynamic response capability.
Accompanying drawing explanation
Fig. 1 is the signal flow graph of the embodiment of the present invention one method.
Fig. 2 is the signal flow graph of the first signal modulate circuit of the embodiment of the present invention one.
Fig. 3 is the signal flow graph of the secondary signal modulate circuit of the embodiment of the present invention one.
Fig. 4 is the circuit structure block diagram of the embodiment of the present invention one.
Fig. 5 is in the embodiment of the present invention one, between inductive current, inductive current valley and sampling pulse signal, is related to schematic diagram.
Fig. 6 a is the time-domain-simulation oscillogram of the embodiment of the present invention one a certain period converter TD inductive current under limit.
Fig. 6 b is and the time-domain-simulation oscillogram of Fig. 6 a converter TD of same period output voltage.
The simulation waveform figure of Fig. 7 a converter TD output voltage that is embodiment mono-when load variations (load on 30ms moment by 1.8A transition to 3.6A).
Fig. 7 b is the continued flow switch pipe S2 that adopts existing pulse train control change device TD, the simulation waveform figure of output voltage when same load variations.
The simulation waveform figure of Fig. 8 a converter TD inductive current that is embodiment mono-when load variations (load on 30ms moment by 1.8A transition to 3.6A).
Fig. 8 b is the continued flow switch pipe S that adopts existing pulse train control change device TD
2, the simulation waveform figure of inductive current when same load variations.
Fig. 9 is the circuit structure block diagram of the embodiment of the present invention two.
Figure 10 is in the embodiment of the present invention two, between inductive current, inductive current peak and sampling pulse signal, is related to schematic diagram.
Figure 11 is the circuit structure block diagram of the embodiment of the present invention three.
In figure: 101, first signal modulate circuit FSC, 102, secondary signal modulate circuit SSC, 103, signal computing circuit SO, 104, pulse signal producer PG, 105, drive circuit DR, 201, current detection circuit CS1,202, sampling pulse generator SP, 203, sampling/retainer SH, 204, variable gain generator VG1,205, multiplier MU1,301, current detection circuit CS2,302, variable gain generator VG2,303, multiplier MU2.
Embodiment
Below in conjunction with the drawings and specific embodiments, the present invention is further detailed explanation.The PCCM switch converters continued flow switch pipe S the present invention relates to
2control method and device ACD, can with PCCM switch converters main switch S
1any control method and device PCD combine.In diagram shown specific embodiments be only as example with and will below describe it in detail, should not serve as restriction.
Embodiment mono-
As Fig. 1 illustrates, Fig. 1 is the signal flow graph of the embodiment of the present invention one method, be specially a kind of PCCM switch converters TD self adaptation afterflow control method and device ACD thereof, its ACD device is mainly comprised of first signal modulate circuit FSC101, secondary signal modulate circuit SSC102, signal computing circuit SO103, pulse signal producer PG104 and drive circuit DR105.First signal modulate circuit FSC101 is used for obtaining inductive current information, secondary signal modulate circuit SSC102 is used for obtaining output current information, inductive current information and output current information are sent into signal computing circuit SO103 simultaneously and synthesize, obtain adaptive reference electric current.In pulse signal producer PG104, adaptive reference electric current and inductive current are compared, according to comparative result, produce corresponding control wave, via drive circuit DR105, control conducting and the shutoff of the continued flow switch pipe of PCCM switch converters TD.
As shown in Figure 2, this routine first signal modulate circuit FSC is comprised of current detection circuit CS1201, sampling pulse generator SP202, sampling/retainer SH203, variable gain generator VG1204 and multiplier MU1205.Current detection circuit CS1201, sampling/retainer SH203, multiplier MU1205 are connected successively; Sampling pulse generator SP202 is connected with sampling/retainer SH203; Variable gain generator VG1204 is connected with multiplier MU1205.
As Fig. 3 illustrates, this routine secondary signal modulate circuit SSC is comprised of current detection circuit CS2301, variable gain generator VG2302 and multiplier MU2303.Current detection circuit CS2301 is connected with multiplier MU2303; Variable gain generator VG2302 is connected with multiplier MU2303.
This example adopts the device of Fig. 4, can realize easily and quickly above-mentioned control method.As shown in Figure 4, the device of the control method of this routine PCCM switch converters, by converter TD, main switch S
1control device PCD and continued flow switch pipe S
2control device ACD composition.Control device ACD comprises first signal modulate circuit FSC101, secondary signal modulate circuit SSC102, signal computing circuit SO103, pulse signal producer PG104 and drive circuit DR105.First signal modulate circuit FSC101, signal computing circuit SO103, pulse signal producer PG104, drive circuit DR105 are connected successively; First signal modulate circuit FSC101 is connected with pulse signal producer PG104; Secondary signal modulate circuit SSC102 is connected with signal computing circuit SO103.
Its course of work of the device of this example and principle are:
Control device PCD adopts the course of work and the principle of pulse train control to be: as shown in Figure 4, arbitrary switch periods zero hour, PCD detects the output voltage VO of converter TD, and compare with reference voltage V ref, its result is for selecting the effective control impuls in this switch periods, thereby realization is to main switch S
1control.Effective selection way of its control impuls is: if VO is less than Vref, selecting duty ratio is the high energy pulse control main switch S of DH
1; Otherwise selecting duty ratio is the low-yield pulse control main switch S of DL
1.
Control device ACD adopts the course of work and the principle of self adaptation afterflow control to be: first signal modulate circuit FSC101 obtains inductive current information, secondary signal modulate circuit SSC102 obtains output current information, inductive current information and output current information are sent into signal computing circuit SO103 simultaneously, and to carry out add operation synthetic, obtains adaptive reference electric current.In pulse signal producer PG104, adaptive reference electric current and inductive current are compared, according to comparative result, produce corresponding control wave, via drive circuit DR105, control change device TD continued flow switch pipe S
2conducting and shutoff.
In this example, the course of work of its first signal modulate circuit FSC101 is: current detection circuit CS1201 obtains inductive current I from converter TD
l, sampling pulse generator SP202 produces a sampling pulse signal CLK; By inductive current I
lsend into sampling/retainer SH203 with sampling pulse signal CLK, obtain the valley I of inductive current
lV, wherein inductive current I
l, sampling pulse signal CLK and inductive current valley I
lVbe related to that schematic diagram as shown in Figure 5; Variable gain generator VG1204 produces gain coefficient K
1, and with inductive current valley I
lVsend into together multiplier MU1205, obtain first signal K
1i
lV, as an input of signal computing circuit SO103.
In this example, the course of work of its secondary signal modulate circuit SSC102 is: current detection circuit CS2301 obtains output current I from converter TD
o; Variable gain generator VG2302 produces gain coefficient K
2, and with output current I
osend into together multiplier MU2303, obtain secondary signal K
2i
o, as another input of signal computing circuit SO103.
In this example, adaptive reference electric current I
dcsynthetic method be: signal computing circuit SO103 is to first signal K
1i
lVwith secondary signal K
2i
ocarry out add operation synthetic, obtain I
dc=K
1i
lV+ K
2i
o.
Current detection circuit CS1201 obtains inductive current I from converter TD
l, sampling pulse generator SP202 produces a sampling pulse signal CLK
2; By inductive current I
lwith sampling pulse signal CLK
2send into sampling/retainer SH203, obtain the arbitrary value I of inductive current except valley
2, variable gain generator VG1204 produces gain coefficient K
3, and with inductive current the arbitrary value I except valley
2send into together multiplier MU1205, obtain first signal K
3i
2, as an input of signal computing circuit SO103.
Now the course of work of its secondary signal modulate circuit SSC102 is: current detection circuit CS2301 obtains output current I from converter TD
o; Variable gain generator VG2302 produces gain coefficient K
4, and with output current I
osend into together multiplier MU2303, obtain secondary signal K
4i
o, as another input of signal computing circuit SO103.
Now, adaptive reference electric current I
dcsynthetic method be: signal computing circuit SO103 is to first signal K
3i
2with secondary signal K
4i
ocarry out computing synthetic, obtain I
dc=K
3i
2+ K
4i
o.
In this example, continued flow switch pipe S
2control impuls Ps2 in pulse signal producer PG, produce, concrete producing method is: when each switch periods starts, main switch S
1conducting, diode turn-off, inductive current I
lstart to rise, control impuls Ps2 is low level; Main switch S
1after conducting set time DHT or DLT, turn-off, diode current flow simultaneously, inductive current IL starts to decline immediately.Work as I
ldrop to adaptive reference electric current I
dctime, pulse signal producer PG makes control impuls Ps2 become high level from low level, continued flow switch pipe S
2conducting, diode turn-off, and inductive current is by continued flow switch pipe S
2afterflow, until current switch periods finishes.
This routine converter TD is PCCM Buck converter.
This routine method is carried out to time-domain-simulation analysis with PSIM software, result is as follows.
Fig. 6 a and Fig. 6 b are respectively the inductive current I that emulation obtains
land output voltage V
owaveform.
Fig. 6 simulated conditions is as follows: input voltage vin=50V, output voltage reference value Vref=18V, its equivalent series resistance of inductance L=800uH, capacitor C=2000uF(are 10m Ω), load resistance R=10 Ω, switch periods T=50 μ s; At converter TD continued flow switch pipe S
2control device ACD in, sampling pulse generator SP202 and sampling/retainer SH203 obtain the valley of inductive current, the gain coefficient K1=0.5 of variable gain generator VG1204, the gain coefficient K2=0.5 of variable gain generator VG2205, signal computing circuit SO103 is used add operation; At converter TD main switch S
1control device PCD in, adopt pulse train control, the wherein duty ratio DL=0.18 of the duty ratio DH=0.48 of high energy pulse, low-yield pulse.
As can be seen from Figure 6, a cycle period of 3 switch periods composition, its combining form is: 1 is high 2 low.Containing in 1 switch periods of high energy pulse, the ON time of continued flow switch pipe is less; Containing in 2 switch periods of low-yield pulse, the ON time of continued flow switch pipe is longer, but unequal.
The simulation waveform figure of Fig. 7 a converter output voltage that is embodiment mono-when load variations (load on 30ms moment by 1.8A transition to 3.6A).Fig. 7 b is the continued flow switch pipe S that adopts existing pulse train control change device
2.Fig. 7 simulated conditions is identical with Fig. 6.The simulation waveform figure of output voltage when same load variations.As seen from Figure 7, while adopting identical control method in device PCD, continued flow switch pipe S
2adopt the PCCM switch converters of pulse train control after disturbance occurs, after about 1.4ms, just can enter new stable state, output voltage peak-to-peak value fluctuation 237mV; And under same condition, adopt the inventive method to continued flow switch pipe S
2while controlling, PCCM switch converters can enter rapidly new stable state, and the adjustment time is 0.6ms, output voltage peak-to-peak value fluctuation 207mV.Therefore the transient response speed of the PCCM switch converters of the inventive method control is faster.
The simulation waveform figure of Fig. 8 a converter inductive current that is embodiment mono-when load variations (load on 30ms moment by 1.8A transition to 3.6A).Fig. 8 simulated conditions is identical with Fig. 7.Fig. 8 b is the continued flow switch pipe S that adopts existing pulse train control change device
2, the simulation waveform figure of inductive current when same load variations.As seen from Figure 8, while adopting identical control method in device PCD, continued flow switch pipe S
2adopt the PCCM switch converters of pulse train control after disturbance occurs, in adjustment process the peak value of inductive current up to 6A, reenter stable state after inductive current afterflow value be all greater than 4A, and time of afterflow is fixed; And under same condition, adopt the inventive method to continued flow switch pipe S
2while controlling, the highest 5.5A that is about of the peak value of inductive current in adjustment process, reenters after stable state inductive current afterflow value substantially below 4A, and time of afterflow dynamic change.Because inductive current afterflow value is larger, time of afterflow is longer, will cause more losses, therefore the efficiency of the PCCM switch converters of the inventive method control is higher.
Embodiment bis-
As shown in Figure 9, Figure 10, this example is basic identical with embodiment mono-, and difference is: the converter TD that this example is controlled is PCCM Boost converter, as shown in Figure 9; That this routine sampling pulse generator SP202 and sampling/retainer SH203 obtain is inductive current peak I
lP, as shown in figure 10.
Embodiment tri-
As shown in figure 11, this example is basic identical with embodiment mono-, and difference is: the converter TD that this example is controlled is PCCM Buck-Boost converter, as shown in figure 11.
The inventive method can realize with analogue device or digital device easily; Except the PCCM switch converters can be used in above embodiment, also can be used for the multiple circuit topologies such as PCCM forward converter, PCCM anti exciting converter, PCCM half-bridge converter, PCCM full-bridge converter.
Claims (4)
1. a pseudo-continuous conduction mode switch converters self adaptation afterflow control method, is characterized in that:
A, detect the inductive current of pseudo-continuous conduction mode PCCM switch converters, select a sampling pulse signal, inductive current is sampled/kept, obtain inductive current value, and be multiplied by variable coefficient, obtain first signal; Be specially: current detection circuit CS1(201) from converter TD, obtain inductive current I
l, sampling pulse generator SP(202) and a sampling pulse signal CLK of generation
2; By inductive current I
lwith sampling pulse signal CLK
2send into sampling/retainer SH(203), obtain the arbitrary value I of inductive current except valley
2, variable gain generator VG1(204) and generation gain coefficient K
3, and with inductive current the arbitrary value I except valley
2send into together multiplier MU1(205), obtain first signal K
3i
2;
The output current of b, detection PCCM switch converters, and be multiplied by another variable coefficient, obtain secondary signal;
Be specially: current detection circuit CS2(301) from converter TD, obtain output current I
o; Variable gain generator VG2(302) generation gain coefficient K
4, and with output current I
osend into together multiplier MU2(303), obtain secondary signal K
4i
o;
First signal and secondary signal are sent into signal computing circuit simultaneously, and to carry out add operation synthetic, its synthetic result is as adaptive reference electric current, adaptive reference electric current and inductive current are compared, with this, control conducting and the shutoff of PCCM switch converters continued flow switch pipe, when inductive current drops to adaptive reference electric current, the conducting of continued flow switch pipe.
2. a device ACD who realizes pseudo-continuous conduction mode switch converters self adaptation afterflow control method described in claim 1, is characterized in that: by first signal modulate circuit FSC(101), secondary signal modulate circuit SSC(102), signal computing circuit SO(103), pulse signal producer PG(104) and drive circuit DR(105) form; Described first signal modulate circuit FSC(101) with signal computing circuit SO(103) and pulse signal producer PG(104) be connected, secondary signal modulate circuit SSC(102) with signal computing circuit SO(103) be connected, signal computing circuit SO(103) with pulse signal producer PG(104) be connected pulse signal producer PG(104) and with drive circuit DR(105) be connected.
3. device ACD according to claim 2, it is characterized in that described first signal modulate circuit FSC(101) by current detection circuit CS1(201), sampling pulse generator SP(202), sampling/retainer SH(203), variable gain generator VG1(204) and multiplier MU1(205) form; Current detection circuit CS1(201), sampling/retainer SH(203), multiplier MU1(205) be successively connected; Sampling pulse generator SP(202) with sampling/retainer SH(203) be connected; Variable gain generator VG1(204) with multiplier MU1(205) be connected.
4. device ACD according to claim 2, is characterized in that, described secondary signal modulate circuit SSC(102) by current detection circuit CS2(301), variable gain generator VG2(302) and multiplier MU2(303) form; Current detection circuit CS2(301) with multiplier MU2(303) be connected; Variable gain generator VG2(302) with multiplier MU2(303) be connected.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201210115359.4A CN102624206B (en) | 2012-04-19 | 2012-04-19 | Self-adaptive continuous-flow control method and device for pseudo continuous conductive mode switch converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201210115359.4A CN102624206B (en) | 2012-04-19 | 2012-04-19 | Self-adaptive continuous-flow control method and device for pseudo continuous conductive mode switch converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN102624206A CN102624206A (en) | 2012-08-01 |
| CN102624206B true CN102624206B (en) | 2014-05-07 |
Family
ID=46563930
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201210115359.4A Expired - Fee Related CN102624206B (en) | 2012-04-19 | 2012-04-19 | Self-adaptive continuous-flow control method and device for pseudo continuous conductive mode switch converter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN102624206B (en) |
Families Citing this family (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103441668A (en) * | 2013-08-26 | 2013-12-11 | 华南理工大学 | High-gain boost DC-DC converter allowing pseudo continuous work |
| EP3092708B1 (en) * | 2014-01-07 | 2018-09-12 | Chaoyang Semiconductor Jiangyin Technology Co., Ltd. | A switched power stage and a method for controlling the latter |
| CN106230260A (en) * | 2016-09-27 | 2016-12-14 | 武汉大学 | A kind of pseudo-continuous conduction mode Buck changer gradient reference current control system and method |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101505098A (en) * | 2008-12-31 | 2009-08-12 | 西南交通大学 | Multi-stage pulse sequence control method of pseudo-continuous working mode and apparatus thereof |
| CN101552547A (en) * | 2009-01-14 | 2009-10-07 | 西南交通大学 | Pseudo-continuous work mode switch power supply power factor correcting method and device thereof |
| CN101557168A (en) * | 2009-02-25 | 2009-10-14 | 西南交通大学 | Multi-frequency control method of quasicontinuous working model switch power supply and device thereof |
| CN101777832A (en) * | 2010-01-19 | 2010-07-14 | 西南交通大学 | Single-loop pulse regulating and controlling method and device of pseudo continuous mode switch power supply |
-
2012
- 2012-04-19 CN CN201210115359.4A patent/CN102624206B/en not_active Expired - Fee Related
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101505098A (en) * | 2008-12-31 | 2009-08-12 | 西南交通大学 | Multi-stage pulse sequence control method of pseudo-continuous working mode and apparatus thereof |
| CN101552547A (en) * | 2009-01-14 | 2009-10-07 | 西南交通大学 | Pseudo-continuous work mode switch power supply power factor correcting method and device thereof |
| CN101557168A (en) * | 2009-02-25 | 2009-10-14 | 西南交通大学 | Multi-frequency control method of quasicontinuous working model switch power supply and device thereof |
| CN101777832A (en) * | 2010-01-19 | 2010-07-14 | 西南交通大学 | Single-loop pulse regulating and controlling method and device of pseudo continuous mode switch power supply |
Also Published As
| Publication number | Publication date |
|---|---|
| CN102624206A (en) | 2012-08-01 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| Luo et al. | Flyboost power factor correction cell and a new family of single-stage AC/DC converters | |
| Li et al. | A novel quadratic boost converter with low inductor currents | |
| CN103715886A (en) | Four-switch buck/boost mode converter control method and control circuit | |
| CN103066811B (en) | Switch converter double-edge constant breakover time modulation voltage type control method | |
| Wang | Parallel DC/DC converters system with a novel primary droop current sharing control | |
| CN105450028A (en) | Converter and control method therefor | |
| CN112398342B (en) | Frequency conversion control device and method for combined single-inductor dual-output switch converter | |
| CN106300964B (en) | Independent charge and discharge sequential single-inductance double-output switch converters method for controlling frequency conversion and its device | |
| CN103166489A (en) | Control circuit for three-phase high power factor rectifier | |
| CN106253662A (en) | Switch converters frequency V2C dynamic afterflow control method surely and control device thereof | |
| CN102624206B (en) | Self-adaptive continuous-flow control method and device for pseudo continuous conductive mode switch converter | |
| CN202586724U (en) | Self-adaptive continuous-flow control device for pseudo continuous conductive mode switch converter | |
| CA2709100A1 (en) | Power converter | |
| CN100594661C (en) | Standard average output current control scheme for switch power convertor | |
| CN203151389U (en) | Control circuit of three-phase high power factor rectifier | |
| CN209767386U (en) | Four-port converter with bipolar output | |
| CN107742972B (en) | Continuous conduction mode double hysteresis pulse sequence control method and device thereof | |
| CN103916020A (en) | Switching power supply and control circuit thereof | |
| Zhu et al. | Current controlled with valley voltage detection three-port converter with current-pulsed load | |
| Ramaprabha et al. | Power quality improvement in single phase AC to DC zeta converter | |
| CN106253657B (en) | Power factor correcting converter mean value current control method and its device | |
| Vazquez et al. | Master-slave technique with direct variable frequency control for interleaved bidirectional boost converter | |
| CN107769532A (en) | Single-inductance double-output switch converters capacitance current ripple control method and device | |
| Tang et al. | A 2MHz Constant-Frequency AOT V 2 Buck Converter with Adaptive Dead Time Control for Data Centers | |
| Pan et al. | A Continuous-Output-Current Buck-Boost Converter Without Right-Half-Plane-Zero (RHPZ) |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20140507 Termination date: 20180419 |
|
| CF01 | Termination of patent right due to non-payment of annual fee |