CN103916020A - Switching power supply and control circuit thereof - Google Patents
Switching power supply and control circuit thereof Download PDFInfo
- Publication number
- CN103916020A CN103916020A CN201410164522.5A CN201410164522A CN103916020A CN 103916020 A CN103916020 A CN 103916020A CN 201410164522 A CN201410164522 A CN 201410164522A CN 103916020 A CN103916020 A CN 103916020A
- Authority
- CN
- China
- Prior art keywords
- voltage
- power supply
- switching power
- magnitude
- control
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4266—Arrangements for improving power factor of AC input using passive elements
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses a switching power supply and a control circuit of the switching power supply. The control circuit of the switching power supply comprises a peak current detection end, a feedback end, a driving end, a first voltage comparator and a pulse width modulation unit. The control circuit of the switching power supply further comprises a control end and a reference voltage adjusting unit, wherein the control end is suitable for receiving control voltage, the reference voltage adjusting unit is suitable for generating a peak value comparison reference voltage according to control voltage, and when the value of the control voltage is equal to zero V, or the value is larger than a first voltage value, the value of the peak value comparison reference voltage is a second voltage value. When the value of the control voltage is larger than zero V and smaller than or equal to the first voltage value, the value of the peak value comparison reference voltage is equal to the sum of a third voltage value and the value of the control voltagea, and the sum of the third voltage value and the first voltage value is equal to the second voltage value. According to the switching power supply and the control circuit of the switching power supply, the total harmonic distortion of the switching power supply is reduced.
Description
Technical field
The present invention relates to electric and electronic technical field, particularly a kind of Switching Power Supply and control circuit thereof.
Background technology
Switching Power Supply is to utilize modern power electronics technology, and the time ratio that control switch transistor turns on and off maintains stable a kind of power supply of exporting.Along with development and the innovation of power electronic technology, switch power technology is also in constantly innovation.At present, Switching Power Supply, with small-sized, light weight and high efficiency feature nearly all electronic equipment that is widely used, is the indispensable a kind of power mode of current electronics and information industry develop rapidly.Whether direct-current switch power supply is by having electrical isolation can be divided into two classes between input and output: isolation type switching power supply and non-isolated Switching Power Supply.
Fig. 1 is the structural representation of common a kind of isolation type switching power supply, described Switching Power Supply comprises rectifier bridge 10, elementary filter capacitor 11, transformer 12, switching transistor 13, sampling resistor 14, control circuit 15, rectifier diode 16 and secondary filter capacitor 17, wherein, described control circuit 15 is generally integrated circuit.Described control circuit 15 comprises peak current detection end CS, feedback end FB, drive end DRV, voltage comparator 151 and pwm unit 152.In described Switching Power Supply, the concrete annexation of each device, with reference to shown in figure 1, does not repeat them here.
The AC-input voltage Vac that described rectifier bridge 10 is suitable for inputting described Switching Power Supply carries out full-wave rectification, and described AC-input voltage Vac is become to unidirectional pulsating voltage by the positive and negative sinusoidal voltage rectification replacing; The pulsating voltage that described elementary filter capacitor 11 is suitable for described rectifier bridge 10 to export carries out smothing filtering, produces level and smooth DC input voitage Vbus; Described transformer 12 is suitable for by certain voltage ratio the voltage induced at its primary coil two ends to its secondary coil; Conducting or cut-off under the control of the driving voltage providing at described drive end DRV is provided described switching transistor 13; Described sampling resistor 14 is suitable for the current conversion that flows through described switching transistor 13 to be voltage and to transfer to described peak current detection end CS; Described control circuit 15 is suitable for providing described driving voltage according to the feedback signal of the voltage of described peak current detection end CS and described feedback end FB; The voltage that described rectifier diode 16 and described secondary filter capacitor 17 are suitable for the secondary coil two ends to described transformer 12 carries out rectification and filtering, produces constant voltage or electric current with the output out in described Switching Power Supply.
The feedback signal of described feedback end FB is provided by feedback circuit.Because described Switching Power Supply has various feedback pattern, correspondingly, described feedback circuit also has multiple circuit structure.Therefore, Fig. 1 does not provide the particular circuit configurations of described feedback circuit.In order to meet the load request of described Switching Power Supply, described control circuit 15 has power regulation functions.Particularly, in the time that the voltage of described peak current detection end CS is greater than preset peakedness ratio compared with reference voltage V ref, the power output that represents described Switching Power Supply has exceeded preset power output, the comparison signal that described pwm unit 152 is exported according to described voltage comparator 151 produces low level driving voltage, export the grid of described switching transistor 13 by described drive end DRV to, control described switching transistor 13 and end; In the time that the voltage of described peak current detection end CS is less than or equal to described peakedness ratio compared with reference voltage V ref, the power output that represents described Switching Power Supply does not exceed preset power output, and the driving voltage that described pwm unit 152 produces is determined by the feedback signal of described feedback end FB.
In the time of described switching transistor 13 conducting, primary current Ip arrives ground, the primary coil energy storage of described transformer 12 through primary coil, described switching transistor 13 and the described sampling resistor 14 of described transformer 12; In the time that described switching transistor 13 ends, be stored in energy in the primary coil of described transformer 12 and be coupled to the secondary coil of described transformer 12 through magnetic circuit, through the rectification of described rectifier diode 16 and the filtering of described secondary filter capacitor 17, produce constant voltage or electric current at described output out.
In order to reduce grid loss and pollution, the power factor (PF) of Switching Power Supply (PF, Power Factor) and total harmonic distortion (THD, Total Harmonic Distortion) need to meet certain requirement.For the Switching Power Supply shown in Fig. 1, when the system power of its application hour, can fill out paddy (ValleyFill) circuit by increase and improve its power factor (PF) and total harmonic distortion.Fig. 2 is the structural representation that paddy circuit is filled out in the Switching Power Supply increase shown in Fig. 1, fills out paddy circuit 20 and comprises the first electric capacity 201, the second electric capacity 202, the first diode 203, the second diode 204 and the 3rd diode 205.The operation principle of filling out paddy circuit 20 described in those skilled in the art know, does not repeat them here.
Described in employing, fill out after paddy circuit 20, the power factor of described Switching Power Supply is improved, and meets the requirement of correlation technique standard.Fig. 3 is the distribution map of input current individual harmonic current after frequency domain launches of the Switching Power Supply shown in Fig. 2, and abscissa is frequency, unit: KHz (kHz); Ordinate is input current, unit: milliampere (mA).Can find out from the input current waveform of described Switching Power Supply, the input current of described Switching Power Supply is on the basis of fundametal compoment, and a lot of higher harmonic components have superposeed.Larger higher harmonic components (for example 7 order harmonic components and 13 order harmonic components) exists, and causes the total harmonic distortion of described Switching Power Supply cannot meet the requirement of correlation technique standard.
In order further to improve the total harmonic distortion of described Switching Power Supply, in prior art, by increasing resistance to adjust the input current of described Switching Power Supply described in filling out paddy circuit 20, the circuit structure of described Switching Power Supply as shown in Figure 4.The described paddy circuit of filling out also comprises current-limiting resistance 206, and described current-limiting resistance 206 is connected with described the 3rd diode 205.Because described current-limiting resistance 206 can reduce the input current of described Switching Power Supply, the total harmonic distortion of described Switching Power Supply can be reduced, but still can not make the total harmonic distortion of described Switching Power Supply meet the requirement of correlation technique standard.And, in the charge circuit of described current-limiting resistance 206 in described the first electric capacity 201 and described the second electric capacity 202, the charging current of described the first electric capacity 201 and described the second electric capacity 202 is reduced, increased the loss while charging, cause the Efficiency Decreasing of described Switching Power Supply.Therefore, how in the situation that not reducing described switch power efficiency, to reduce total harmonic distortion and be still a problem demanding prompt solution.
Summary of the invention
What the present invention solved is the problem that Switching Power Supply total harmonic distortion is high.
For addressing the above problem, the invention provides a kind of control circuit of Switching Power Supply, comprise peak current detection end, feedback end, drive end, the first voltage comparator and pwm unit, also comprise:
Control end, is suitable for receiving control voltage;
Reference voltage adjustment unit, is suitable for producing peakedness ratio compared with reference voltage according to described control voltage:
In the time that the magnitude of voltage of described control voltage equals 0V or is greater than the first magnitude of voltage, described peakedness ratio is second voltage value compared with the magnitude of voltage of reference voltage;
In the time that the magnitude of voltage of described control voltage is greater than 0V and is not more than described the first magnitude of voltage, described peakedness ratio equals the magnitude of voltage sum of tertiary voltage value and described control voltage compared with the magnitude of voltage of reference voltage, described tertiary voltage value and described the first magnitude of voltage sum equal described second voltage value.
Optionally, described reference voltage adjustment unit comprises:
Clamper unit, is suitable in the time that the magnitude of voltage of described control end is greater than described the first magnitude of voltage, the magnitude of voltage of described control end being restricted to described the first magnitude of voltage;
Second voltage comparator, is suitable for the voltage of 0V voltage and described control end to compare to produce comparative level, produces the first comparative level in the time that the voltage of described control end is greater than 0V voltage, otherwise produces the second comparative level;
Selected cell, be suitable for receiving the voltage of the first reference voltage, described control end and the comparative level that described second voltage comparator produces, in the time receiving described the first comparative level, select the Voltage-output of described control end, in the time receiving described the second comparative level, select described the first reference voltage output, the magnitude of voltage of described the first reference voltage equals described the first magnitude of voltage;
Adder, the voltage of be suitable for superposeing the second reference voltage and the output of described selected cell is to produce described peakedness ratio compared with reference voltage, and the magnitude of voltage of described the second reference voltage equals described tertiary voltage value.
Based on the control circuit of above-mentioned Switching Power Supply, the present invention also provides a kind of Switching Power Supply, comprises rectifier bridge, fills out paddy circuit and switching transistor, also comprises:
The control circuit of above-mentioned Switching Power Supply;
Sample circuit, is suitable for the voltage of the described half-wave voltage signal node of filling out paddy circuit to sample to produce described control voltage.
Compared with prior art, technical scheme of the present invention has the following advantages:
The Switching Power Supply that technical solution of the present invention provides and control circuit thereof, by reference voltage adjustment unit is set in described control circuit, the peakedness ratio that generation magnitude of voltage can change with the AC-input voltage of described Switching Power Supply is compared with reference voltage.In the time that DC input voitage is lower, the peakedness ratio that described reference voltage adjustment unit produces is compared with the corresponding reduction of reference voltage.Because the lowest high-current value of the primary current of described Switching Power Supply and described peakedness ratio are compared with the reference voltage variation that is proportionate, described peakedness ratio reduces the lowest high-current value of described primary current is reduced compared with reference voltage, thereby the waveform that makes the interchange input current of described Switching Power Supply becomes level and smooth, can generation current jumping phenomenon, reduce the total harmonic distortion of described Switching Power Supply.And, described Switching Power Supply is that the voltage to filling out half-wave voltage signal node in paddy circuit is sampled and obtained the control voltage of described control circuit, this kind of sample mode is the simplest, is convenient to described control circuit and follows the tracks of the variation of AC-input voltage, can simplify the structure of described control circuit.
Further, the control circuit highly versatile of Switching Power Supply provided by the invention, applicable to dissimilar Switching Power Supply, described Switching Power Supply can be isolation type switching power supply (for example inverse-excitation type switch power-supply), also can be non-isolated Switching Power Supply (for example step-down/up type Switching Power Supply and step down switching regulator), reduce the cost of described Switching Power Supply.
In possibility of the present invention, described reference voltage adjustment unit comprises clamper unit, second voltage comparator, selected cell and adder, and described clamper unit comprises voltage stabilizing didoe.Described voltage stabilizing didoe simple in structure, has saved the area of described control circuit.
In possibility of the present invention, described clamper unit comprises transistor and operational amplifier.Because described operational amplifier has higher gain, in the time that the magnitude of voltage of the control end of described control circuit is greater than the first magnitude of voltage of setting, described operational amplifier can output control signals to described transistorized control electrode rapidly, control described transistor turns, described control end is shunted, thereby rapidly described control end is carried out to clamper, improve described peakedness ratio compared with the precision of reference voltage.
In possibility of the present invention, described transistor is PNP triode.Because described PNP triode has electric current enlarging function, can make response to the control signal of its base stage input rapidly, rapidly described control end is carried out to clamper.
Accompanying drawing explanation
Fig. 1 is the structural representation of existing a kind of Switching Power Supply;
Fig. 2 is the structural representation of existing another kind of Switching Power Supply;
Fig. 3 is the distribution map of input current individual harmonic current after frequency domain launches of the Switching Power Supply shown in Fig. 2;
Fig. 4 is the structural representation of existing another kind of Switching Power Supply;
Fig. 5 is that the AC-input voltage, DC input voitage, half-wave voltage signal node voltage, peakedness ratio of the Switching Power Supply shown in Fig. 2 is compared with reference voltage and exchange the time dependent waveform schematic diagram of input current;
Fig. 6 is the structural representation of the Switching Power Supply of embodiment of the present invention;
Fig. 7 is that the AC-input voltage, DC input voitage, control voltage, peakedness ratio of the Switching Power Supply of embodiment of the present invention is compared with reference voltage and exchange the time dependent waveform schematic diagram of input current;
Fig. 8 is the distribution map of input current individual harmonic current after frequency domain launches of the Switching Power Supply of embodiment of the present invention;
Fig. 9 is the structural representation of a kind of Switching Power Supply of providing of the embodiment of the present invention;
Figure 10 is that voltage, comparative level, the second reference voltage and the peakedness ratio of the control voltage that provides of the embodiment of the present invention, control end is compared with the time dependent waveform schematic diagram of reference voltage;
Figure 11 is the structural representation of a kind of clamper unit of providing of the embodiment of the present invention;
Figure 12 is the structural representation of the another kind of clamper unit that provides of the embodiment of the present invention;
Figure 13 is the structural representation of the another kind of clamper unit that provides of the embodiment of the present invention;
Figure 14 is the structural representation of a kind of selected cell of providing of the embodiment of the present invention;
Figure 15 is the structural representation of the another kind of Switching Power Supply that provides of the embodiment of the present invention;
Figure 16 is the structural representation of the another kind of Switching Power Supply that provides of the embodiment of the present invention.
Embodiment
The high order harmonic component that Switching Power Supply produces can produce conducted interference and radiated interference along grid power transmission circuit, thereby electric power system is produced and pollutes and affect other and normally move at road power consumption equipment.Therefore, no matter from protecting the safe operation of electrical network, or from the normal work of power consumption equipment, pollution, the inhibition electromagnetic interference of harmonic reduction to electrical network become industry question of common concern.The reason that Switching Power Supply produces high order harmonic component is mainly the interchange input current generation wave distortion that in Switching Power Supply, generally the capacitor filtering type bridge rectifier of employing causes.
Fill out paddy circuit 20 although the Switching Power Supply shown in Fig. 2 has increased, its total harmonic distortion still cannot meet the requirement of correlation technique standard.Fig. 5 be AC-input voltage Vac, DC input voitage Vbus, the half-wave voltage signal node N0 of the Switching Power Supply shown in Fig. 2 voltage VH, peakedness ratio is compared with reference voltage V ref and exchange the input current Iac waveform schematic diagram that t changes in time, the voltage VH of described AC-input voltage Vac, DC input voitage Vbus, half-wave voltage signal node N0 and exchange input current Iac and be all cyclic variation.Wherein, the frequency of described AC-input voltage Vac is identical with the described frequency that exchanges input current Iac, the frequency of described DC input voitage Vbus is identical with the frequency of the voltage VH of described half-wave voltage signal node N0, and the frequency of described DC input voitage Vbus is the twice of the frequency of described AC-input voltage Vac.
Because described AC-input voltage Vac is periodically variable, the course of work of described Switching Power Supply is also cyclic variation.Take half work period T0 of described AC-input voltage Vac as example, below in conjunction with Fig. 2, each waveform in Fig. 5 is described in detail.According to the changes in amplitude situation of described AC-input voltage Vac, described half work period T0 comprises four moment: the first moment t1, the second moment t2, the 3rd moment t3 and the 4th moment t4.Described the first moment t1 is the initial time of described half work period T0, and at described the first moment t1, the amplitude of described AC-input voltage Vac is zero; From described the first moment t1, the amplitude of described AC-input voltage Vac constantly increases, and during to described the second moment t2, the amplitude of described AC-input voltage Vac is increased to the half of peak value Upk; The amplitude of described AC-input voltage Vac continues to increase, and constantly reduces after reaching peak value Upk, and during to described the 3rd moment t3, the amplitude of described AC-input voltage Vac is reduced to the half of peak value Upk; The amplitude of described AC-input voltage Vac continues to reduce, and during to described the 4th moment t4, the amplitude of described AC-input voltage Vac reduces to zero, and described half work period T0 finishes.
Between described the first moment t1 and described the second moment t2, due to the unilateal conduction effect of described the 3rd diode 205, described the first electric capacity 201 and described the second electric capacity 202 are in parallel discharge state, and the amplitude of the voltage VH of described half-wave voltage signal node N0 is zero.The electric energy of the load consumption of described Switching Power Supply is provided by described the first electric capacity 201 and described the second electric capacity 202 completely, thereby the amplitude of described interchange input current Iac is zero.Because the load of described Switching Power Supply constantly consumes electric energy, the amplitude of described DC input voitage Vbus constantly reduces.During to described the second moment t2, the amplitude of described DC input voitage Vbus is down to minimum.
Between described the second moment t2 and described the 3rd moment t3, the electric energy of the load consumption of described Switching Power Supply is provided by described AC-input voltage Vac, and described DC input voitage Vbus follows described AC-input voltage Vac and changes.And, near the amplitude of described AC-input voltage Vac reaches peak value Upk, described AC-input voltage Vac not only provides the energy of the load consumption of described Switching Power Supply, also by described the 3rd diode 205 conductings, described the first electric capacity 201 and described the second electric capacity 202 are charged, therefore, the amplitude of described interchange input current Iac reaches peak value.
Between described the 3rd moment t3 and described the 4th moment t4, described the first electric capacity 201 and described the second electric capacity 202 parallel discharge again, the electric energy of the load consumption of described Switching Power Supply is provided by described the first electric capacity 201 and described the second electric capacity 202 completely, and the amplitude of described DC input voitage Vbus constantly reduces.At described AC-input voltage Vac, the operating state during in negative half period, with at described AC-input voltage Vac, the operating state during in positive half cycle is similar, does not repeat them here described Switching Power Supply.
In prior art, in the time that the load of described Switching Power Supply is constant, the input power of described Switching Power Supply is invariable, and described peakedness ratio is constant compared with the magnitude of voltage of reference voltage V ref.At described the second moment t2 and described the 3rd moment t3, the amplitude of described DC input voitage Vbus falls too low, equal the product of voltage and electric current according to power, the amplitude of described primary current Ip is very high, cause that described interchange input current Iac undergos mutation at described the second moment t2 and described the 3rd moment t3, produce larger peak current, cause the total harmonic distortion of described Switching Power Supply high.
Technical solution of the present invention provides a kind of Switching Power Supply and control circuit thereof, by reference voltage adjustment unit is set in described control circuit, the peakedness ratio that generation magnitude of voltage can change with the AC-input voltage of described Switching Power Supply is compared with reference voltage, make the waveform of the interchange input current of described Switching Power Supply become level and smooth, can generation current jumping phenomenon, reduce the total harmonic distortion of described Switching Power Supply.
Fig. 6 is the structural representation of the Switching Power Supply of embodiment of the present invention, described Switching Power Supply comprises rectifier bridge 60, transformer 62, switching transistor 63, sampling resistor 64, control circuit 65, rectifier diode 66, secondary filter capacitor 67, fills out paddy circuit 68 and sample circuit 69, wherein, the concrete structure of described rectifier bridge 60, described transformer 62, described switching transistor 63, described sampling resistor 64, described rectifier diode 66 and described secondary filter capacitor 67 and function similarly to the prior art, do not repeat them here.
Described sample circuit 69 is suitable for the voltage VH of the described half-wave voltage signal node N0 that fills out paddy circuit 68 to sample to produce control voltage Vctr.Particularly, the described paddy circuit 68 of filling out comprises the first electric capacity 681, the second electric capacity 682, the first diode 683, the second diode 684 and the 3rd diode 685, and described half-wave voltage signal node N0 is the connected node of described the first electric capacity 681, described the first diode 683 and described the 3rd diode 685.Because described control voltage Vctr is to the voltage VH of the described half-wave voltage signal node N0 acquisition of sampling, described control voltage Vctr can follow with a predefined voltage ratio voltage VH variation of described half-wave voltage signal node N0, for example, the voltage ratio of setting the voltage VH of described control voltage Vctr and described half-wave voltage signal node N0 is 1:100, in the time that the voltage VH of described half-wave voltage signal node N0 is 100V, described control voltage Vctr is 1V.Described voltage ratio can arrange by actual demand, and the present invention is not construed as limiting this.
Described control circuit 65 comprises peak current detection end CS, feedback end FB, drive end DRV, the first voltage comparator 651, pwm unit 652, control end CTR and reference voltage adjustment unit 653.The concrete structure of described peak current detection end CS, described feedback end FB, described drive end DRV, described the first voltage comparator 651 and described pwm unit 652 and function similarly to the prior art, do not repeat them here.
Described control end CTR is suitable for receiving described control voltage Vctr, be that described control end CTR is suitable for receiving the sample voltage of acquisition to the voltage VH of described half-wave voltage signal node N0, described control end CTR connects described sample circuit 69 and exports the output of described control voltage Vctr.Described reference voltage adjustment unit 653 is suitable for producing peakedness ratio compared with reference voltage V ref according to described control voltage Vctr, and described peakedness ratio is controlled by described control voltage Vctr compared with reference voltage V ref.Particularly, equal 0V or in the time that the magnitude of voltage of described control voltage Vctr is greater than the first magnitude of voltage, described peakedness ratio is second voltage value compared with the magnitude of voltage of reference voltage V ref at the magnitude of voltage of described control voltage Vctr; When the magnitude of voltage that is greater than 0V and described control voltage Vctr at the magnitude of voltage of described control voltage Vctr is not more than described the first magnitude of voltage, described peakedness ratio equals the magnitude of voltage sum of tertiary voltage value and described control voltage Vctr compared with the magnitude of voltage of reference voltage V ref.Wherein, described tertiary voltage value and described the first magnitude of voltage sum equal described second voltage value.
Described the first magnitude of voltage, described second voltage value and described tertiary voltage value all can be set according to the actual requirements, and the present invention is not restricted this.Further, described second voltage value and peakedness ratio of the prior art are similar compared with the magnitude of voltage of reference voltage, and it is relevant to the power output of described Switching Power Supply: if the power output of described Switching Power Supply is larger, described second voltage value arranges greatlyr; If the power output of described Switching Power Supply is less, described second voltage value arranges littlely.Those skilled in the art know how to set described second voltage value according to the performance number of the power output of described Switching Power Supply, do not repeat them here.Described the first magnitude of voltage is the threshold value of setting, in the time that the voltage ratio of the voltage VH of described control voltage Vctr and described half-wave voltage signal node N0 is determined, the total harmonic distortion of described Switching Power Supply is relevant to described the first magnitude of voltage: described the first magnitude of voltage arranges greatlyr, and the total harmonic distortion of described Switching Power Supply is less.Therefore, can require to determine described the first magnitude of voltage according to the total harmonic distortion to described Switching Power Supply.
Fig. 7 be the Switching Power Supply of embodiment of the present invention AC-input voltage Vac, DC input voitage Vbus, control voltage Vctr, peakedness ratio is compared with reference voltage V ref and exchange the time dependent waveform schematic diagram of input current Iac, each voltage and electric current are all cyclic variation.Wherein, the frequency of described AC-input voltage Vac is identical with the described frequency that exchanges input current Iac, the frequency of described DC input voitage Vbus, frequency and the peakedness ratio of controlling voltage Vctr are identical compared with the frequency of reference voltage V ref, and the frequency of described DC input voitage Vbus is the twice of the frequency of described AC-input voltage Vac.
Or take half work period T0' of described AC-input voltage Vac as example, below in conjunction with Fig. 6, each waveform in Fig. 7 is described in detail.According to the changes in amplitude situation of described AC-input voltage Vac, described half work period T0' comprises six moment: the first moment t1', the second moment t2', the 3rd moment t3', the 4th moment t4', the 5th moment t5' and the 6th moment t6'.
Described the first moment t1' is the initial time of described half work period T0', and at described the first moment t1', the amplitude of described AC-input voltage Vac is zero; From described the first moment t1', the amplitude of described AC-input voltage Vac constantly increases, and during to described the second moment t2', the amplitude of described AC-input voltage Vac is increased to the half of peak value Upk; The amplitude of described AC-input voltage Vac continues to increase, and during to described the 3rd moment t3', the magnitude of voltage of described control voltage Vctr is increased to described the first magnitude of voltage U1; The amplitude of described AC-input voltage Vac continues to increase, and constantly reduces after reaching peak value Upk, and during to described the 4th moment t4', the magnitude of voltage of described control voltage Vctr is reduced to described the first magnitude of voltage U1; The amplitude of described AC-input voltage Vac continues to reduce, and during to described the 4th moment t5', the amplitude of described AC-input voltage Vac is reduced to the half of peak value Upk; The amplitude of described AC-input voltage Vac continues to reduce, and during to described the 6th moment t6', the amplitude of described AC-input voltage Vac reduces to zero, and described half work period T0' finishes.
Between described the first moment t1' and described the second moment t2', due to the unilateal conduction effect of described the 3rd diode 685, described the first electric capacity 681 and described the second electric capacity 682 are in parallel discharge state, the magnitude of voltage of the voltage VH of described half-wave voltage signal node N0 is zero, and the magnitude of voltage of following the control voltage Vctr of the voltage VH variation of described half-wave voltage signal node N0 is also zero.Therefore the described peakedness ratio that, described reference voltage adjustment unit 653 produces is second voltage value U2 compared with the magnitude of voltage of reference voltage V ref.The electric energy of the load consumption of described Switching Power Supply is provided by described the first electric capacity 681 and described the second electric capacity 682 completely, and the amplitude of described interchange input current Iac is zero.Because the load of described Switching Power Supply constantly consumes electric energy, the amplitude of described DC input voitage Vbus constantly reduces.During to described the second moment t2', the amplitude of described DC input voitage Vbus is down to minimum.
Between described the second moment t2' and described the 3rd moment t3', the electric energy of the load consumption of described Switching Power Supply is provided by described AC-input voltage Vac, described DC input voitage Vbus follows described AC-input voltage Vac and changes, the magnitude of voltage of the voltage VH of described half-wave voltage signal node N0 constantly increases, the magnitude of voltage of following the control voltage Vctr of the voltage VH variation of described half-wave voltage signal node N0 also constantly increases, and the magnitude of voltage of described control voltage Vctr is not more than described the first magnitude of voltage U1.Therefore the described peakedness ratio that, described reference voltage adjustment unit 653 produces equals the magnitude of voltage sum of tertiary voltage value U3 and described control voltage Vctr compared with the magnitude of voltage of reference voltage V ref.
Because described peakedness ratio increases to described the first magnitude of voltage U1 compared with the magnitude of voltage of reference voltage V ref by described tertiary voltage value U3, between described the second moment t2' and described the 3rd moment t3', the input power of described Switching Power Supply is slowly to change.Compared with prior art, the lowest high-current value of the primary current of described Switching Power Supply reduces, and the waveform of described interchange input current Iac is become smoothly, has avoided generation current jumping phenomenon.
Between described the 3rd moment t3' and described the 4th moment t4', the electric energy of the load consumption of described Switching Power Supply is still provided by described AC-input voltage Vac, and the magnitude of voltage of described control voltage Vctr is greater than described the first magnitude of voltage U1.Therefore the described peakedness ratio that, described reference voltage adjustment unit 653 produces equals described second voltage value U2 compared with the magnitude of voltage of reference voltage V ref.Near the amplitude of described AC-input voltage Vac reaches peak value Upk, described AC-input voltage Vac not only provides the energy of the load consumption of described Switching Power Supply, also by described the 3rd diode 685 conductings, described the first electric capacity 681 and described the second electric capacity 682 are charged, the amplitude of described interchange input current Iac reaches peak value.
Between described the 4th moment t4' and described the 5th moment t5', the magnitude of voltage of described control voltage Vctr is again between 0V and described the first magnitude of voltage U1.Therefore, described peakedness ratio equals the magnitude of voltage sum of tertiary voltage value U3 and described control voltage Vctr compared with the magnitude of voltage of reference voltage V ref, makes the waveform of described interchange input current Iac become level and smooth.
Between described the 5th moment t5' and described the 6th moment t6', described the first electric capacity 681 and described the second electric capacity 682 parallel discharge again, the electric energy of the load consumption of described Switching Power Supply is provided by described the first electric capacity 681 and described the second electric capacity 682 completely, and the amplitude of described DC input voitage Vbus constantly reduces.The magnitude of voltage of the voltage VH of described half-wave voltage signal node N0 is zero, and the magnitude of voltage of following the control voltage Vctr of the voltage VH variation of described half-wave voltage signal node N0 is also zero.Therefore the described peakedness ratio that, described reference voltage adjustment unit 653 produces is second voltage value U2 compared with the magnitude of voltage of reference voltage V ref.At described AC-input voltage Vac, the operating state during in negative half period, with at described AC-input voltage Vac, the operating state during in positive half cycle is similar, does not repeat them here described Switching Power Supply.
Constant peakedness ratio is different compared with reference voltage from arranging in prior art, the Switching Power Supply that embodiment of the present invention provides and control circuit thereof, by the voltage VH of described half-wave voltage signal node N0 is sampled obtain described control voltage Vctr, then by described control voltage Vctr control described reference voltage adjustment unit 653 obtain magnitude of voltage change peakedness ratio compared with reference voltage V ref.Between described the second moment t2' and described the 3rd moment t3' and between described the 4th moment t4' and described the 5th moment t5', described peakedness ratio reduces and reduces with the voltage VH of described half-wave voltage signal node N0 compared with reference voltage V ref, the amplitude of the primary current of described Switching Power Supply reduces, make described interchange input current Iac become level and smooth, produce without peak current, reduce the total harmonic distortion of described Switching Power Supply.
Fig. 8 is the distribution map of input current individual harmonic current after frequency domain launches of the Switching Power Supply of embodiment of the present invention, and abscissa is frequency, unit: KHz (kHz); Ordinate is input current, unit: milliampere (mA).As can be seen from Figure 8, compared with the Switching Power Supply of prior art, each higher harmonic components of the Switching Power Supply of embodiment of the present invention obviously declines, corresponding the reducing of total harmonic distortion of described Switching Power Supply.
For above-mentioned purpose of the present invention, feature and advantage can more be become apparent, below in conjunction with accompanying drawing, specific embodiments of the invention are described in detail.
Fig. 9 is the structural representation of a kind of Switching Power Supply of providing of the embodiment of the present invention, described Switching Power Supply comprises rectifier bridge 90, transformer 92, switching transistor 93, sampling resistor 94, control circuit 95, rectifier diode 96, secondary filter capacitor 97, fills out paddy circuit 98 and sample circuit 99, wherein, described control circuit 95 comprises peak current detection end CS, feedback end FB, drive end DRV, the first voltage comparator 951, pwm unit 952, control end CTR and reference voltage adjustment unit 953.
Particularly, in the present embodiment, described sample circuit 99 comprises the first impedance component 991 and the second impedance component 992.One end of described the first impedance component 991 connects half-wave voltage signal node N0, and the other end of described the first impedance component 991 connects one end of described the second impedance component 992 and is suitable for producing control voltage Vctr, the other end ground connection of described the second impedance component 992.By the dividing potential drop of described the first impedance component 991 and described the second impedance component 992, realize the voltage VH sampling to described half-wave voltage signal node N0, obtain described control voltage Vctr.It should be noted that, described impedance component 991 and described the second impedance component 992 can be pure resistance element, also can be for presenting other electric components of impedance operator, and the present invention is not construed as limiting this.
Described reference voltage adjustment unit 953 comprises clamper unit 9531, second voltage comparator 9532, selected cell 9533 and adder 9534.
Described clamper unit 9531 is suitable for described control end CTR to carry out clamper,, in the time that the magnitude of voltage of the voltage Vq of described control end CTR is greater than described the first magnitude of voltage U1, the magnitude of voltage of the voltage Vq of described control end CTR is restricted to described the first magnitude of voltage U1.
Described second voltage comparator 9532 is suitable for the voltage Vq of 0V voltage and described control end CTR to compare to produce comparative level Vcomp, produces the first comparative level in the time that the voltage Vq of described control end CTR is greater than 0V voltage, otherwise produces the second comparative level.Particularly, the first input end of described second voltage comparator 9532 connects described control end CTR, the second input end grounding of described second voltage comparator 9532.It should be noted that, in the present embodiment, the first input end of described second voltage comparator 9532 is the anode of described second voltage comparator 9532, and the second input of described second voltage comparator 9532 is the negative terminal of described second voltage comparator 9532.In other embodiments, the first input end of described second voltage comparator 9532 can be also the negative terminal of described second voltage comparator 9532, the second input of described second voltage comparator 9532 should be the anode of described second voltage comparator 9532 mutually, and the present invention is not construed as limiting this.
Described selected cell 9533 is suitable for receiving the voltage Vq of the first reference voltage VR1, described control end CTR and the comparative level Vcomp that described second voltage comparator 9532 produces, in the time receiving described the first comparative level, select the voltage Vq output of described control end CTR, in the time receiving described the second comparative level, select described the first reference voltage VR1 output, the magnitude of voltage of described the first reference voltage VR1 equals described the first magnitude of voltage U1.
Described adder 9534 is suitable for superposeing voltage that the second reference voltage VR2 and described selected cell 9533 export to produce described peakedness ratio compared with reference voltage V ref, and the magnitude of voltage of described the second reference voltage VR2 equals described tertiary voltage value U3.Described adder 9534 can adopt operational amplifier to realize, and those skilled in the art know the physical circuit of described adder 9534, do not repeat them here.
Described the first reference voltage VR1 and described the second reference voltage VR2 can be provided by external circuit, also can be provided by the internal source voltage of described control circuit 953.In the present embodiment, described control circuit 953 also comprises the first voltage source 9535 and second voltage source 9536.The anode of described the first voltage source 9535 is suitable for exporting described the first reference voltage VR1, the negativing ending grounding of described the first voltage source 9535; The anode in described second voltage source 9536 is suitable for exporting described the second reference voltage VR2, the negativing ending grounding in described second voltage source 8536.
Figure 10 be voltage Vq, comparative level Vcomp, the second reference voltage VR2 and the peakedness ratio of control voltage Vctr, the control end CTR of the embodiment of the present invention compared with the time dependent waveform schematic diagram of reference voltage V ref, below in conjunction with Fig. 9 and Figure 10, the operation principle of the reference voltage adjustment unit 953 to the embodiment of the present invention describes.
Described control end CTR receives the control voltage Vctr that described sample circuit 89 is exported, and the waveform of described control voltage Vctr is half-wave.Along with described control voltage Vctr constantly increases, the voltage Vq of described control end CTR constantly increases.In the time that the magnitude of voltage of described control voltage Vctr exceedes described the first magnitude of voltage U1, described clamper unit 9531 carries out clamper to described control end CTR, and the magnitude of voltage of the voltage Vq of described control end CTR is limited in to described the first magnitude of voltage U1.
Voltage Vq and the 0V voltage of described second voltage comparator 9532 to described control end CTR compares, and in the time that the voltage Vq of described control end CTR is greater than 0V, described comparative level Vcomp is the first comparative level comp1; In the time that the voltage Vq of described control end CTR equals 0V, described comparative level Vcomp is the second comparative level comp2.Described the first comparative level comp1 is high level, and described the second comparative level comp2 is low level.
Described selected cell 9533 is exported the voltage Vq of described control end CTR in the time receiving described the first comparative level comp1, and described adder 9534 is added the voltage Vq of described control end CTR and described the second reference voltage VR2; Described selected cell 9533 is exported described the first reference voltage VR1 in the time receiving described the second comparative level comp2, and described adder 9534 is added described the first reference voltage VR1 and described the second reference voltage VR2.
The embodiment of the present invention provides the particular circuit configurations of a kind of described clamper unit 9531, as shown in figure 11.Described clamper unit 9531 comprises voltage stabilizing didoe D0, and the magnitude of voltage of the burning voltage of described voltage stabilizing didoe D0 equals described the first magnitude of voltage U1.Particularly, the negative electrode of described voltage stabilizing didoe D0 connects described control end CTR, the plus earth of described voltage stabilizing didoe D0.In the time that the magnitude of voltage of described control end CTR is greater than described the first magnitude of voltage U1, described voltage stabilizing didoe D0 is breakdown, and the magnitude of voltage Vq of described control end CTR equals the burning voltage of described voltage stabilizing didoe D0.Described voltage stabilizing didoe D0's is simple in structure, has saved the area of described control circuit 95.
The embodiment of the present invention provides the particular circuit configurations of another kind of described clamper unit 9531, as shown in figure 12.Described clamper unit 9531 comprises transistor Q0 and operational amplifier A 0, wherein, the control electrode of described transistor Q0 connects the output of described operational amplifier A 0, the first electrode of described transistor Q0 connects the inverting input of described control end CTR and described operational amplifier A 0, the second electrode grounding of described transistor Q0, the in-phase input end of described operational amplifier A 0 is suitable for inputting described the first reference voltage VR1.
In the time that the magnitude of voltage of described control end CTR is greater than described the first magnitude of voltage U1, the anti-phase input terminal voltage of described operational amplifier A 0, higher than its in-phase input end voltage, produces amplifying signal; Crystal Q0 conducting described in described amplifying signal control, described transistor Q0 shunts described control end CTR, makes the voltage drop of described control end CTR, and the magnitude of voltage of the voltage Vq of described control end CTR is limited in to described the first magnitude of voltage U1.
Because described operational amplifier A 0 has higher gain, in the time that the magnitude of voltage of described control end CTR is greater than described the first magnitude of voltage U1, described operational amplifier A 0 can output control signals to the control electrode of described transistor Q0 rapidly, control described transistor Q0 conducting, described control end CTR is shunted, thereby rapidly described control end CTR is carried out to clamper, improve described peakedness ratio compared with the precision of reference voltage V ref.
In the present embodiment, described transistor Q0 is PNP triode: the base stage of described PNP triode is the control electrode of described transistor Q0, the first electrode of the very described transistor Q0 of the transmitting of described PNP triode, the second electrode of the very described transistor Q0 of the current collection of described PNP triode.Because described PNP triode has electric current enlarging function, can make response to the control signal of its base stage input rapidly, rapidly described control end CTR is carried out to clamper.
The embodiment of the present invention provides the particular circuit configurations of another kind of described clamper unit 9531, as shown in figure 13.Described clamper unit 9531 comprises transistor Q0' and operational amplifier A 0', wherein, the control electrode of described transistor Q0' connects the output of described operational amplifier A 0', the first electrode of described transistor Q0' connects the inverting input of described control end CTR and described operational amplifier A 0', the second electrode grounding of described transistor Q0', the in-phase input end of described operational amplifier A 0' is suitable for inputting described the first reference voltage VR1.
In the present embodiment, described transistor Q0' is PMOS pipe: the grid of described PMOS pipe is the control electrode of described transistor Q0', the drain electrode of described PMOS pipe is the first electrode of described transistor Q0', and the source electrode of described PMOS pipe is the second electrode of described transistor Q0'.
The embodiment of the present invention provides a kind of particular circuit configurations of described selected cell 9533, as shown in figure 14.Described selected cell 9533 comprises the first K switch 1 and second switch K2.Particularly, the control electrode of described the first K switch 1 connects the control electrode of described second switch K2 and the output of described second voltage comparator 9532, be suitable for inputting described comparative level Vcomp, the first end of described the first K switch 1 connects described control end CTR, be suitable for inputting the voltage Vq of described control end CTR, the second end of described the first K switch 1 connects the first end of described second switch K2 the output Out1 as described selected cell 9533, connects described adder 9534.The second end of described second switch K2 is suitable for inputting described the first reference voltage VR1.
Described first K switch 1 conducting in the time receiving described the first comparative level comp1 disconnects in the time receiving described the second comparative level comp2; Described second switch K2 conducting in the time receiving described the second comparative level comp2 disconnects in the time receiving described the first comparative level comp1.
It should be noted that, described the first K switch 1 and described second switch K2 can be MOS switch.For example, described the first K switch 1 is NMOS pipe, and described second switch K2 is PMOS pipe.The grid of described NMOS pipe is the control electrode of described the first K switch 1, and the drain electrode of described NMOS pipe is the first end of described the first K switch 1, and the source electrode of described NMOS pipe is the second end of described the first K switch 1; The grid of described PMOS pipe is the control electrode of described second switch K2, and the drain electrode of described PMOS pipe is the first end of described second switch K2, and the source electrode of described PMOS pipe is the second end of described second switch K2.Described the first K switch 1 and described second switch K2 can be also other device or integrated circuits with switching function, and the present invention is not construed as limiting this.
In embodiments of the present invention and embodiment, be all to describe as an example of inverse-excitation type switch power-supply example.In fact, the control circuit highly versatile of Switching Power Supply provided by the invention, Switching Power Supply applicable to dissimilar: can be applied to (example inverse-excitation type switch power-supply as shown in Figure 8) in isolation type switching power supply, also can be applied in non-isolated Switching Power Supply.
Figure 15 is the structural representation of the another kind of Switching Power Supply that provides of the embodiment of the present invention, and described Switching Power Supply is step down switching regulator.Particularly, described Switching Power Supply comprises rectifier bridge 60a, inductance 62a, switching transistor 63a, sampling resistor 64a, control circuit 65a, rectifier diode 66a, secondary filter capacitor 67a, fills out paddy circuit 68a and sample circuit 69a, wherein, described control circuit 65a comprises peak current detection end CS, feedback end FB, drive end DRV, the first voltage comparator 65a1, pwm unit 65a2, control end CTR and reference voltage adjustment unit 65a3.The concrete structure of described sample circuit 69a and described control circuit 65a and function can be with reference to the descriptions to Fig. 6, and those skilled in the art know the specific works principle of step down switching regulator, do not repeat them here.
Figure 16 is the structural representation of the another kind of Switching Power Supply that provides of the embodiment of the present invention, described Switching Power Supply is step-down/up type Switching Power Supply, comprise rectifier bridge 60b, inductance 62b, switching transistor 63b, sampling resistor 64b, control circuit 65b, rectifier diode 66b, secondary filter capacitor 67b, fill out paddy circuit 68b and sample circuit 69b, wherein, described control circuit 65b comprises peak current detection end CS, feedback end FB, drive end DRV, the first voltage comparator 65b1, pwm unit 65b2, control end CTR and reference voltage adjustment unit 65b3.The concrete structure of described sample circuit 69b and described control circuit 65b and function can be with reference to the descriptions to Fig. 6, and those skilled in the art know the specific works principle of step-down/up type Switching Power Supply, do not repeat them here.
In sum, the Switching Power Supply that technical solution of the present invention provides and control circuit thereof, sample by the half-wave voltage signal node to filling out paddy circuit, obtain and control voltage, and change peakedness ratio compared with reference voltage by reference voltage adjustment unit according to described control voltage, make the input power of described Switching Power Supply follow the input voltage variation of described Switching Power Supply, to eliminate the spike that exchanges input current, reduce the total harmonic distortion of described Switching Power Supply.
Although the present invention discloses as above, the present invention is not defined in this.Any those skilled in the art, without departing from the spirit and scope of the present invention, all can make various changes or modifications, and therefore protection scope of the present invention should be as the criterion with claim limited range.
Claims (11)
1. a control circuit for Switching Power Supply, comprises peak current detection end, feedback end, drive end, the first voltage comparator and pwm unit, it is characterized in that, also comprises:
Control end, is suitable for receiving control voltage;
Reference voltage adjustment unit, is suitable for producing peakedness ratio compared with reference voltage according to described control voltage:
In the time that the magnitude of voltage of described control voltage equals 0V or is greater than the first magnitude of voltage, described peakedness ratio is second voltage value compared with the magnitude of voltage of reference voltage;
In the time that the magnitude of voltage of described control voltage is greater than 0V and is not more than described the first magnitude of voltage, described peakedness ratio equals the magnitude of voltage sum of tertiary voltage value and described control voltage compared with the magnitude of voltage of reference voltage, described tertiary voltage value and described the first magnitude of voltage sum equal described second voltage value.
2. the control circuit of Switching Power Supply as claimed in claim 1, is characterized in that, described reference voltage adjustment unit comprises:
Clamper unit, is suitable in the time that the magnitude of voltage of described control end is greater than described the first magnitude of voltage, the magnitude of voltage of described control end being restricted to described the first magnitude of voltage;
Second voltage comparator, is suitable for the voltage of 0V voltage and described control end to compare to produce comparative level, produces the first comparative level in the time that the voltage of described control end is greater than 0V voltage, otherwise produces the second comparative level;
Selected cell, be suitable for receiving the voltage of the first reference voltage, described control end and the comparative level that described second voltage comparator produces, in the time receiving described the first comparative level, select the Voltage-output of described control end, in the time receiving described the second comparative level, select described the first reference voltage output, the magnitude of voltage of described the first reference voltage equals described the first magnitude of voltage;
Adder, the voltage of be suitable for superposeing the second reference voltage and the output of described selected cell is to produce described peakedness ratio compared with reference voltage, and the magnitude of voltage of described the second reference voltage equals described tertiary voltage value.
3. the control circuit of Switching Power Supply as claimed in claim 2, is characterized in that, described clamper unit comprises voltage stabilizing didoe, and the magnitude of voltage of the burning voltage of described voltage stabilizing didoe equals described the first magnitude of voltage;
The negative electrode of described voltage stabilizing didoe connects described control end, the plus earth of described voltage stabilizing didoe.
4. the control circuit of Switching Power Supply as claimed in claim 2, is characterized in that, described clamper unit comprises transistor and operational amplifier;
Described transistorized control electrode connects the output of described operational amplifier, and described transistorized the first electrode connects the inverting input of described control end and described operational amplifier, described transistorized the second electrode grounding;
The in-phase input end of described operational amplifier is suitable for inputting described the first reference voltage.
5. the control circuit of Switching Power Supply as claimed in claim 4, is characterized in that, described transistor is PNP triode;
The base stage of described PNP triode is described transistorized control electrode, very described transistorized the first electrode of the transmitting of described PNP triode, very described transistorized the second electrode of the current collection of described PNP triode.
6. the control circuit of Switching Power Supply as claimed in claim 4, is characterized in that, described transistor is PMOS pipe;
The grid of described PMOS pipe is described transistorized control electrode, and the drain electrode of described PMOS pipe is described transistorized the first electrode, and the source electrode of described PMOS pipe is described transistorized the second electrode.
7. the control circuit of Switching Power Supply as claimed in claim 2, is characterized in that, described selected cell comprises the first switch and second switch;
The control electrode of described the first switch connects the control electrode of described second switch and the output of described second voltage comparator, the first end of described the first switch connects described control end, and the second end of described the first switch connects the first end of described second switch the output as described selected cell;
The second end of described second switch is suitable for inputting described the first reference voltage;
The conducting in the time that described selected cell receives described the first comparative level of described the first switch disconnects in the time that described selected cell receives described the second comparative level;
Described second switch disconnects in the time that described selected cell receives described the first comparative level, conducting in the time that described selected cell receives described the second comparative level.
8. the control circuit of the Switching Power Supply as described in claim 2 to 7 any one, is characterized in that, also comprises:
The first voltage source, is suitable for providing described the first reference voltage;
Second voltage source, is suitable for providing described the second reference voltage.
9. a Switching Power Supply, comprises rectifier bridge, fills out paddy circuit and switching transistor, it is characterized in that, also comprises:
The control circuit of the Switching Power Supply described in claim 1 to 8 any one;
Sample circuit, is suitable for the voltage of the described half-wave voltage signal node of filling out paddy circuit to sample to produce described control voltage.
10. Switching Power Supply as claimed in claim 9, is characterized in that, described sample circuit comprises the first impedance component and the second impedance component;
Described first impedor one end connects described half-wave voltage signal node, and the described first impedor other end connects described second impedor one end and is suitable for producing described control voltage;
Described the second impedor other end ground connection.
11. Switching Power Supplies as claimed in claim 9, is characterized in that, described Switching Power Supply is inverse-excitation type switch power-supply, step down switching regulator or step-down/up type Switching Power Supply.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201410164522.5A CN103916020B (en) | 2014-04-22 | 2014-04-22 | Switching Power Supply and control circuit thereof |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201410164522.5A CN103916020B (en) | 2014-04-22 | 2014-04-22 | Switching Power Supply and control circuit thereof |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN103916020A true CN103916020A (en) | 2014-07-09 |
| CN103916020B CN103916020B (en) | 2016-08-24 |
Family
ID=51041475
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201410164522.5A Active CN103916020B (en) | 2014-04-22 | 2014-04-22 | Switching Power Supply and control circuit thereof |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN103916020B (en) |
Cited By (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105978535A (en) * | 2016-05-24 | 2016-09-28 | 浙江大华技术股份有限公司 | Low-frequency signal generating circuit and isolated switching power supply |
| CN107957514A (en) * | 2016-10-14 | 2018-04-24 | 佛山市顺德区美的电热电器制造有限公司 | A kind of zero crossing detection device, method and electric appliance |
| CN109068444A (en) * | 2018-08-17 | 2018-12-21 | 江苏大学 | A kind of single-stage non-isolation type valley fill type no electrolytic capacitor LED drive power and switching method |
| CN109600060A (en) * | 2018-12-27 | 2019-04-09 | 广州金升阳科技有限公司 | A kind of modified flyback power supply circuit |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN201122904Y (en) * | 2007-11-29 | 2008-09-24 | 上海辰蕊微电子科技有限公司 | Summit current operated electric voltage feed forward circuit in switch power source |
| US7609533B2 (en) * | 2007-05-29 | 2009-10-27 | Richtek Technology Corp. | Light-load efficiency improving method and apparatus for a flyback converter |
| CN101951177A (en) * | 2010-09-06 | 2011-01-19 | Bcd半导体制造有限公司 | Switch power supply system and switching power source control circuit |
| CN103166471A (en) * | 2011-12-19 | 2013-06-19 | 比亚迪股份有限公司 | Switching power supply, control method of switching power supply and control chip |
-
2014
- 2014-04-22 CN CN201410164522.5A patent/CN103916020B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US7609533B2 (en) * | 2007-05-29 | 2009-10-27 | Richtek Technology Corp. | Light-load efficiency improving method and apparatus for a flyback converter |
| CN201122904Y (en) * | 2007-11-29 | 2008-09-24 | 上海辰蕊微电子科技有限公司 | Summit current operated electric voltage feed forward circuit in switch power source |
| CN101951177A (en) * | 2010-09-06 | 2011-01-19 | Bcd半导体制造有限公司 | Switch power supply system and switching power source control circuit |
| CN103166471A (en) * | 2011-12-19 | 2013-06-19 | 比亚迪股份有限公司 | Switching power supply, control method of switching power supply and control chip |
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105978535A (en) * | 2016-05-24 | 2016-09-28 | 浙江大华技术股份有限公司 | Low-frequency signal generating circuit and isolated switching power supply |
| CN105978535B (en) * | 2016-05-24 | 2019-02-12 | 浙江大华技术股份有限公司 | A kind of low frequency signal generation circuit and isolation type switching power supply |
| CN107957514A (en) * | 2016-10-14 | 2018-04-24 | 佛山市顺德区美的电热电器制造有限公司 | A kind of zero crossing detection device, method and electric appliance |
| CN109068444A (en) * | 2018-08-17 | 2018-12-21 | 江苏大学 | A kind of single-stage non-isolation type valley fill type no electrolytic capacitor LED drive power and switching method |
| CN109068444B (en) * | 2018-08-17 | 2020-07-31 | 江苏大学 | Single-stage non-isolated electrolytic capacitor L ED driving power supply and switching method |
| CN109600060A (en) * | 2018-12-27 | 2019-04-09 | 广州金升阳科技有限公司 | A kind of modified flyback power supply circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| CN103916020B (en) | 2016-08-24 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN109247081B (en) | Half-bridge resonant converter, circuit using same, and corresponding control method | |
| CN101282079B (en) | System and method for power controller | |
| CN103219901B (en) | AC/DC converter control circuit and apply its AC/DC converter | |
| CN102761265B (en) | Switching power supply controller and method of operating switching power supply | |
| CN106063103B (en) | Burst mode control | |
| CN106787675B (en) | Resonant converter with power factor correction function and controller thereof | |
| CN102263492A (en) | Semiconductor device and power supply device | |
| JP6272691B2 (en) | Amplitude normalization circuit, power supply device and electronic device | |
| CN107682957B (en) | LED drive circuit and its control circuit and control method | |
| Cervera et al. | Resonant switched-capacitor voltage regulator with ideal transient response | |
| CN102629833A (en) | Power supply and apparatus and method for controlling link voltage control switch | |
| CN109120153B (en) | BUCK circuit and switching power supply | |
| CN103916020A (en) | Switching power supply and control circuit thereof | |
| CN109088536B (en) | Active power factor correction circuit and method for improving harmonic waves and driving system | |
| TWI556078B (en) | Dynamic voltage restorer and transient voltage control mechanism thereof | |
| Mali et al. | Simulstion Analysis of Universal Flyback Converter Using Matlab Simulink | |
| US20190181744A1 (en) | Bus converter current ripple reduction | |
| KR20090102948A (en) | Dc/dc converter with multi-output | |
| CN103747600B (en) | High Power Factor is without the method and device of stroboscopic output constant current | |
| CN203722885U (en) | High-power-factor and non-stroboscopic device capable of outputting constant current | |
| Dia et al. | A single phase input switched SEPIC PFC AC-DC converter | |
| CN108347169B (en) | LED constant-current control circuit of flyback conversion topology framework and harmonic distortion optimization method | |
| Dia et al. | A single phase two switch SEPIC power factor corrected rectifier | |
| Ma et al. | Analysis and design for single-phase three-level boost PFC converter with quasi-static model | |
| Bai et al. | Novel adaptive blanking regulation scheme for constant current and constant voltage primary-side controlled flyback converter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| TR01 | Transfer of patent right | ||
| TR01 | Transfer of patent right |
Effective date of registration: 20210714 Address after: 201100 room 803, 8 / F, building 5, No. 7001, Zhongchun Road, Minhang District, Shanghai Patentee after: SHANGHAI LUMIXESS LIGHTING TECHNOLOGY Co. Address before: 213164 room 210, block C, Tianrun science and technology building, Changzhou science and Education City, No. 801, middle Changwu Road, Wujin District, Changzhou City, Jiangsu Province Patentee before: CHANGZHOU LUMIXESS TECHNOLOGY Co.,Ltd. |