CN107863880B - A kind of full digital control method and device of totem PFC - Google Patents
A kind of full digital control method and device of totem PFC Download PDFInfo
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- CN107863880B CN107863880B CN201711213723.XA CN201711213723A CN107863880B CN 107863880 B CN107863880 B CN 107863880B CN 201711213723 A CN201711213723 A CN 201711213723A CN 107863880 B CN107863880 B CN 107863880B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0012—Control circuits using digital or numerical techniques
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0016—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses the full digital control methods and device of a kind of totem PFC, it include: that relevant voltage current information is obtained by sampling module, input voltage virtual value and phase value are calculated after the completion of digital servo-control, error signal is adjusted by outer voltage adjuster and current inner loop adjuster, feedforward compensation is carried out to output duty cycle using duty ratio feedforward.The present invention is by introducing duty ratio feedforward, so that current inner loop adjuster only needs to inhibit small signal disturbance, substantially increase the ability of controller tracking power frequency sinusoidal current, it acquires input voltage zero crossing and carries out digital servo-control, input voltage phase value is obtained by inquiry sine table, it acquires input voltage real value and carries out virtual value calculating, calculated input voltage real value is as input current command value and feedforward duty ratio computing module input value, to eliminate the disturbance of input voltage sampling deviation bring output duty cycle, improve the anti-interference and stability of digital control totem PFC.
Description
Technical field
The invention belongs to PFC fields, more particularly, to the full digital control method of totem PFC a kind of
And device.
Background technique
In order to solve power electronic equipment harmonic pollution caused by power grid, PFC (PFC, Power
Factor Correction) technology developed rapidly.Relative to there is bridge Boost PFC, bridgeless Boost PFC efficiency is more
Height, volume is smaller, but traditional bridgeless Boost PFC common mode interference is strong, and EMI is larger.Totem Boost PFC is as no bridge
A kind of differentiation circuit of Boost PFC, possesses high efficient high power density, many advantages such as low common mode interference, but traditional
Si MOSFET parasitic body diode reverse recovery time is long, and reverse recovery loss is serious, can only operate under CRM mode, input
Current ripples and THD are larger, limit the practical application of totem PFC.Due to the material property of wide bandgap semiconductor, it is based on GaN
MOSFET parasitic body diode characteristic it is more preferable, can effectively solve the above problems, make totem PFC work in ccm mode, because
, with the rapid development of wide bandgap semiconductor manufacturing process, the totem PFC based on GaN MOSFET got back extensively in recent years for this
General concern.
Peripheral circuit needed for traditional PFC simulation controls is more, and design is complicated, and reliability is low, and totem PFC needs to acquire electricity
Inducing current, output voltage, the information such as input voltage polarity, control device is complicated, therefore totem PFC is more suitable for using control mode
Flexibly, the low digital control method of design cost.It is digital control with simulate control compared with, have control lag defect, make total
Word control totem PFC inner ring electric current loop bandwidth relative analog control totem PFC is lower, and controller is caused to track power current ability
Poor, input current THD is larger, and simultaneity factor stability margin is small.By introduce duty ratio feedforward can solve to a certain degree with
Upper problem, however due to calculating one of duty ratio feedforward desired signal from the input real-time voltage directly collected, so that
Final duty ratio output is easy to be interfered, and reduces the stability that system is run under high-power.In addition, PFC is electric
Road generally requires the wide input voltage range for adapting to 85VAC~265VAC, and traditional simulation control is since real-time is good, control ginseng
Number it is adaptable, and if it is digital control still using simulation control control parameter design method, be difficult to reach in full voltage range
To preferably control effect.
Summary of the invention
In view of the drawbacks of the prior art, the purpose of the present invention is to provide the full digital control methods of totem PFC a kind of
And device, it is intended to solve the problems, such as that totem PFC is digital control easily disturbed in the prior art and control effect is bad.
The present invention provides the full digital control methods of totem PFC a kind of, include the following steps:
(1) totem PFC input voltage V is acquiredAC, and work as the input voltage VACZero passage detection signal is exported when zero passage；And
The flipping side edge for capturing the zero passage detection signal, by carrying out digital servo-control, Zhi Daosuo in each input voltage zero-acrross ing moment
State input voltage VACZero crossing and when digitial controller internal sine table zero crossing zero deflection complete digital servo-control；
(2) acquisition input voltage is calculated by carrying out input voltage virtual value inside digitial controller after the completion of locking phase
Virtual value Vrms；And according to the input voltage virtual value VrmsSize select corresponding control parameter to input current waveform and
Output voltage size is controlled；
(3) output voltage V is acquiredDC, and by the output voltage VDCWith the output order voltage V of converter settingDC-ref
Error signal V is obtained after making the differenceerr, the error signal VerrInput power instruction is obtained after the correction of outer voltage adjuster
PIN-ref；
(4) pass through the discrete sine table stored in advance inside inquiry controller after the completion of locking phase and obtain present input voltage
Phase value Vphase_tab, and according to present input voltage phase value Vphase_tabWith the input voltage virtual value VrmsIt is inputted
Voltage real value VINAC；
(5) inverse 1/ of input voltage virtual value square is obtained by the division table stored in advance inside inquiry controller
V2 rms, and according to the inverse 1/V2 rms, the input voltage real value VINACP is instructed with the input powerIN-refIt obtains defeated
Enter current instruction value iL-ref；
(6) input current i is acquiredL, and by the input current iLWith the input current command value iL-refIt is obtained after making the difference
Obtain error signal Ierr, the error signal IerrBy current inner loop adjuster correction after obtain output duty cycle d1, and will before
Present duty ratio d2 multiplied by after being added after proportionality coefficient km with the output duty cycle d1 acquisition final output pwm signal duty ratio d,
The driving signal for driving totem PFC GaN MOSFET bridge arm is exported according to the duty ratio d.
Wherein, the maximum value that proportionality coefficient km can be got under the premise of stablizing for guarantee converter, proportionality coefficient km's
Value range is 0.9~0.95.
Further, in step (2), the voltage effective valueWherein, M is calculating time
Number, N are the cumulative points of half of power frequency period,T is power frequency period, fswitchFor converter switches frequency.
Further, in step (2), if input voltage virtual value in 85V~165V, selects low voltage control ginseng
Number, that is, the outer voltage compensator parameter kvp and kvi being suitable under low input, current inner loop compensator parameter kip and
Kii, if input voltage virtual value in 165~265V, selects high voltage control parameter, that is, the voltage being suitable under high input voltage
Outer ring compensator parameter kvp and kvi, current inner loop compensator parameter kip and kii.
Further, in step (4), input voltage real value VINAC=Vphase_tab*Vrms。
Further, in step (5), input current command value
Further, in step (6), feedover duty ratio in real time
The present invention also provides the full-digital control devices of totem PFC a kind of, comprising: output voltage monitoring modular is used
In acquisition totem PFC DC output voltage VDC；Input voltage monitoring modular, for acquiring totem PFC input voltage VACAnd judge
Input voltage VACPolarity；Input current monitoring modular, for acquiring totem PFC input current iL；And digitial controller, it uses
In realizing digital servo-control, input voltage virtual value and real value are calculated, and according to input voltage VAC, output voltage VDCAnd input
Electric current iLWhat is obtained is used to drive the driving signal of totem PFC GaN MOSFET bridge arm.
Further, the digitial controller includes: PLL module, input voltage virtual value computing module, input voltage
Phase calculation module, feedover duty ratio computing module, PWM output module, outer voltage adjuster, and current inner loop adjuster is put down
Side seeks reverse mould block, the first summation module, the second summation module, third summation module, the first multiplier module, the second multiplier module and
Third multiplier module；The input terminal of PLL module is used to be connected to the output end of input voltage monitoring modular, input voltage virtual value
The input terminal of computing module is connected to the first output end of PLL module, and the input terminal of input voltage phase computing module is connected to
The second output terminal of PLL module, the first input end of the second multiplier module are connected to the defeated of input voltage virtual value computing module
Outlet, the second input terminal of the second multiplier module are connected to the output end of input voltage phase computing module, square seek reverse mould block
Input terminal be connected to the output end of input voltage virtual value computing module, the first input end of the first summation module is for receiving
Output order voltage VDC-ref, it is second defeated to be used to be connected to output voltage monitoring modular the second input terminal of the first summation module
Outlet, the input terminal of outer voltage adjuster are connected to the output end of the first summation module, the first input of the first multiplier module
End is connected to the output end of outer voltage adjuster, and the second input terminal of the first multiplier module, which is connected to, square seeks the defeated of reverse mould block
Outlet, the first input end of third multiplier module are connected to the output end of the first multiplier module, and the second of third multiplier module is defeated
Enter the output end that end is connected to the second multiplier module, the first input end of the second summation module is connected to the defeated of third multiplier module
Outlet, the second input terminal of the second summation module are used to be connected to the output end of input current monitoring modular, and current inner loop is adjusted
The input terminal of device is connected to the output end of the second summation module, and the first input end of third summation module is connected to current inner loop tune
The output end of device is saved, the second input terminal of third summation module is connected to the output end of the feedforward duty ratio computing module, PWM
The input terminal of output module is connected to the output end of third summation module, and the output end of PWM output module is used for output driving figure
Rise the driving signal of PFC GaN MOSFET bridge arm；The first input end of feedforward duty ratio computing module is connected to the second multiplication modulo
Second input terminal of the output end of block, feedforward duty ratio computing module is used to be connected to the output end of output voltage monitoring modular.
The present invention, so that current inner loop adjuster only needs to inhibit small signal disturbance, is mentioned significantly by introducing duty ratio feedforward
The high ability of controller tracking power frequency sinusoidal current, solves the problems, such as that digital control totem PFC control effect is bad；Acquisition
Input voltage zero crossing carries out digital servo-control, obtains input voltage phase value by inquiry sine table, acquisition input voltage is real-time
Value carries out virtual value calculating, and calculated input voltage real value is as input current command value and feedforward duty ratio meter
Module input value is calculated, to eliminate the disturbance of input voltage sampling deviation bring output duty cycle, improves digital control figure
Rise the anti-interference and stability of PFC.
Detailed description of the invention
Fig. 1 is totem PFC main circuit topological structure schematic diagram；
Fig. 2 is using the digital control totem PFC controling device structure diagram of the present invention；
Fig. 3 is the flow chart of totem PFC full digital control method of the present invention；
Fig. 4 is the control block diagram of totem PFC full digital control method of the present invention；
In Fig. 5, (a) is that the totem PFC for the control method control that the prior art provides is inputted under high voltage and high power occasion
Current waveform expanded view, input voltage waveform and output voltage waveform；It (b) is the figure of control method provided by the invention control
Rise PFC input current waveform expanded view, input voltage waveform and output voltage waveform under high voltage and high power occasion.
Specific embodiment
In order to make the objectives, technical solutions, and advantages of the present invention clearer, with reference to the accompanying drawings and embodiments, right
The present invention is further elaborated.It should be appreciated that the specific embodiments described herein are merely illustrative of the present invention, and
It is not used in the restriction present invention.
The present invention provides the full digital control methods of totem PFC a kind of, reduce input current THD, improve number
The anti-interference degree of PFC.
This method includes the following steps:
(1) outer voltage control method:
(A) totem PFC input ac voltage, when monitoring totem PFC input ac voltage zero passage, monitoring modular are monitored
Zero passage detection signal is issued, digitial controller captures zero passage detection signal flipping side edge, carries out digital servo-control；
(B) totem PFC input ac voltage is monitored, input voltage real value V is acquiredAC, counted in digitial controller
Calculation obtains input voltage virtual value Vrms, and corresponding control parameter is selected according to input voltage valid value range, if input voltage
For low pressure, then outer voltage adjuster and current inner loop adjuster select low voltage control parameter, if input voltage is high pressure, electricity
Outer ring adjuster and current inner loop adjuster is pressed to select high voltage control parameter；
(C) monitoring totem PFC exports busbar voltage VDC, with reference voltage VDC-refIt makes the difference to obtain command voltage VDC-refWith work as
Preceding actual bus voltage VDCVoltage error signal Verr, voltage error signal VerrIt is obtained after the correction of outer voltage adjuster
Input power instructs PIN-ref；
(2) current inner loop control method:
(D) after the completion of locking phase, obtain present input voltage phase value by tabling look-up, and with input voltage virtual value VrmsPhase
Multiply, obtains calculated input voltage real value VINAC；
(E) pass through the 1/V reciprocal of computation of table lookup input voltage virtual value square2 rms, and it is real with calculated input voltage
Duration VINAC, input power instruction PIN-refIt is multiplied, obtains input current command value iL-ref；
(F) input current i is monitoredL, with input current command value iL-refIt makes the difference, obtains error signal Ierr, through in overcurrent
Output pwm signal duty ratio d1 is obtained after the correction of ring adjuster；
Shown in Boost circuit input and output voltage steady state relation formula such as following formula (1):
It is duty ratio D such as following formula (2) institute required for meeting output voltage stabilization according to (1) formula available stable state lower any time
Show:(2) formula is applied in circuit of power factor correction, feedforward duty ratio d2 such as following formula is obtained
(3) shown in:
(G) calculated input voltage V is utilizedINACFeedforward duty ratio d2 is calculated, it is dry to eliminate input voltage sampling bring
It disturbs, feedforward duty ratio d2 is added with current inner loop adjuster output duty cycle d1, obtains final output pwm signal duty ratio d,
And the driving signal S1, S2 for driving totem PFC GaN MOSFET bridge arm are obtained by PWM module.
As shown in Fig. 2, the embodiment of the invention also provides a set of totem PFC suitable for above-mentioned control method to control dress
It sets, comprising:
Output voltage monitoring modular, for acquiring totem PFC DC output voltage；
Input voltage monitoring modular, for acquiring input voltage and the judgement of input voltage polarity；
Input current monitoring modular, for acquiring totem PFC input inductive current；
Digitial controller is used for digital servo-control, calculates input voltage virtual value and real value, and generate by above-mentioned control
The pwm signal that method is calculated.
Wherein, digitial controller includes: PLL module 8, input voltage virtual value computing module 9, input voltage phase calculating
Module 10, feedover duty ratio computing module 18, PWM output module 19, outer voltage adjuster 4, and current inner loop adjuster 16 is put down
Side seeks reverse mould block 20, and the first summation module 3, the second summation module 15, third summation module 17, the first multiplier module 5, second multiply
Method module 11 and third multiplier module 12；The input terminal of PLL module 8 is used to be connected to the output end of input voltage monitoring modular 7,
The input terminal of input voltage virtual value computing module 9 is connected to the first output end of PLL module 8, and input voltage phase calculates mould
The input terminal of block 10 is connected to the second output terminal of PLL module 8, and the first input end of the second multiplier module 11 is connected to input electricity
It is pressed with the output end of valid value computing module 9, the second input terminal of the second multiplier module 11 is connected to input voltage phase and calculates mould
The output end of block 10 square asks the input terminal of reverse mould block 20 to be connected to the output end of input voltage virtual value computing module 9, and first
The first input end of summation module 3 is for receiving output order voltage VDC-ref, the second input terminal of the first summation module 3 is used for
It is connected to the second output terminal of output voltage monitoring modular 2, the input terminal of outer voltage adjuster 4 is connected to the first summation module
The first input end of 3 output end, the first multiplier module 5 is connected to the output end of outer voltage adjuster 4, the first multiplier module
5 the second input terminal is connected to square output end for seeking reverse mould block 20, and the first input end of third multiplier module 12 is connected to
The output end of one multiplier module 5, the second input terminal of third multiplier module 12 are connected to the output end of the second multiplier module 11, the
The first input end of two summation modules 15 is connected to the output end of third multiplier module 12, the second input of the second summation module 15
The output end for being connected to input current monitoring modular 14 is held, the input terminal of current inner loop adjuster 16 is connected to the second summation
The output end of module 15, the first input end of third summation module 17 are connected to the output end of current inner loop adjuster 16, third
Second input terminal of summation module 17 is connected to the output end of feedforward duty ratio computing module 18, the input of PWM output module 19
End is connected to the output end of third summation module 17, and the output end of PWM output module 19 is used for output driving totem PFC GaN
The driving signal of MOSFET bridge arm；The first input end of feedforward duty ratio computing module 18 is connected to the defeated of the second multiplier module 11
Second input terminal of outlet, feedforward duty ratio computing module 18 is used to be connected to the output end of output voltage monitoring modular 2.
The present invention, so that current inner loop adjuster only needs to inhibit small signal disturbance, is mentioned significantly by introducing duty ratio feedforward
The high ability of controller tracking power frequency sinusoidal current, solves the problems, such as that digital control totem PFC control effect is bad；Acquisition
Input voltage zero crossing carries out digital servo-control, obtains input voltage phase value by inquiry sine table, acquisition input voltage is real-time
Value carries out virtual value calculating, and calculated input voltage real value is as input current command value and feedforward duty ratio meter
Module input value is calculated, to eliminate the disturbance of input voltage sampling deviation bring output duty cycle, improves digital control figure
Rise the anti-interference and stability of PFC.
This example 1 is a totem PFC control process using control method of the present invention, technical parameter used by this example
As follows: input filter inductance selects iron nickel powder core magnet ring, and 13 strands of diameter 0.51mm enameled wire is simultaneously formed around coiling, static
Inductance 750uH@0A；Switching tube selects the TPH3207WS of Transphormusa company production, voltage rating 650V, rated current
50A；Bus capacitor selects four capacitances in parallel with the electrolytic capacitor that two capacitances are 270uF for the electrolytic capacitor of 330uF, pressure resistance
It is 450V, total bus capacitor is 1620uF；Nominal input voltage is 220V, and specified busbar voltage is 390V, rated output function
Rate is 3300W, switching frequency fswitch40kHz；Under the above technical parameter, according to experiment and simulation result, input voltage is obtained
Outer voltage compensator parameter is kvp=12, kvi=0.018375, current inner loop compensator ginseng when within the scope of 85V~165V
Number is kip=0.015, and kii=0.00075, input voltage outer voltage compensator parameter in 165V~265V is kvp=
23.5, kvi=0.018375, current inner loop compensator parameter is kip=0.04449, kii=0.000489.
Present invention will now be described in detail with reference to the accompanying drawings..
The totem PFC main circuit topological structure of control method control of the present invention is as shown in Figure 1, single phase alternating current power supply AC mono-
End passes through boost inductance L and Q1、Q2The MOSFET bridge arm midpoint GaN of composition is connected, the other end and D1、D2The diode bridge of composition
Arm midpoint is connected, and DC side output end is parallel with filter capacitor COWith DC load resistance RL, it is based on this circuit topology, foundation is adopted
With the control device structure of control method of the present invention as shown in Fig. 2, control device includes: input voltage monitoring modular 7, input electricity
Flow monitoring modular 10, output voltage monitoring modular 2 and digitial controller, wherein digitial controller includes: PLL module 8, input
Voltage effective value computing module 9, input voltage phase computing module 10, feedover duty ratio computing module 18, PWM output module
19, outer voltage adjuster 4, current inner loop adjuster 16 square asks reverse mould block 20, the first summation module 3, the second summation module
15, third summation module 17, the first multiplier module 5, the second multiplier module 11, third multiplier module 12.Input voltage monitors mould
Block 7, input current monitoring modular 10 and output voltage monitoring modular 2 acquire input voltage, input current and output voltage respectively
After be sent into digitial controller；PLL module 8 obtains input voltage zero passage information, realizes digital servo-control function；Input voltage virtual value
Computing module 9 square asks reverse mould block 20 to carry out input voltage virtual value flat by accumulation calculating output-input voltage virtual value
Fang Houqiu derivative action；Input voltage phase value is calculated after obtaining PLL module information in input voltage phase computing module 10；
Input voltage phase computing module output valve is multiplied work by the second multiplier 11 with input voltage virtual value computing module output valve
For the duty cycle module input signal that feedovers；First summation module 3 makes the difference output voltage instruction value and output voltage real value
To error signal, compensation is adjusted to error signal in voltage regulator；First multiplier module 5 and third multiplier module 12 will be electric
Pressure outer ring regulator output signal square asks down module output signal and 11 output signal of the second multiplier to carry out multiplying,
Obtain input current reference signal；Input current reference signal and input current real value are made the difference acquisition by the second summation module 15
Compensation is adjusted to current error signal in input current error signal, current inner loop adjuster, exports forward path duty ratio
d1；The duty cycle signals that feedover obtain input voltage signal from the second multiplier 11 and from output voltage monitoring modulars
Feedforward duty ratio d2 is calculated in output voltage signal；Third summation module 17 by forward path duty ratio d1 and feedforward duty
PWM output module, output drive signal S are sent into after being added than d2Q1And SQ2, Q1 and Q2 are controlled.Itd is proposed control device
Then corresponding control block diagram passes through accumulation calculating as shown in figure 4, by digital servo-control and table look-up and obtain input voltage phase value
Input voltage virtual value is obtained, then the two multiplication is obtained into the input voltage real value being calculated, by output voltage reference value
It makes the difference to obtain output voltage error signal with output voltage real value, benefit is adjusted by the outer voltage adjuster of PI form
Repay, obtain the inverse of input voltage virtual value square by way of tabling look-up, and with the input voltage real value being calculated and
Outer voltage regulator output signal is multiplied to obtain input current reference value, then by the current inner loop adjuster of PI form into
Row adjusts compensation and obtains forward path duty ratio d1, then obtains feedforward duty ratio d2 by feedforward duty ratio calculation formula, and preceding
It is added to obtain final output duty ratio to channel duty ratio d1.
Its corresponding control method flow chart is as shown in Figure 3, the specific steps are as follows:
(1) outer voltage control method:
(1.1) totem PFC input voltage V is acquired using input voltage monitoring modularAC, when monitoring input voltage zero passage
When, input voltage measurement module issues zero passage detection signal, and digitial controller captures the overturning of zero passage detection signal by CAP module
Edge carries out digital servo-control in each input voltage zero-acrross ing moment by phaselocked loop, until the input voltage zero crossing detected
200 power frequency period zero deflections are continued to exceed with digitial controller internal sine table zero crossing, then digital servo-control is completed；
(1.2) after the completion of locking phase, the calculating of input voltage virtual value is carried out inside digitial controller, obtaining input voltage has
Valid value Vrms, controlled from traditional analog and input voltage virtual value carry out to classification is different, it is of the invention in full digital control method can
To calculate output voltage virtual value in real time, calculation method is as follows:
Input voltage real value V is acquired using input voltage monitoring modularAC, will each collected input voltage real value
VACCumulative, the cumulative points of half of power frequency period areT is power frequency period, fswitchFor converter switches frequency, N
For cumulative points, after being added to half period, is converted by the mathematical relationship of virtual value and accumulated value, obtain single meter
Virtual value that continuous 20 times are calculated is carried out average calculating operation and obtains finally entering voltage to have by the input voltage virtual value of calculating
Valid value, shown in expression formula such as formula (4):
(1.3) after obtaining input voltage virtual value by above-mentioned effective value calculating method, according to the input electricity being calculated
It is pressed with valid value size and selects corresponding control parameter, if input voltage virtual value in 85V~165V, selects low voltage control ginseng
Number, i.e., suitable for the outer voltage compensator parameter kvp=12 of low input, kvi=0.018375, current inner loop compensator
Parameter kip=0.015, kii=0.00075, if input voltage virtual value in 165~265V, selects high voltage control parameter, i.e.,
Suitable for the outer voltage compensator parameter kvp=23.5 of high input voltage, kvi=0.018375, current inner loop compensator ginseng
Number kip=0.04449, kii=0.000489；
(1.4) output voltage V is acquired using output voltage monitoring modularDC, with output order voltage VDC-refIt makes the difference, obtains
Error signal Verr, input power instruction P is obtained after the correction of outer voltage adjusterIN-ref；
(2) current inner loop control method:
(2.1) after the completion of locking phase, current input electricity is obtained by the discrete sine table stored in advance inside inquiry controller
Press phase value Vphase_tab, and with input voltage virtual value VrmsIt is multiplied, obtains calculated input voltage real value VINAC, table
Up to shown in formula such as formula (5)；VINAC=Vphase_tab*Vrms……(5)；
(2.2) inverse 1/ of input voltage virtual value square is calculated by the division table stored in advance inside inquiry controller
V2 rms, and with calculated input voltage real value VINAC, input power instruction PIN-refIt is multiplied, obtains input current command value
iL-ref, shown in expression formula such as formula (6)；
(2.3) input current i is acquired using input current monitoring modularL, with input current command value iL-refIt makes the difference, obtains
Error signal Ierr, output pwm signal duty ratio d1 is obtained after the correction of current inner loop adjuster, reality is calculated by formula (3)
When feedover duty ratio d2, will feedforward duty ratio d2 multiplied by proportionality coefficient km, km is to guarantee to take under the premise of converter stabilization
Then the maximum value arrived, generally 0.9~0.95 are added with current inner loop adjuster output duty cycle d1, obtain final output
Pwm signal duty ratio d, and the driving signal S1 for driving totem PFC GaN MOSFET bridge arm is obtained by PWM module,
S2。
For the control performance for verifying control method of the present invention, this example 2 controls simulation for direct described in the prior art
Method processed be transplanted to it is digital control, acquisition input voltage real value as input current instruction, merely with current inner loop bandwidth with
This method of track input current instructional waveform is compared with control method used by example 1, as previously described in technical parameter
Totem pfc circuit on be respectively controlled, and using the U.S. Tektronix company production model TPS024B oscillography
Device acquires input current waveform under different control methods, output voltage waveforms and input voltage waveform such as Fig. 5 (a), (b) institute respectively
Show.Comparative diagram 5 (a), (b) are it can be seen that under same technique parameter, according to control method described in the prior art, due to
Digital delay bring influences so that current inner loop bandwidth is limited, and tracking power current waveform ability is not as good as simulation control, input
Current zero-crossing point nearby distort it is very big, input current due to directly with collected input voltage waveform be instruction, current waveform
There are many burrs, measuring input current THD using the power analyzer of the model 3390 of HIOKI company production is
18.59%；After full digital control method of the present invention, input current waveform has good improvement, can be good at
Input voltage waveform is tracked, measuring input current THD using the power analyzer of the model 3390 of HIOKI company production is
2.53%.
According to experimental result, it can be clearly seen that, full digital control method control effect provided by the invention is better than existing
Directly transplanting simulation control method, can be substantially reduced input current THD, eliminate input voltage sampling interference, it is very suitable
The occasion more demanding to input current THD for such as Vehicular charger etc..
As it will be easily appreciated by one skilled in the art that the foregoing is merely illustrative of the preferred embodiments of the present invention, not to
The limitation present invention, any modifications, equivalent substitutions and improvements made within the spirit and principles of the present invention should all include
Within protection scope of the present invention.
Claims (9)
1. a kind of full digital control method of totem PFC, which is characterized in that include the following steps:
(1) totem PFC input voltage V is acquiredAC, and work as the input voltage VACZero passage detection signal is exported when zero passage；And it catches
The flipping side edge for obtaining the zero passage detection signal, by carrying out digital servo-control in each input voltage zero-acrross ing moment, until described
Input voltage VACZero crossing and when digitial controller internal sine table zero crossing zero deflection complete digital servo-control；
(2) effective by carrying out input voltage virtual value calculating acquisition input voltage inside digitial controller after the completion of locking phase
Value Vrms；And according to the input voltage virtual value VrmsSize select corresponding control parameter to input current waveform and output
Voltage swing is controlled；
(3) output voltage V is acquiredDC, and by the output voltage VDCWith the output order voltage V of converter settingDC-refAfter making the difference
Obtain error signal Verr, the error signal VerrInput power instruction P is obtained after the correction of outer voltage adjusterIN-ref；
(4) pass through the discrete sine table stored in advance inside inquiry controller after the completion of locking phase and obtain present input voltage phase
Value Vphase_tab, and according to present input voltage phase value Vphase_tabWith the input voltage virtual value VrmsObtain input voltage
Real value VINAC；
(5) 1/V reciprocal of input voltage virtual value square is obtained by the division table stored in advance inside inquiry controller2 rms, and
According to the inverse 1/V2 rms, the input voltage real value VINACP is instructed with the input powerIN-refInput current is obtained to refer to
Enable value iL-ref；
(6) input current i is acquiredL, and by the input current iLWith the input current command value iL-refError is obtained after making the difference
Signal Ierr, the error signal IerrOutput duty cycle d1, and the duty that will feedover are obtained after the correction of current inner loop adjuster
Than d2 multiplied by final output pwm signal duty ratio d is obtained after being added after proportionality coefficient km with the output duty cycle d1, according to institute
It states duty ratio d and exports driving signal for driving totem PFC GaN MOSFET bridge arm.
2. full digital control method as described in claim 1, which is characterized in that the proportionality coefficient km is to guarantee that converter is steady
The maximum value that can be got under the premise of fixed, the value of the proportionality coefficient km are 0.9~0.95.
3. full digital control method as described in claim 1, which is characterized in that in step (2), the voltage effective valueWherein, M is calculation times, and N is the cumulative points in half frequency period,T is power frequency week
Phase, fswitchFor converter switches frequency.
4. full digital control method as described in any one of claims 1-3, which is characterized in that in step (2), if input electricity
Valid value is pressed in 85V~165V, selects low voltage control parameter, if input voltage virtual value in 165~265V, selects high pressure
Control parameter.
5. full digital control method as described in any one of claims 1-3, which is characterized in that in step (4), input voltage
Real value VINAC=Vphase_tab*Vrms。
6. full digital control method as described in any one of claims 1-3, which is characterized in that in step (5), input current
Instruction value
7. full digital control method as described in any one of claims 1-3, which is characterized in that in step (6), feedover in real time
Duty ratio
8. a kind of full-digital control device for the totem PFC for realizing full digital control method described in claim 1, feature
It is, comprising:
Output voltage monitoring modular (2), for acquiring totem PFC DC output voltage VDC；
Input voltage monitoring modular (7), for acquiring totem PFC input voltage VACAnd judge input voltage VACPolarity；
Input current monitoring modular (14), for acquiring totem PFC input current iL；And
Digitial controller calculates input voltage virtual value and real value for realizing digital servo-control, and according to input voltage VAC,
Output voltage VDCWith input current iLWhat is obtained is used to drive the driving signal of totem PFCGaN MOSFET bridge arm.
9. full-digital control device as claimed in claim 8, which is characterized in that the digitial controller includes: PLL module
(8), input voltage virtual value computing module (9), input voltage phase computing module (10), feedover duty ratio computing module
(18), PWM output module (19), outer voltage adjuster (4), current inner loop adjuster (16) square are asked reverse mould block (20), and
One summation module (3), the second summation module (15), third summation module (17), the first multiplier module (5), the second multiplier module
(11) and third multiplier module (12)；
The input terminal of the PLL module (8) is used to be connected to the output end of the input voltage monitoring modular (7), the input
The input terminal of voltage effective value computing module (9) is connected to the first output end of the PLL module (8), the input voltage phase
The input terminal of position computing module (10) is connected to the second output terminal of the PLL module (8), second multiplier module (11)
First input end is connected to the output end of the input voltage virtual value computing module (9), second multiplier module (11)
Second input terminal is connected to the output end of the input voltage phase computing module (10), and described square is sought the defeated of reverse mould block (20)
Enter the output end that end is connected to the input voltage virtual value computing module (9), the first input of first summation module (3)
End is for receiving output order voltage VDC-ref, the second input terminal of first summation module (3) is for being connected to the output
The second output terminal of voltage monitoring module (2), the input terminal of the outer voltage adjuster (4) are connected to the first summation mould
The output end of block (3), the first input end of first multiplier module (5) are connected to the defeated of the outer voltage adjuster (4)
Outlet, the second input terminal of first multiplier module (5) are connected to the described square of output end for asking reverse mould block (20), and described the
The first input end of three multiplier modules (12) is connected to the output end of first multiplier module (5), the third multiplier module
(12) the second input terminal is connected to the output end of second multiplier module (11), and the first of second summation module (15)
Input terminal is connected to the output end of the third multiplier module (12), and the second input terminal of second summation module (15) is used for
It is connected to the output end of the input current monitoring modular (14), the input terminal of the current inner loop adjuster (16) is connected to institute
The output end of the second summation module (15) is stated, the first input end of the third summation module (17) is connected to the current inner loop
The output end of adjuster (16), the second input terminal of the third summation module (17) are connected to the feedforward duty ratio and calculate mould
The output end of block (18), the input terminal of the PWM output module (19) are connected to the output end of the third summation module (17),
The output end of the PWM output module (19) is used for the driving signal of output driving totem PFC GaN MOSFET bridge arm；Institute
The first input end for stating feedforward duty ratio computing module (18) is connected to the output end of second multiplier module (11), before described
Second input terminal of feedback duty ratio computing module (18) is used to be connected to the first output of the output voltage monitoring modular (2)
End.
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| CN112803750B (en) * | 2021-01-29 | 2022-07-05 | 上海瞻芯电子科技有限公司 | Power factor correction device and power supply |
| CN113114035A (en) * | 2021-04-15 | 2021-07-13 | 浙江奉天电子有限公司 | Digital-control bidirectional PFC system |
| CN113364264B (en) * | 2021-05-21 | 2023-03-24 | 珠海格力电器股份有限公司 | PFC topological circuit and control method thereof |
| CN113394965B (en) * | 2021-07-23 | 2022-12-30 | 杭州电子科技大学 | Digital control totem pole PFC voltage zero crossing distortion control device and method |
| CN115622439B (en) * | 2022-12-19 | 2023-04-14 | 宁波芯合为一电子科技有限公司 | Pulse power supply control method with PFC circuit and pulse power supply |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104883060A (en) * | 2015-05-26 | 2015-09-02 | 华南理工大学 | Dual independent current-loop digital control method facing interleaving parallel PFC |
| CN105226932A (en) * | 2015-10-21 | 2016-01-06 | 上海大学 | High efficiency circuit of power factor correction topological structure and control method thereof |
| CN106100373A (en) * | 2016-07-04 | 2016-11-09 | 南京航空航天大学 | The high frequency CRM boost PFC changer of adaptive optimization THD |
| CN106452046A (en) * | 2016-10-13 | 2017-02-22 | 广州视源电子科技股份有限公司 | Control method and device for switch tube of PFC circuit |
| CN107257202A (en) * | 2016-11-17 | 2017-10-17 | 南京航空航天大学 | Optimal control method containing active energy-storage units type BoostPFC |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JP6080345B2 (en) * | 2011-09-27 | 2017-02-15 | ミネベアミツミ株式会社 | Switching power supply and AC waveform generation method in switching power supply |
| US9812951B2 (en) * | 2015-05-21 | 2017-11-07 | Pacific Power Source, Inc. | Advanced PFC voltage controller |
-
2017
- 2017-11-28 CN CN201711213723.XA patent/CN107863880B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104883060A (en) * | 2015-05-26 | 2015-09-02 | 华南理工大学 | Dual independent current-loop digital control method facing interleaving parallel PFC |
| CN105226932A (en) * | 2015-10-21 | 2016-01-06 | 上海大学 | High efficiency circuit of power factor correction topological structure and control method thereof |
| CN106100373A (en) * | 2016-07-04 | 2016-11-09 | 南京航空航天大学 | The high frequency CRM boost PFC changer of adaptive optimization THD |
| CN106452046A (en) * | 2016-10-13 | 2017-02-22 | 广州视源电子科技股份有限公司 | Control method and device for switch tube of PFC circuit |
| CN107257202A (en) * | 2016-11-17 | 2017-10-17 | 南京航空航天大学 | Optimal control method containing active energy-storage units type BoostPFC |
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Effective date of registration: 20221031 Address after: 430000 Floor 2, Building 1, Nanhua Industrial Park, Science Park, Wuhan University of Technology, Donghu New Technology Development Zone, Wuhan City, Hubei Province Patentee after: Wuhan Matrix Energy Technology Co.,Ltd. Address before: 430074 Hubei Province, Wuhan city Hongshan District Luoyu Road No. 1037 Patentee before: HUAZHONG University OF SCIENCE AND TECHNOLOGY |