CN107863880A - A kind of totem PFC full digital control method and device - Google Patents
A kind of totem PFC full digital control method and device Download PDFInfo
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- CN107863880A CN107863880A CN201711213723.XA CN201711213723A CN107863880A CN 107863880 A CN107863880 A CN 107863880A CN 201711213723 A CN201711213723 A CN 201711213723A CN 107863880 A CN107863880 A CN 107863880A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0012—Control circuits using digital or numerical techniques
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0003—Details of control, feedback or regulation circuits
- H02M1/0016—Control circuits providing compensation of output voltage deviations using feedforward of disturbance parameters
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
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Abstract
The invention discloses a kind of totem PFC full digital control method and device, including：Relevant voltage current information is obtained by sampling module, input voltage virtual value and phase value are calculated after the completion of digital servo-control, error signal is adjusted by outer voltage adjuster and current inner loop adjuster, feedforward compensation is carried out to output duty cycle using dutycycle feedforward.The present invention is feedovered by introducing dutycycle, so that current inner loop adjuster only needs to suppress small-signal disturbance, substantially increase the ability of controller tracking power frequency sinusoidal current, gather input voltage zero crossing and carry out digital servo-control, input voltage phase value is obtained by inquiring about sine table, gather input voltage instantaneous value and carry out virtual value calculating, calculated input voltage instantaneous value is as input current command value and feedforward dutycycle computing module input value, so as to eliminate the output duty cycle disturbance that input voltage sampling deviation is brought, improve digital control totem PFC anti-interference and stability.
Description
Technical field
The invention belongs to PFC field, more particularly, to a kind of totem PFC full digital control method
And device.
Background technology
In order to solve power electronic equipment harmonic pollution to caused by power network, PFC (PFC, Power
Factor Correction) technology developed rapidly.Relative to having bridge Boost PFC, bridgeless Boost PFC efficiency more
Height, volume is smaller, but traditional bridgeless Boost PFC common mode disturbances are strong, and EMI is larger.Totem Boost PFC are used as without bridge
The a kind of of Boost PFC develops circuit, possesses many advantages such as high efficient high power density, low common mode disturbances, but traditional
Si MOSFET parasitic body diode reverse recovery times are grown, and reverse recovery loss is serious, can only operate under CRM patterns, input
Current ripples and THD are larger, limit totem PFC practical application.Due to the material property of wide bandgap semiconductor, based on GaN
MOSFET parasitic body diode characteristics it is more preferable, can effectively solve the above problems, make totem PFC work in ccm mode, because
This is developed rapidly with wide bandgap semiconductor manufacturing process, and the totem PFC based on GaN MOSFET has got back extensively in recent years
General concern.
Peripheral circuit needed for traditional PFC simulation controls is more, and complex designing, reliability is low, and totem PFC needs to gather electricity
The information such as inducing current, output voltage, input voltage polarity, control device is complicated, therefore totem PFC is more suitable for using control mode
Flexibly, the low digital control method of design cost.It is digital control compared with simulating control, have control lag the defects of so that number
Word control totem PFC inner ring electric current loop bandwidths relative analog control totem PFC is relatively low, causes controller to track power current ability
Poor, input current THD is larger, and simultaneity factor stability margin is small.By introduce dutycycle feedforward can solve to a certain degree with
Upper problem, one of desired signal is feedovered from the input real-time voltage directly collected yet with dutycycle is calculated so that
Final dutycycle output is easily interfered, and reduces the stability that system is run under high-power.In addition, PFC is electric
Road generally requires the wide input voltage range for adapting to 85VAC~265VAC, and traditional simulation control is because real-time is good, control ginseng
Number strong adaptabilities, and if it is digital control still using simulation control control parameter design method, it is difficult to be reached in full voltage range
To preferably control effect.
The content of the invention
The defects of for prior art, it is an object of the invention to provide a kind of totem PFC full digital control method
And device, it is intended to solve the problems, such as that totem PFC is digital control easily disturbed in the prior art and control effect is bad.
The invention provides a kind of totem PFC full digital control method, comprise the steps：
(1) totem PFC input voltages V is gatheredAC, and work as the input voltage VACZero passage detection signal is exported during zero passage；And
The flipping side edge of the zero passage detection signal is captured, by carrying out digital servo-control, Zhi Daosuo in each input voltage zero-acrross ing moment
State input voltage VACZero crossing and digitial controller internal sine table zero crossing zero deflection when complete digital servo-control；
(2) acquisition input voltage is calculated by carrying out input voltage virtual value inside digitial controller after the completion of phase is locked
Virtual value Vrms；And according to the input voltage virtual value VrmsSize select corresponding control parameter to input current waveform and
Output voltage size is controlled；
(3) output voltage V is gatheredDC, and by the output voltage VDCWith the output order voltage V of converter settingDC-ref
Error signal V is obtained after making the differenceerr, the error signal VerrInput power instruction is obtained after the correction of outer voltage adjuster
PIN-ref；
(4) the discrete sine table stored in advance inside controller after the completion of phase is locked by inquiring about obtains present input voltage
Phase value Vphase_tab, and according to present input voltage phase value Vphase_tabWith the input voltage virtual value VrmsInputted
Voltage instantaneous value VINAC；
(5) division table stored in advance inside controller by inquiring about obtains the inverse 1/ of input voltage virtual value square
V2 rms, and according to the 1/V reciprocal2 rms, the input voltage instantaneous value VINACP is instructed with the input powerIN-refObtain defeated
Enter current instruction value iL-ref；
(6) input current i is gatheredL, and by the input current iLWith the input current command value iL-refObtained after making the difference
Obtain error signal Ierr, the error signal IerrOutput duty cycle d1 is obtained after the correction of current inner loop adjuster, and by before
Feedback dutycycle d2 is multiplied by after proportionality coefficient km is added with the output duty cycle d1 after acquisition final output pwm signal dutycycle d,
Drive signal for driving totem PFC GaN MOSFET bridge arms is exported according to the dutycycle d.
Wherein, the maximum that can be got on the premise of proportionality coefficient km is ensures converter stabilization, proportionality coefficient km's
Span is 0.9~0.95.
Further, in step (2), the voltage effective valueWherein, M is secondary to calculate
Number, N are the cumulative points of half of power frequency period,T is power frequency period, fswitchFor converter switches frequency.
Further, in step (2), if input voltage virtual value in 85V~165V, selects low voltage control ginseng
Number, i.e., suitable for the outer voltage compensator parameter kvp and kvi under low input, current inner loop compensator parameter kip and
Kii, if input voltage virtual value in 165~265V, selects high voltage control parameter, i.e., suitable for the voltage under high input voltage
Outer shroud compensator parameter kvp and kvi, current inner loop compensator parameter kip and kii.
Further, in step (4), input voltage instantaneous value VINAC=Vphase_tab*Vrms。
Further, in step (5), input current command value
Further, in step (6), feedover dutycycle in real time
Present invention also offers a kind of totem PFC full-digital control device, including：Output voltage monitoring modular, use
In collection totem PFC VDs VDC；Input voltage monitoring modular, for gathering totem PFC input voltages VACAnd judge
Input voltage VACPolarity；Input current monitoring modular, for gathering totem PFC input currents iL；And digitial controller, use
In realizing digital servo-control, input voltage virtual value and instantaneous value are calculated, and according to input voltage VAC, output voltage VDCAnd input
Electric current iLWhat is obtained is used to drive the drive signal of totem PFC GaN MOSFET bridge arms.
Further, the digitial controller includes：PLL modules, input voltage virtual value computing module, input voltage
Phase calculation module, feedover dutycycle computing module, PWM output modules, outer voltage adjuster, current inner loop adjuster, puts down
Side seeks reverse mould block, the first summation module, the second summation module, the 3rd summation module, the first multiplier module, the second multiplier module and
3rd multiplier module；The input of PLL modules is used for the output end for being connected to input voltage monitoring modular, input voltage virtual value
The input of computing module is connected to the first output end of PLL modules, and the input of input voltage phase computing module is connected to
Second output end of PLL modules, the first input end of the second multiplier module are connected to the defeated of input voltage virtual value computing module
Go out end, the second input of the second multiplier module is connected to the output end of input voltage phase computing module, square seeks reverse mould block
Input be connected to the output end of input voltage virtual value computing module, the first input end of the first summation module is used to receive
Output order voltage VDC-ref, it is second defeated to be used to be connected to output voltage monitoring modular the second input of the first summation module
Go out end, the input of outer voltage adjuster is connected to the output end of the first summation module, the first input of the first multiplier module
End is connected to the output end of outer voltage adjuster, and the second input of the first multiplier module, which is connected to, square seeks the defeated of reverse mould block
Go out end, the first input end of the 3rd multiplier module is connected to the output end of the first multiplier module, and the second of the 3rd multiplier module is defeated
Enter the output end that end is connected to the second multiplier module, the first input end of the second summation module is connected to the defeated of the 3rd multiplier module
Go out end, the second input of the second summation module is used for the output end for being connected to input current monitoring modular, current inner loop regulation
The input of device is connected to the output end of the second summation module, and the first input end of the 3rd summation module is connected to current inner loop tune
The output end of device is saved, the second input of the 3rd summation module is connected to the output end of the feedforward dutycycle computing module, PWM
The input of output module is connected to the output end of the 3rd summation module, and the output end of PWM output modules is used for output driving figure
Rise the drive signal of PFC GaN MOSFET bridge arms；The first input end of feedforward dutycycle computing module is connected to the second multiplication modulo
The output end of block, the second input of feedforward dutycycle computing module are used for the output end for being connected to output voltage monitoring modular.
The present invention is feedovered by introducing dutycycle so that current inner loop adjuster only needs to suppress small-signal disturbance, carries significantly
The high ability of controller tracking power frequency sinusoidal current, solves the problems, such as that digital control totem PFC control effects are bad；Collection
Input voltage zero crossing carries out digital servo-control, obtains input voltage phase value by inquiring about sine table, collection input voltage is real-time
Value carries out virtual value calculating, and calculated input voltage instantaneous value is as input current command value and feedforward dutycycle meter
Module input value is calculated, so as to eliminate the output duty cycle disturbance that input voltage sampling deviation is brought, improves digital control figure
Rise PFC anti-interference and stability.
Brief description of the drawings
Fig. 1 is totem PFC main circuit topological structure schematic diagrames；
Fig. 2 is using the digital control totem PFC controling device structure diagrams of the present invention；
Fig. 3 is the flow chart of totem PFC full digital control methods of the present invention；
Fig. 4 is the control block diagram of totem PFC full digital control methods of the present invention；
In Fig. 5, (a) is that the totem PFC for the control method control that prior art provides is inputted under high voltage and high power occasion
Current waveform expanded view, input voltage waveform and output voltage waveform；(b) it is the figure of control method provided by the invention control
Rise PFC input current waveform expanded view, input voltage waveform and output voltage waveform under high voltage and high power occasion.
Embodiment
In order to make the purpose , technical scheme and advantage of the present invention be clearer, it is right below in conjunction with drawings and Examples
The present invention is further elaborated.It should be appreciated that the specific embodiments described herein are merely illustrative of the present invention, and
It is not used in the restriction present invention.
The invention provides a kind of totem PFC full digital control method, reduces input current THD, improves numeral
The anti-interference degree of PFC.
This method comprises the following steps：
(1) outer voltage control method：
(A) totem PFC input ac voltages, when monitoring totem PFC input ac voltage zero passages, monitoring modular are monitored
Zero passage detection signal is sent, digitial controller capture zero passage detection signal flipping side edge, carries out digital servo-control；
(B) totem PFC input ac voltages, collection input voltage instantaneous value V are monitoredAC, counted in digitial controller
Calculation obtains input voltage virtual value Vrms, and corresponding control parameter is selected according to input voltage valid value range, if input voltage
For low pressure, then outer voltage adjuster and current inner loop adjuster selection low voltage control parameter, electric if input voltage is high pressure
Press outer shroud adjuster and current inner loop adjuster selection high voltage control parameter；
(C) totem PFC output busbar voltages V is monitoredDC, with reference voltage VDC-refMake the difference to obtain command voltage VDC-refWith working as
Preceding actual bus voltage VDCVoltage error signal Verr, voltage error signal VerrObtained after the correction of outer voltage adjuster
Input power instructs PIN-ref；
(2) current inner loop control method：
(D) lock phase after the completion of, by table look-up obtain present input voltage phase value, and with input voltage virtual value VrmsPhase
Multiply, the input voltage instantaneous value V calculatedINAC；
(E) 1/V reciprocal of computation of table lookup input voltage virtual value square is passed through2 rms, and the input voltage with calculating is real
Duration VINAC, input power instruction PIN-refIt is multiplied, obtains input current command value iL-ref；
(F) input current i is monitoredL, with input current command value iL-refMake the difference, obtain error signal Ierr, through in overcurrent
Output pwm signal dutycycle d1 is obtained after the correction of ring adjuster；
Shown in Boost circuit input and output voltage steady state relation formula such as following formula (1)：
It is dutycycle D such as following formulas (2) institute required for meeting output voltage stabilization that can obtain stable state lower any time according to (1) formula
Show：(2) formula is applied in circuit of power factor correction, obtains the dutycycle d2 such as following formulas that feedover
(3) shown in：
(G) the input voltage V calculated is utilizedINACFeedforward dutycycle d2 is calculated, elimination input voltage sample strip comes dry
Disturb, feedforward dutycycle d2 be added with current inner loop adjuster output duty cycle d1, obtains final output pwm signal dutycycle d,
And the drive signal S1, S2 for driving totem PFC GaN MOSFET bridge arms are obtained by PWM module.
As shown in Fig. 2 the embodiment of the present invention, which additionally provides a set of totem PFC suitable for above-mentioned control method, controls dress
Put, including：
Output voltage monitoring modular, for gathering totem PFC VDs；
Input voltage monitoring modular, judge for gathering input voltage and input voltage polarity；
Input current monitoring modular, for gathering totem PFC input inductive currents；
Digitial controller, for digital servo-control, input voltage virtual value and instantaneous value are calculated, and produce by above-mentioned control
The pwm signal that method is calculated.
Wherein, digitial controller includes：PLL modules 8, input voltage virtual value computing module 9, input voltage phase calculate
Module 10, feedforward dutycycle computing module 18, PWM output modules 19, outer voltage adjuster 4, current inner loop adjuster 16, puts down
Side seeks reverse mould block 20, and the first summation module 3, the second summation module 15, the 3rd summation module 17, the first multiplier module 5, second multiply
The multiplier module 12 of method module 11 and the 3rd；The input of PLL modules 8 is used for the output end for being connected to input voltage monitoring modular 7,
The input of input voltage virtual value computing module 9 is connected to the first output end of PLL modules 8, and input voltage phase calculates mould
The input of block 10 is connected to the second output end of PLL modules 8, and the first input end of the second multiplier module 11 is connected to input electricity
The output end of valid value computing module 9 is pressed with, the second input of the second multiplier module 11 is connected to input voltage phase and calculates mould
The output end of block 10, the input of reverse mould block 20 square is asked to be connected to the output end of input voltage virtual value computing module 9, first
The first input end of summation module 3 is used for Rreceive output command voltage VDC-ref, the second input of the first summation module 3 is used for
The second output end of output voltage monitoring modular 2 is connected to, the input of outer voltage adjuster 4 is connected to the first summation module
3 output end, the first input end of the first multiplier module 5 are connected to the output end of outer voltage adjuster 4, the first multiplier module
5 the second input is connected to square output end for seeking reverse mould block 20, and the first input end of the 3rd multiplier module 12 is connected to
The output end of one multiplier module 5, the second input of the 3rd multiplier module 12 are connected to the output end of the second multiplier module 11, the
The first input end of two summation modules 15 is connected to the output end of the 3rd multiplier module 12, the second input of the second summation module 15
The output end for being connected to input current monitoring modular 14 is held, the input of current inner loop adjuster 16 is connected to the second summation
The output end of module 15, the first input end of the 3rd summation module 17 are connected to the output end of current inner loop adjuster 16, and the 3rd
Second input of summation module 17 is connected to the output end of feedforward dutycycle computing module 18, the input of PWM output modules 19
End is connected to the output end of the 3rd summation module 17, and the output end of PWM output modules 19 is used for output driving totem PFC GaN
The drive signal of MOSFET bridge arm；The first input end of feedforward dutycycle computing module 18 is connected to the defeated of the second multiplier module 11
Go out end, the second input of feedforward dutycycle computing module 18 is used for the output end for being connected to output voltage monitoring modular 2.
The present invention is feedovered by introducing dutycycle so that current inner loop adjuster only needs to suppress small-signal disturbance, carries significantly
The high ability of controller tracking power frequency sinusoidal current, solves the problems, such as that digital control totem PFC control effects are bad；Collection
Input voltage zero crossing carries out digital servo-control, obtains input voltage phase value by inquiring about sine table, collection input voltage is real-time
Value carries out virtual value calculating, and calculated input voltage instantaneous value is as input current command value and feedforward dutycycle meter
Module input value is calculated, so as to eliminate the output duty cycle disturbance that input voltage sampling deviation is brought, improves digital control figure
Rise PFC anti-interference and stability.
This example 1 is the totem PFC control process of use control method of the present invention, technical parameter used by this example
It is as follows：Input filter inductance selects iron nickel powder core magnet ring, and 13 strands of diameter 0.51mm enamel-covered wires simultaneously form around coiling, static
Inductance 750uH@0A；Switching tube selects the TPH3207WS of Transphormusa companies production, rated voltage 650V, rated current
50A；Bus capacitor selects four capacitances in parallel with the electrochemical capacitor that two capacitances are 270uF for 330uF electrochemical capacitor, pressure-resistant
It is 450V, total bus capacitor is 1620uF；Nominal input voltage is 220V, and specified busbar voltage is 390V, rated output work(
Rate is 3300W, switching frequency fswitch40kHz；Under above technical parameter, according to experiment and simulation result, input voltage is obtained
Outer voltage compensator parameter is kvp=12 when in the range of 85V~165V, kvi=0.018375, current inner loop compensator ginseng
Number is kip=0.015, and kii=0.00075, input voltage outer voltage compensator parameter in 165V~265V is kvp=
23.5, kvi=0.018375, current inner loop compensator parameter is kip=0.04449, kii=0.000489.
The present invention will be described in detail below in conjunction with the accompanying drawings.
The totem PFC main circuit topological structures of control method control of the present invention are as shown in figure 1, single phase alternating current power supply AC mono-
End passes through boost inductance L and Q1、Q2The GaN MOSFET bridge arms midpoint of composition is connected, the other end and D1、D2The diode bridge of composition
Arm midpoint is connected, and DC side output end is parallel with filter capacitor COWith DC load resistance RL, based on this circuit topology, foundation is adopted
With the control device structure of control method of the present invention as shown in Fig. 2 control device includes：Input voltage monitoring modular 7, input electricity
Monitoring modular 10, output voltage monitoring modular 2 and digitial controller are flowed, wherein, digitial controller includes：PLL modules 8, input
Voltage effective value computing module 9, input voltage phase computing module 10, feedforward dutycycle computing module 18, PWM output modules
19, outer voltage adjuster 4, current inner loop adjuster 16 square asks reverse mould block 20, the first summation module 3, the second summation module
15th, the 3rd summation module 17, the first multiplier module 5, the second multiplier module 11, the 3rd multiplier module 12.Input voltage monitors mould
Block 7, input current monitoring modular 10 and output voltage monitoring modular 2 gather input voltage, input current and output voltage respectively
After be sent into digitial controller；PLL modules 8 obtain input voltage zero passage information, realize digital servo-control function；Input voltage virtual value
Computing module 9 square asks reverse mould block 20 to put down input voltage virtual value by accumulation calculating output-input voltage virtual value
Derivative action is sought behind side；Input voltage phase value is calculated after obtaining PLL module informations in input voltage phase computing module 10；
Input voltage phase computing module output valve is multiplied work by the second multiplier 11 with input voltage virtual value computing module output valve
For the duty cycle module input signal that feedovers；First summation module 3 makes the difference output voltage command value and output voltage instantaneous value
To error signal, voltage regulator error signal is adjusted compensation；First multiplier module 5 and the 3rd multiplier module 12 are by electricity
Pressure outer shroud regulator output signal, square module output signal and the output signal of the second multiplier 11 is asked down to carry out multiplying,
Obtain input current reference signal；Input current reference signal and input current instantaneous value are made the difference acquisition by the second summation module 15
Input current error signal, current inner loop adjuster current error signal are adjusted compensation, export forward path dutycycle
d1；The duty cycle signals that feedover obtain input voltage signal from the second multiplier 11 and from output voltage monitoring modulars
Output voltage signal, feedforward dutycycle d2 is calculated；3rd summation module 17 by forward path dutycycle d1 and feedforward duty
PWM output modules, output drive signal S are sent into after being added than d2Q1And SQ2, Q1 and Q2 are controlled.Itd is proposed control device
Then corresponding control block diagram passes through accumulation calculating as shown in figure 4, by digital servo-control and acquisition input voltage phase value of tabling look-up
Input voltage virtual value is obtained, then the input voltage instantaneous value for obtaining and being calculated that both are multiplied, by output voltage reference value
Make the difference to obtain output voltage error signal with output voltage instantaneous value, benefit is adjusted by the outer voltage adjuster of PI forms
Repay, obtain the inverse of input voltage virtual value square by way of tabling look-up, and the input voltage instantaneous value with being calculated and
Outer voltage regulator output signal is multiplied to obtain input current reference value, is then entered by the current inner loop adjuster of PI forms
Row regulation compensation obtains forward path dutycycle d1, then obtains feedforward dutycycle d2 by the dutycycle calculation formula that feedovers, and preceding
It is added to obtain final output dutycycle to passage dutycycle d1.
Its corresponding control method flow chart is as shown in figure 3, comprise the following steps that：
(1) outer voltage control method：
(1.1) input voltage monitoring modular collection totem PFC input voltages V is utilizedAC, when monitoring input voltage zero passage
When, input voltage measurement module sends zero passage detection signal, and digitial controller captures zero passage detection signal by CAP modules and overturn
Edge, digital servo-control is carried out in each input voltage zero-acrross ing moment by phaselocked loop, until the input voltage zero crossing detected
200 power frequency period zero deflections are continued to exceed with digitial controller internal sine table zero crossing, then digital servo-control is completed；
(1.2) after the completion of locking phase, input voltage virtual value calculating is carried out inside digitial controller, obtaining input voltage has
Valid value Vrms, controlled from traditional analog and input voltage virtual value carry out to classification is different, it is of the invention in full digital control method can
To calculate output voltage virtual value in real time, computational methods are as follows：
Utilize input voltage monitoring modular collection input voltage instantaneous value VAC, the input voltage instantaneous value that will collect every time
VACCumulative, the cumulative points of half of power frequency period areT is power frequency period, fswitchFor converter switches frequency, N
For cumulative points, after half period is added to, changed by the mathematical relationship of virtual value and accumulated value, obtain single meter
The input voltage virtual value calculated, the virtual value being calculated for continuous 20 times carried out into average calculating operation obtain finally entering voltage to have
Valid value, shown in its expression formula such as formula (4)：
(1.3) after obtaining input voltage virtual value by above-mentioned effective value calculating method, according to the input electricity being calculated
It is pressed with valid value size and selects corresponding control parameter, if input voltage virtual value in 85V~165V, selects low voltage control ginseng
Number, i.e. the outer voltage compensator parameter kvp=12 suitable for low input, kvi=0.018375, current inner loop compensator
Parameter kip=0.015, kii=0.00075, if input voltage virtual value in 165~265V, selects high voltage control parameter, i.e.,
Suitable for the outer voltage compensator parameter kvp=23.5 of high input voltage, kvi=0.018375, current inner loop compensator ginseng
Number kip=0.04449, kii=0.000489；
(1.4) output voltage monitoring modular collection output voltage V is utilizedDC, with output order voltage VDC-refMake the difference, obtain
Error signal Verr, input power instruction P is obtained after the correction of outer voltage adjusterIN-ref；
(2) current inner loop control method：
(2.1) after the completion of locking phase, current input electricity is obtained by inquiring about the discrete sine table stored in advance inside controller
Press phase value Vphase_tab, and with input voltage virtual value VrmsIt is multiplied, the input voltage instantaneous value V calculatedINAC, its table
Up to formula such as formula (5) Suo Shi；VINAC=Vphase_tab*Vrms……(5)；
(2.2) division table stored in advance inside controller by inquiring about calculates the inverse 1/ of input voltage virtual value square
V2 rms, and the input voltage instantaneous value V with calculatingINAC, input power instruction PIN-refIt is multiplied, obtains input current command value
iL-ref, shown in its expression formula such as formula (6)；
(2.3) input current monitoring modular collection input current i is utilizedL, with input current command value iL-refMake the difference, obtain
Error signal Ierr, output pwm signal dutycycle d1 is obtained after the correction of current inner loop adjuster, reality is calculated by formula (3)
When feedover dutycycle d2, will feedforward dutycycle d2 be multiplied by proportionality coefficient km, km for ensure converter stably on the premise of can take
The maximum arrived, generally 0.9~0.95, then it is added with current inner loop adjuster output duty cycle d1, obtains final output
Pwm signal dutycycle d, and the drive signal S1 for driving totem PFC GaN MOSFET bridge arms is obtained by PWM module,
S2。
To verify the control performance of control method of the present invention, this example 2 will be direct by simulation control described in prior art
Method processed be transplanted to it is digital control, collection input voltage instantaneous value as input current instruction, merely with current inner loop bandwidth with
Control method is contrasted used by this method of track input current instructional waveform and example 1, in technical parameter as previously described
Totem pfc circuit on be respectively controlled, and using Tektronix companies of the U.S. production model TPS024B oscillographys
Device gathers input current waveform under different control methods, output voltage waveforms and input voltage waveform such as Fig. 5 (a), (b) institute respectively
Show.Compares figure 5 (a), (b) can be seen that：Under constructed parameter, according to the control method described in prior art, due to
The influence that digital delay is brought make it that current inner loop bandwidth is limited, and tracking power current waveform ability controls not as simulation, input
Nearby distortion is very big for current zero-crossing point, and input current is due to directly using the input voltage waveform collected as instruction, current waveform
In the presence of many burrs, measuring input current THD using the power analyzer of the model 3390 of HIOKI companies production is
18.59%；After full digital control method of the present invention, input current waveform has good improvement, can be good at
Input voltage waveform is tracked, measuring input current THD using the power analyzer of the model 3390 of HIOKI companies production is
2.53%.
According to experimental result, it can be clearly seen that, full digital control method control effect provided by the invention is better than existing
Directly transplanting simulation control method, can substantially reduce input current THD, eliminate input voltage sampling interference, it is very suitable
For requiring higher occasion to input current THD such as Vehicular charger.
As it will be easily appreciated by one skilled in the art that the foregoing is merely illustrative of the preferred embodiments of the present invention, not to
The limitation present invention, all any modification, equivalent and improvement made within the spirit and principles of the invention etc., all should be included
Within protection scope of the present invention.
Claims (9)
1. a kind of totem PFC full digital control method, it is characterised in that comprise the steps：
(1) totem PFC input voltages V is gatheredAC, and work as the input voltage VACZero passage detection signal is exported during zero passage；And capture
The flipping side edge of the zero passage detection signal, by carrying out digital servo-control in each input voltage zero-acrross ing moment, until described defeated
Enter voltage VACZero crossing and digitial controller internal sine table zero crossing zero deflection when complete digital servo-control；
(2) it is effective by carrying out input voltage virtual value calculating acquisition input voltage inside digitial controller after the completion of phase is locked
Value Vrms；And according to the input voltage virtual value VrmsSize select corresponding control parameter to input current waveform and output
Voltage swing is controlled；
(3) output voltage V is gatheredDC, and by the output voltage VDCWith the output order voltage V of converter settingDC-refAfter making the difference
Obtain error signal Verr, the error signal VerrInput power instruction P is obtained after the correction of outer voltage adjusterIN-ref；
(4) the discrete sine table stored in advance inside controller after the completion of phase is locked by inquiring about obtains present input voltage phase
Value Vphase_tab, and according to present input voltage phase value Vphase_tabWith the input voltage virtual value VrmsObtain input voltage
Instantaneous value VINAC；
(5) division table stored in advance inside controller by inquiring about obtains the 1/V reciprocal of input voltage virtual value square2 rms, and
According to the 1/V reciprocal2 rms, the input voltage instantaneous value VINACP is instructed with the input powerIN-refInput current is obtained to refer to
Make value iL-ref；
(6) input current i is gatheredL, and by the input current iLWith the input current command value iL-refError is obtained after making the difference
Signal Ierr, the error signal IerrOutput duty cycle d1, and the duty that will feedover are obtained after the correction of current inner loop adjuster
Acquisition final output pwm signal dutycycle d after being added after proportionality coefficient km with the output duty cycle d1 is multiplied by than d2, according to institute
State dutycycle d and export drive signal for driving totem PFC GaN MOSFET bridge arms.
2. full digital control method as claimed in claim 1, it is characterised in that the proportionality coefficient km is steady to ensure converter
The maximum that can be got on the premise of fixed, the value of the proportionality coefficient km is 0.9~0.95.
3. full digital control method as claimed in claim 1, it is characterised in that in step (2), the voltage effective valueWherein, M is calculation times, and N is the cumulative points of half of power frequency period,T is power frequency
Cycle, fswitchFor converter switches frequency.
4. the full digital control method as described in claim any one of 1-3, it is characterised in that in step (2), if input electricity
Valid value is pressed with 85V~165V, selects low voltage control parameter, if input voltage virtual value in 165~265V, selects high pressure
Control parameter.
5. the full digital control method as described in claim any one of 1-4, it is characterised in that in step (4), input voltage
Instantaneous value VINAC=Vphase_tab*Vrms。
6. the full digital control method as described in claim any one of 1-5, it is characterised in that in step (5), input current
Command value
7. the full digital control method as described in claim any one of 1-6, it is characterised in that in step (6), feedforward in real time
Dutycycle
A kind of 8. totem PFC full-digital control device, it is characterised in that including：
Output voltage monitoring modular, for gathering totem PFC VDs VDC；
Input voltage monitoring modular, for gathering totem PFC input voltages VACAnd judge input voltage VACPolarity；
Input current monitoring modular, for gathering totem PFC input currents iL；And
Digitial controller, for realizing digital servo-control, input voltage virtual value and instantaneous value are calculated, and according to input voltage VAC,
Output voltage VDCWith input current iLWhat is obtained is used to drive the drive signal of totem PFC GaN MOSFET bridge arms.
9. full-digital control device as claimed in claim 8, it is characterised in that the digitial controller includes：PLL modules
(8), input voltage virtual value computing module (9), input voltage phase computing module (10), feedover dutycycle computing module
(18), PWM output modules (19), outer voltage adjuster (4), current inner loop adjuster (16) square seek reverse mould block (20), and
One summation module (3), the second summation module (15), the 3rd summation module (17), the first multiplier module (5), the second multiplier module
And the 3rd multiplier module (12) (11)；
The input of the PLL modules (8) is used for the output end for being connected to the input voltage monitoring modular (7), the input
The input of voltage effective value computing module (9) is connected to the first output end of the PLL modules (8), the input voltage phase
The input of position computing module (10) is connected to the second output end of the PLL modules (8), second multiplier module (11)
First input end is connected to the output end of the input voltage virtual value computing module (9), second multiplier module (11)
Second input is connected to the output end of the input voltage phase computing module (10), and described square is sought the defeated of reverse mould block (20)
Enter the output end that end is connected to the input voltage virtual value computing module (9), the first input of first summation module (3)
Hold and be used for Rreceive output command voltage VDC-ref, the second input of first summation module (3) is for being connected to the output
Second output end of voltage monitoring module (2), the input of the outer voltage adjuster (4) are connected to the first summation mould
The output end of block (3), the first input end of first multiplier module (5) are connected to the defeated of the outer voltage adjuster (4)
Going out end, the second input of first multiplier module (5) is connected to the described square of output end for asking reverse mould block (20), and described the
The first input end of three multiplier modules (12) is connected to the output end of first multiplier module (5), the 3rd multiplier module
(12) the second input is connected to the output end of second multiplier module (11), and the first of second summation module (15)
Input is connected to the output end of the 3rd multiplier module (12), and the second input of second summation module (15) is used for
The output end of the input current monitoring modular (14) is connected to, the input of the current inner loop adjuster (16) is connected to institute
The output end of the second summation module (15) is stated, the first input end of the 3rd summation module (17) is connected to the current inner loop
The output end of adjuster (16), the second input of the 3rd summation module (17) are connected to the feedforward dutycycle and calculate mould
The output end of block (18), the input of the PWM output modules (19) are connected to the output end of the 3rd summation module (17),
The output end of the PWM output modules (19) is used for the drive signal of output driving totem PFC GaN MOSFET bridge arms；It is described
The first input end of feedforward dutycycle computing module (18) is connected to the output end of second multiplier module (11), the feedforward
Second input of dutycycle computing module (18) is used for the output end for being connected to the output voltage monitoring modular (2).
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Effective date of registration: 20221031 Address after: 430000 Floor 2, Building 1, Nanhua Industrial Park, Science Park, Wuhan University of Technology, Donghu New Technology Development Zone, Wuhan City, Hubei Province Patentee after: Wuhan Matrix Energy Technology Co.,Ltd. Address before: 430074 Hubei Province, Wuhan city Hongshan District Luoyu Road No. 1037 Patentee before: HUAZHONG University OF SCIENCE AND TECHNOLOGY |